RT8025
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DS8025-00 October 2008 www.richtek.com
Features
+2.5V to +5.5V Input Range
Adjustable Output From 0.5V to VIN
1.0V, 1.2V, 1.3V, 1.5V, 1.8V, 2.5V and 3.3V Fixed/
Adjustable Output Voltage
400mA Output Current
95% Efficiency
No Schottky Diode Required
1.25MHz Fixed-Frequency PWM Operation
Small SOT-23-5 and TSOT-23-5 Package
RoHS Compliant and Halogen Free
Applications
Cellular Telephones
Personal Information Appliances
Wireless and DSL Modems
MP3 Players
Portable Instruments
1.25MHz, 400mA, High Efficiency PWM Step-Down
DC/DC Converter
General Description
The RT8025 is a high-efficiency pulse-width-modulated
(PWM) step-down DC-DC converter. Capable of delivering
400mA output current over a wide input voltage range from
2.5 to 5.5V, the RT8025 is ideally suited for portable
electronic devices that are powered from 1-cell Li-ion
battery or from other power sources within the range such
as cellular phones, PDAs and handy-terminals.
Internal synchronous rectifier with low RDS(ON) dramatically
reduces conduction loss at PWM mode. No external
Schottky diode is required in practical application. The
RT8025 automatically turns off the synchronous rectifier
while the inductor current is low and enters discontinuous
PWM mode. This can increase efficiency at light load
condition.
The RT8025 enters Low-Dropout mode when normal PWM
cannot provide regulated output voltage by continuously
turning on the upper P-MOSFET. RT8025 enter shutdown
mode and consumes less than 0.1uA when EN pin is pulled
low.
The switching ripple is easily smoothed-out by small
package filtering elements due to a fixed operation
frequency of 1.25MHz. This along with small SOT-23-5
and TSOT-23-5 package provides small PCB area
application. Other features include soft start, lower internal
reference voltage with 2% accuracy, over temperature
protection, and over current protection.
Ordering Information
Pin Configurations
(TOP VIEW)
SOT-23-5/TSOT-23-5
RT8025(- )
Package Type
B : SOT-23-5
J5 : TSOT-23-5
Operating Temperature Range
G : Green (Halogen Free with Commer-
cial Standard)
Output Voltage
Default : Adjustable
10 : 1.0V
12 : 1.2V
13 : 1.3V
15 : 1.5V
18 : 1.8V
25 : 2.5V
33 : 3.3V
VIN GND EN
LX FB/VOUT
4
23
5
Note :
Richtek Green products are :
` RoHS compliant and compatible with the current require-
ments of IPC/JEDEC J-STD-020.
` Suitable for use in SnPb or Pb-free soldering processes.
RT8025
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DS8025-00 October 2008www.richtek.com
Typical Application Circuit
Figure 1. Fixed Voltage Regulator
Figure 2. Adjustable Voltage Regulator
0.5VV
and 1MR2R1 with
R2
R1
1 x VV
REF(Typ.)
REFOUT
=
Ω≤+
⎟
⎠
⎞
⎜
⎝
⎛+=
Layout Guide
Layout note:
1. The distance that CIN connects to VIN is as close as possible (Under 2mm).
2. COUT should be placed near RT8025.
Figure 3
VIN
GND
EN
LX
2
3
5
4
1
VOUT
VIN
CIN
VOUT
L
GND
COUT
VIN
GND
EN
LX
2
3
5
4
1
FB
VIN
CIN
VOUT
L
GND
VOUT
COUT
R2
R1
C1
4.7uF
10uF
VIN LX
GND
RT8025
EN VOUT
4.7uH
2.5V to 5.5V
VIN VOUT
CIN
L
4
5
1
3
2
COUT
4.7uF
10uF
VIN LX
GND
RT8025
EN FB
4.7uH
2.5V to 5.5V
VIN VOUT
CIN
L
4
5
1
3
2
COUT
R1
R2
C1
RT8025
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DS8025-00 October 2008 www.richtek.com
Function Block Diagram
Functional Pin Description
Pin No. Pin Name Pin Function
1 VIN Power Input.
2 GND Ground.
3 EN Chip Enable (Active High, do not leave EN pin floating, and VEN < VIN + 0.6V).
4 FB/VOUT Feedback Input Pin.
5 LX Pin for Switching.
COMP
RC
RS1
RS2
EN VIN
LX
FB/VOUT
UVLO &
Power Good
Detector VREF
Slope
Compensation
Current
Sense
OSC &
Shutdown
Control
Zero
Detector
Current
Limit
Detector
Driver
Control
Logic
PWM
Comparator
Error
Amplifier
GND
RT8025
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Absolute Maximum Ratings (Note 1)
Supply Input Voltage ------------------------------------------------------------------------------------------------------ 6.5V
Enable, FB Voltage ------------------------------------------------------------------------------------------------------- VIN + 0.6V
Power Dissipation, PD @ TA = 25°C
SOT-23-5, TSOT-23-5 ----------------------------------------------------------------------------------------------------- 0.4W
Package Thermal Resistance (Note 4)
SOT-23-5, TSOT-23-5, θJA ----------------------------------------------------------------------------------------------- 250°C/W
SOT-23-5, TSOT-23-5, θJC ----------------------------------------------------------------------------------------------- 130°C/W
Junction Temperature Range -------------------------------------------------------------------------------------------- 150°C
Lead Temperature (Soldering, 10 sec.) ------------------------------------------------------------------------------- 260°C
Storage Temperature Range -------------------------------------------------------------------------------------------- −65°C to 150°C
ESD Susceptibility (Note 2)
HBM (Human Body Mode) ---------------------------------------------------------------------------------------------- 2kV
MM (Machine Mode) ------------------------------------------------------------------------------------------------------ 200V
Electrical Characteristics
(VIN = 3.6V, VOUT = 2.5V, VREF = 0.5V, L = 4.7μH, CIN = 4.7μF, C OUT = 10μF, T A = 25°C, IMAX = 400mA, unless otherwise specified)
Parameter Symbol Test Conditions Min Typ Max Units
Input Voltage Range VIN 2.5 -- 5.5 V
Quiescent Current IQ I
OUT = 0mA, VFB = VREF + 5% -- 50 100
μA
Shutdown Current ISHDN EN = GND -- 0.1 1 μA
Reference Voltage VREF For adjustable output voltage 0.49 0.5 0.51 V
Adjustable Output Range VOUT VREF -- VIN − 0.2 V
ΔVOUT VIN = 2.5 to 5.5V, VOUT = 1.0V
0A < IOUT < 400mA −3 -- +3 %
ΔVOUT VIN = 2.5 to 5.5V, VOUT = 1.2V
0A < IOUT < 400mA −3 -- +3 %
ΔVOUT VIN = 2.5 to 5.5V, VOUT = 1.3V
0A < IOUT < 400mA −3 -- +3 %
ΔVOUT VIN = 2.5 to 5.5V, VOUT = 1.5V
0A < IOUT < 400mA −3 -- +3 %
ΔVOUT VIN = 2.5 to 5.5V, VOUT = 1.8V
0A < IOUT < 400mA −3 -- +3 %
ΔVOUT VIN = VOUT + ΔV to 5.5V (Note 5)
VOUT = 2.5V, 0A < IOUT < 400mA −3 -- +3 %
ΔVOUT VIN = VOUT + ΔV to 5.5V (Note 5)
VOUT = 3.3V, 0A < IOUT < 400mA −3 -- +3 %
Output Voltage
Accuracy Fix
ΔVOUT VIN = VOUT + 0.2V to 5.5V
0A < IOUT < 400mA −3 -- +3 %
To be continued
Recommended Operating Conditions (Note 3)
Supply Input Voltage ------------------------------------------------------------------------------------------------------ 2.5V to 5.5V
Junction Temperature Range -------------------------------------------------------------------------------------------- −40°C to 125°C
Ambient Temperature Range -------------------------------------------------------------------------------------------- −40°C to 85°C
RT8025
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Parameter Symbol Test Conditions Min Typ Max Units
Output Voltage
Accuracy Adjustable ΔVOUT VIN = VOUT + ΔV to 5.5V (Note 5)
0A < IOUT < 400mA −3 -- +3 %
FB Input Current IFB V
FB = VIN −50 -- 50 nA
VIN = 3.6V -- 0.3 0.65
RDS(ON) of P-Channel MOSFET RDS(ON)_P IOUT = 200mA VIN = 2.5V -- 0.4 0.80
Ω
VIN = 3.6V -- 0.25 0.55
RDS(ON) of N-Channel MOSFET RDS(ON)_N IOUT = 200mA VIN = 2.5V -- 0.35 0.65
Ω
P-Channel Current Limit ILIM_P VIN = 2.5V to 5.5 V 1 -- 1.8 A
EN High-Level Input Voltage VEN_H V
IN = 2.5V to 5.5V 1.5 -- -- V
EN Low-Level Input Voltage VEN_L V
IN = 2.5V to 5.5V -- -- 0.4 V
Undervoltage Lock Out threshold -- 1.8 -- V
Hysteresis -- 0.1 -- V
Oscillator Frequency fOSC V
IN = 3.6V, IOUT = 100mA 0.8 1.25 1.85 MHz
Thermal Shutdown Temperature TSD -- 160 -- °C
Min. On Time -- 50 -- ns
Max. Duty Cycle 100 -- -- %
LX Leakage Current VIN = 3.6V, VLX = 0V or VLX = 3.6V -1 -- 1
μA
Note 1. Stresses listed as the above “Absolute Maximum Ratings” may cause permanent damage to the device. These are for
stress ratings. Functional operation of the device at these or any other conditions beyond those indicated in the
operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended
periods may remain possibility to affect device reliability.
Note 2. Devices are ESD sensitive. Handling precaution recommended.
Note 3. The device is not guaranteed to function outside its operating conditions.
Note 4. θJA is measured in the natural convection at TA = 25°C on a low effective thermal conductivity test board of
JEDEC 51-3 thermal measurement standard.
Note 5. ΔV = IOUT x RDS(ON)_P
RT8025
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Typical Operating Characteristics
Frequency vs. Temperature
1.10
1.12
1.14
1.16
1.18
1.20
1.22
1.24
1.26
-50 -25 0 25 50 75 100 125
Temperature
Frequency (MHz)
VIN = 3.3V, VOUT = 1.8V
(°C)
Frequency vs. Input Voltage
1.14
1.16
1.18
1.20
1.22
1.24
1.26
2.5 2.8 3.1 3.4 3.7 4 4.3 4.6 4.9 5.2 5.5
Input Voltage (V)
Frequency (MHz
)
VOUT = 1.8V
Current Limit vs. Input Voltage
0.00
0.25
0.50
0.75
1.00
1.25
1.50
1.75
2.00
2.25
2.50
2.5 2.8 3.1 3.4 3.7 4 4.3 4.6 4.9 5.2 5.5
Input Voltage (V)
Current Limit (A)
VOUT = 1.8V
Reference vs. Input Voltage
0.40
0.42
0.44
0.46
0.48
0.50
0.52
0.54
0.56
0.58
0.60
2.5 2.8 3.1 3.4 3.7 4 4.3 4.6 4.9 5.2 5.5
Input Voltage (V)
Reference (V)
VOUT = 1.8V
Efficiency vs. Load Current
0
10
20
30
40
50
60
70
80
90
100
0.01 0.11 0.21 0.31 0.41 0.51 0.61
Load Current (A)
Efficiency (%)
VIN = 3.3V
VIN = 5V
VOUT = 1.8V
Load Regulation
1.770
1.775
1.780
1.785
1.790
1.795
1.800
1.805
1.810
0.1 0.15 0.2 0.25 0.3 0.35 0.4
Load Current (A)
Load Regulation (V)
VIN = 3.3V
VIN = 5.5V
VIN = 2.5V
VOUT = 1.8V
RT8025
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DS8025-00 October 2008 www.richtek.com
Reference vs. Temperature
0.490
0.493
0.495
0.498
0.500
0.503
0.505
0.508
0.510
-50 -25 0 25 50 75 100 125
Temperature
Reference (V)
VIN = 3.3V, VOUT = 1.8V
(°C)
Load Transient Response
Time (50us/Div)
IOUT
(200mA/Div)
VOUT
(20mV/Div)
VIN = 3.3V, VOUT = 1.8V, IOUT = 100mA to 400mA
Load Transient Response
Time (50us/Div)
IOUT
(200mA/Div)
VOUT
(20mV/Div)
VIN = 3.3V, VOUT = 1.8V, IOUT = 200mA to 400mA
Output Ripple
Time (500ns/Div)
VOUT
(5mV/Div)
VLX
(5V/Div)
ILX
(500mA/Div)
VIN = 3.3V, VOUT = 1.8V, IOUT = 400mA
Power On
Time (100us/Div)
VEN
(5V/Div)
VOUT
(1V/Div)
IIN
(200mA/Div)
VIN = 3.3V, VOUT = 1.8V, IOUT = 400mA
Power Off
Time (100us/Div)
VEN
(5V/Div)
VOUT
(2V/Div)
IIN
(200mA/Div)
VIN = 3.3V, VOUT = 1.8V, IOUT = 400mA
RT8025
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⎥
⎦
⎤
⎢
⎣
⎡+≤
OUT
LOUT 8fC
1
ESR ΔIΔV
Applications Information
The basic RT8025 application circuit is shown in Typical
Application Circuit. External component selection is
determined by the maximum load current and begins with
the selection of the inductor value and operating frequency
followed by CIN and COUT.
Inductor Selection
For a given input and output voltage, the inductor value
and operating frequency determine the ripple current. The
ripple current ΔIL increases with higher VIN and decreases
with higher inductance.
Having a lower ripple current reduces the ESR losses in
the output capacitors and the output voltage ripple. Highest
efficiency operation is achieved at low frequency with small
ripple current. This, however, requires a large inductor.
A reasonable starting point for selecting the ripple current
is ΔIL = 0.4(IMAX). The largest ripple current occurs at the
highest VIN. To guarantee that the ripple current stays
below a specified maximum, the inductor value should be
chosen according to the following equation :
Inductor Core Selection
Once the value for L is known, the type of inductor must
be selected. High efficiency converters generally cannot
afford the core loss found in low cost powdered iron cores,
forcing the use of more expensive ferrite or mollypermalloy
cores. Actual core loss is independent of core size for a
fixed inductor value but it is very dependent on the
inductance selected. As the inductance increases, core
losses decrease. Unfortunately, increased inductance
requires more turns of wire and therefore copper losses
will increase.
Ferrite designs have very low core losses and are preferred
at high switching frequencies, so design goals can
concentrate on copper loss and preventing saturation.
Ferrite core material saturates “hard”, which means that
inductance collapses abruptly when the peak design
current is exceeded. This results in an abrupt increase in
⎥
⎦
⎤
⎢
⎣
⎡−
⎥
⎦
⎤
⎢
⎣
⎡
×
=
IN
OUTOUT
LV
V
1
Lf
V
ΔI
⎥
⎥
⎦
⎤
⎢
⎢
⎣
⎡−
⎥
⎦
⎤
⎢
⎣
⎡
Δ×
=
IN(MAX)
OUT
L(MAX)
OUT
V
V
1
If
V
L
inductor ripple current and consequent output voltage ripple.
Do not allow the core to saturate!
Different core materials and shapes will change the size/
current and price/current relationship of an inductor.
Toroid or shielded pot cores in ferrite or permalloy materials
are small and don’t radiate energy but generally cost
more than powdered iron core inductors with similar
characteristics. The choice of which style inductor to use
mainly depends on the price vs size requirements and
any radiated field/EMI requirements.
CIN and COUT Selection
The input capacitance, CIN, is needed to filter the
trapezoidal current at the source of the top MOSFET. To
prevent large ripple voltage, a low ESR input capacitor
sized for the maximum RMS current should be used. RMS
current is given by :
1
V
V
V
V
II
OUT
IN
IN
OUT
OUT(MAX)RMS −=
This formula has a maximum at VIN = 2VOUT, where IRMS
= IOUT/2. This simple worst-case condition is commonly
used for design because even significant deviations do
not offer much relief. Note that ripple current ratings from
capacitor manufacturers are often based on only 2000
hours of life which makes it advisable to further derate the
capacitor, or choose a capacitor rated at a higher
temperature than required. Several capacitors may also
be paralleled to meet size or height requirements in the
design.
The selection of COUT is determined by the effective series
resistance (ESR) that is required to minimize voltage ripple
and load step transients, as well as the amount of bulk
capacitance that is necessary to ensure that the control
loop is stable. Loop stability can be checked by viewing
the load transient response as described in a later section.
The output ripple, ΔVOUT, is determined by :
The output ripple is highest at maximum input voltage
since ΔIL increases with input voltage. Multiple capacitors
placed in parallel may be needed to meet the ESR and
RMS current handling requirements. Dry tantalum, special
RT8025
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Output Voltage Programming
The resistive divider allows the VFB pin to sense a fraction
of the output voltage as shown in Figure 4.
)
R2
R1
(1VV REF
OUT +=
where VREF is the internal reference voltage (0.5V typ.)
Efficiency Considerations
The efficiency of a switching regulator is equal to the output
power divided by the input power times 100%. It is often
useful to analyze individual losses to determine what is
limiting the efficiency and which change would produce
the most improvement. Efficiency can be expressed as :
Efficiency = 100% − (L1+ L2+ L3+ ...)
where L1, L2, etc. are the individual losses as a percentage
of input power. Although all dissipative elements in the
circuit produce losses, two main sources usually account
for most of the losses : VIN quiescent current and I2R
losses. The VIN quiescent current loss dominates the
efficiency loss at very low load currents whereas the I2R
loss dominates the efficiency loss at medium to high load
currents. In a typical efficiency plot, the efficiency curve
at very low load currents can be misleading since the
actual power lost is of no consequence.
1. The VIN quiescent current is due to two components :
the DC bias current as given in the electrical characteristics
and the internal main switch and synchronous switch gate
charge currents. The gate charge current results from
switching the gate capacitance of the internal power
MOSFET switches. Each time the gate is switched from
high to low to high again, a packet of charge ΔQ moves
from VIN to ground.
The resulting ΔQ/Δt is the current out of VIN that is typically
larger than the DC bias current. In continuous mode,
IGATECHG = f(QT+QB)
where QT and QB are the gate charges of the internal top
and bottom switches. Both the DC bias and gate charge
losses are proportional to VIN and thus their effects will
be more pronounced at higher supply voltages.
2. I2R losses are calculated from the resistances of the
internal switches, RSW and external inductor RL. In
continuous mode the average output current flowing
through inductor L is “chopped” between the main switch
and the synchronous switch. Thus, the series resistance
looking into the LX pin is a function of both top and bottom
MOSFET RDS(ON) and the duty cycle (DC) as follows :
RSW = RDS(ON)TOP x DC + RDS(ON)BOT x (1−DC)
The RDS(ON) for both the top and bottom MOSFETs can be
obtained from the Typical Performance Characteristics
For adjustable about voltage mode, the output voltage is
set by an external resistive divider according to the following
equation :
polymer, aluminum electrolytic and ceramic capacitors are
all available in surface mount packages. Special polymer
capacitors offer very low ESR but have lower capacitance
density than other types. Tantalum capacitors have the
highest capacitance density but it is important to only
use types that have been surge tested for use in switching
power supplies. Aluminum electrolytic capacitors have
significantly higher ESR but can be used in cost-sensitive
applications provided that consideration is given to ripple
current ratings and long term reliability. Ceramic capacitors
have excellent low ESR characteristics but can have a
high voltage coefficient and audible piezoelectric effects.
The high Q of ceramic capacitors with trace inductance
can also lead to significant ringing.
Using Ceramic Input and Output Capacitors
Higher values, lower cost ceramic capacitors are now
becoming available in smaller case sizes. Their high ripple
current, high voltage rating and low ESR make them ideal
for switching regulator applications. However, care must
be taken when these capacitors are used at the input and
output. When a ceramic capacitor is used at the input
and the power is supplied by a wall adapter through long
wires, a load step at the output can induce ringing at the
input, VIN. At best, this ringing can couple to the output
and be mistaken as loop instability. At worst, a sudden
inrush of current through the long wires can potentially
cause a voltage spike at VIN large enough to damage the
part.
Figure 4. Setting the Output Voltage
RT8025
GND
VFB
R1
R2
VOUT
RT8025
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Checking Transient Response
The regulator loop response can be checked by looking
at the load transient response. Switching regulators take
several cycles to respond to a step in load current. When
a load step occurs, VOUT immediately shifts by an amount
equal to ΔILOAD (ESR), where ESR is the effective series
resistance of COUT. ΔILOAD also begins to charge or
discharge COUT generating a feedback error signal used
by the regulator to return VOUT to its steady-state value.
During this recovery time, VOUT can be monitored for
overshoot or ringing that would indicate a stability problem.
Layout Considerations
Follow the PCB layout guidelines for optimal performance
of RT8025.
` For the main current paths as indicated in bold lines in
Figure 6 keep their traces short and wide.
` Put the input capacitor as close as possible to the device
pins (VIN and GND).
` LX node is with high frequency voltage swing and should
be kept small area. Keep analog components away from
LX node to prevent stray capacitive noise pick-up.
curves. Thus, to obtain I2R losses, simply add RSW to RL
and multiply the result by the square of the average output
current.
Other losses including CIN and COUT ESR dissipative
losses and inductor core losses generally account for less
than 2% of the total loss.
Thermal Considerations
The maximum power dissipation depends on the thermal
resistance of IC package, PCB layout, the rate of
surroundings airflow and temperature difference between
junction to ambient. The maximum power dissipation can
be calculated by following formula :
PD(MAX) = ( TJ(MAX) - TA ) / θJA
Where TJ(MAX) is the maximum operation junction
temperature 125°C, TA is the ambient temperature and the
θJA is the junction to ambient thermal resistance.
For recommended operating conditions specification of
RT8025 DC/DC converter, where TJ (MAX) is the maximum
junction temperature of the die (125°C) and TA is the
maximum ambient temperature. The junction to ambient
thermal resistance θJA is layout dependent. For
SOT-23-5/TSOT-23-5 packages, the thermal resistance θJA
is 250°C/W on the standard JEDEC 51-3 single-layer
thermal test board. The maximum power dissipation at
TA = 25°C can be calculated by following formula :
PD(MAX) = ( 125°C - 25°C ) / 250 = 0.4 W for SOT-23-5/
TSOT-23-5 packages
The maximum power dissipation depends on operating
ambient temperature for fixed TJ(MAX) and thermal
resistance θJA. For RT8025 packages, the Figure 5 of
derating curves allows the designer to see the effect of
rising ambient temperature on the maximum power
allowed.
The value of junction to case thermal resistance θJC is
popular for users. This thermal parameter is convenient
for users to estimate the internal junction operated
temperature of packages while IC operating. It's
independent of PCB layout, the surroundings airflow effects
and temperature difference between junction to ambient.
The operated junction temperature can be calculated by
following formula :
TJ = TC + PD x θJC
Where TC is the package case (Pin 2 of package leads)
temperature measured by thermal sensor, PD is the power
dissipation defined by user's function and the θJC is the
junction to case thermal resistance provided by IC
manufacturer. Therefore it's easy to estimate the junction
temperature by any condition.
Figure 5. Derating Curves for RT8025 Package
0
50
100
150
200
250
300
350
400
450
0 20 40 60 80 100 120 140
Ambient Temperature (°C)
Maximum Power Dissipation (mW)
Single Layer PCB
SOT-23-5, TSOT-23-5 Packages
RT8025
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Component Supplier Series Inductance (uH) DCR (mΩ) Current Rating (mA) Dimensions (mm)
TAIYO Y UDE N NR 3015 2.2 60 1480 3x3x1.5
TAIYO Y UDE N NR 3015 4.7 120 1020 3x3x1.5
Sumida CDRH2D14 2.2 75 1500 4.5
x
3.2x1.55
Sumida CDRH2D14 4.7 135 1000 4.5
x
3.2x1.55
GOTREND GT SD32 2.2 58 1500 3.85x3.85x1.8
GOTREND GT SD32 4.7 146 1100 3.85x3.85x1.8
Table 1. Inductors
Component Supplier Part No. Capacitance (uF) Case Size
TDK C1608JB0J475M 4.7 0603
TDK C2012JB0J106M 10 0805
MURATA GRM188R60J475KE19 4.7 0603
MURATA GRM219R60J106ME19 10 0805
MURATA GRM219R60J106KE19 10 0805
TAIYO YUDEN JMK107BJ475RA 4. 7 0603
TAIYO YUDEN JMK107BJ106MA 10 0603
TAIYO Y UDE N JMK212BJ106RD 10 0805
Table 2. Capacitors for CIN and COUT
Recommended component selection for Typical Application
` Connect feedback network behind the output capacitors.
Keep the loop area small. Place the feedback
components near the RT8025.
` Connect all analog grounds to a command node and
then connect the command node to the power ground
behind the output capacitors.
LX
GND
RT8025
EN FB
L1
C4
VIN VOUT
C3
R1
R2
VIN
1
3
2
5
4
10uF
C1
C2
4.7uF
R3
4.7uH
Figure 6. EVB Schematic
RT8025
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Outline Dimension
AA1
e
b
B
D
C
H
L
SOT-23-5 Surface Mount Package
Dimensions In Millimeters Dimensions In Inches
Symbol
Min Max Min Max
A 0.889 1.295 0.035 0.051
A1 0.000 0.152 0.000 0.006
B 1.397 1.803 0.055 0.071
b 0.356 0.559 0.014 0.022
C 2.591 2.997 0.102 0.118
D 2.692 3.099 0.106 0.122
e 0.838 1.041 0.033 0.041
H 0.080 0.254 0.003 0.010
L 0.300 0.610 0.012 0.024
RT8025
13
DS8025-00 October 2008 www.richtek.com
Richtek Technology Corporation
Headquarter
5F, No. 20, Taiyuen Street, Chupei City
Hsinchu, Taiwan, R.O.C.
Tel: (8863)5526789 Fax: (8863)5526611
Richtek Technology Corporation
Taipei Office (Marketing)
8F, No. 137, Lane 235, Paochiao Road, Hsintien City
Taipei County, Taiwan, R.O.C.
Tel: (8862)89191466 Fax: (8862)89191465
Email: marketing@richtek.com
Information that is provided by Richtek Technology Corporation is believed to be accurate and reliable. Richtek reserves the right to make any change in circuit
design, specification or other related things if necessary without notice at any time. No third party intellectual property infringement of the applications should be
guaranteed by users when integrating Richtek products into any application. No legal responsibility for any said applications is assumed by Richtek.
TSOT-23-5 Surface Mount Package
Dimensions In Millimeters Dimensions In Inches
Symbol
Min Max Min Max
A 0.700 1.000 0.028 0.039
A1 0.000 0.100 0.000 0.004
B 1.397 1.803 0.055 0.071
b 0.300 0.559 0.012 0.022
C 2.591 3.000 0.102 0.118
D 2.692 3.099 0.106 0.122
e 0.838 1.041 0.033 0.041
H 0.080 0.254 0.003 0.010
L 0.300 0.610 0.012 0.024
AA1
e
b
B
D
C
H
L
