ADE7752BARWZ - ANALOG DEVICES

3-Phase, 3-Wire, and 4-Wire

Energy Metering IC with Pulse Output

ADE7752B

Rev. 0

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FEATURES

High accuracy supports 50 Hz/60 Hz IEC 62053-21

Less than 0.1% error over a dynamic range of 500 to 1

Compatible with 3-phase, 3-wire delta and 3-phase, 4-wire

Wye configurations

Supplies average active power on the frequency outputs F1

and F2

High frequency output (CF) is intended for calibration and

supplies instantaneous active power

Logic output REVP indicates a potential miswiring or

negative power on the sum of all phases

Direct drive for electromechanical counters and 2-phase

stepper motors (F1 and F2)

Proprietary ADCs and DSP provide high accuracy over large

variations in environmental conditions and time

On-chip power supply monitoring

On-chip creep protection (no load threshold)

On-chip reference 2.4 V ± 8% (25 ppm/°C typical) with

external overdrive capability

Single 5 V supply, low power (42.5 mW typical)

Low cost CMOS process

GENERAL DESCRIPTION

The ADE7752B is a high accuracy polyphase electrical energy

measurement IC. The ADE7752B specifications surpass the

accuracy requirements as quoted in the IEC62053-21 standard.

The only analog circuitry used in the ADE7752B is in the

analog-to-digital converters (ADCs) and reference circuit. All

other signal processing (for example, multiplication, filtering,

and summation) is carried out in the digital domain. This

approach provides superior stability and accuracy over

extremes in environmental conditions and over time.

The ADE7752B supplies average active power information on

the low frequency outputs, F1 and F2. These logic outputs can

be used to directly drive an electromechanical counter or to

interface with a microcontroller (MCU). The CF logic output

gives instantaneous active power information. This output is

intended to be used for calibration purposes.

The ADE7752B includes a power supply monitoring circuit on

the VDD pin. The ADE7752B remains inactive until the supply

voltage on VDD reaches 4 V. If the supply falls below 4 V, the

ADE7752B resets and no pulses are issued on F1, F2, and CF.

Internal phase matching circuitry ensures that the voltage and

current channels are phase matched. An internal no load

threshold ensures that the ADE7752B does not exhibit any

creep when there is no load.

The ADE7752B is available in a 24-lead SOIC package.

FUNCTIONAL BLOCK DIAGRAM

17 3

232122181211

LPF

HPF

CLKOUT

CLKIN

DGND

CFS0 F1F2S1SCF

DIGITAL-TO-FREQUENCY CONVERTER

2.4V REF

REFIN/OUT

AGND

4kΩ

IBP

IBN

VBP

ICP

ICN

VCP

IAP

IAN

VAP

ADC

VDD

ADE7752B

POWER

SUPPLY

MONITOR

ADC

HPF

LPF

LPF X

ABS

REVP

05905-001

Figure 1.

ADE7752B

Rev. 0 | Page 2 of 24

TABLE OF CONTENTS

Features .............................................................................................. 1

General Description......................................................................... 1

Functional Block Diagram .............................................................. 1

Revision History ............................................................................... 2

Specifications..................................................................................... 3

Timing Characteristics ................................................................ 4

Absolute Maximum Ratings............................................................ 5

ESD Caution.................................................................................. 5

Pin Configuration and Function Descriptions............................. 6

Typical Performance Characteristics ............................................. 8

Terminology ...................................................................................... 9

Test Circuit ...................................................................................... 10

Theory of Operation ...................................................................... 11

Power Factor Considerations.................................................... 11

Nonsinusoidal Voltage and Current ........................................ 12

Analog Inputs.................................................................................. 13

Current Channels ....................................................................... 13

Voltage Channels........................................................................ 13

Typical Connection Diagrams...................................................... 14

Current Channel Connection................................................... 14

Voltage Channel Connection.................................................... 14

Meter Connections..................................................................... 14

Power Supply Monitor ................................................................... 16

HPF and Offset Effects .................................................................. 17

Digital-to-Frequency Conversion ................................................ 18

Accumulation of 3-Phase Power .............................................. 19

Transfer Function ........................................................................... 20

Frequency Outputs F1 and F2 .................................................. 20

Frequency Output CF ................................................................ 21

Selecting a Frequency for an Energy Meter Application........... 22

Frequency Outputs..................................................................... 22

No-Load Threshold.................................................................... 23

Outline Dimensions ....................................................................... 24

Ordering Guide .......................................................................... 24

REVISION HISTORY

8/07—Revision 0: Initial Version

ADE7752B

Rev. 0 | Page 3 of 24

SPECIFICATIONS

VDD = 5 V ± 5%, AGND = DGND = 0 V, on-chip reference, CLKIN = 10 MHz, TMIN to TMAX = −40°C to +85°C, unless otherwise noted.

Table 1.

Parameter Conditions Min Typ Max Unit

ACCURACY1, 2

Measurement Error on Current

Channel

Voltage channel with full-scale signal (±500 mV), 25°C,

over a dynamic range of 500 to 1

0.1 % reading

Phase Error Between Channels

PF = 0.8 Capacitive ±0.1 Degrees

PF = 0.5 Capacitive ±0.1 Degrees

AC Power Supply Rejection SCF = 0, S0 = S1 = 1

Output Frequency Variation (CF) IA = IB = IC = 100 mV rms,

VA = VB = VC = 100 mV rms @ 50 Hz,

Ripple on VDD of 200 mV rms @ 100 Hz

0.01 % reading

DC Power Supply Rejection S1 = 1, S0 = SCF = 0

Output Frequency Variation (CF) V1 = 100 mV rms, V2 = 100 mV rms,

VDD = 5 V ± 250 mV

0.1 % reading

ANALOG INPUTS See the Analog Inputs section

Maximum Signal Levels VAP – VN, VBP – VN, VCP – VN, IAP – IAN, IBP – IBN, ICP – ICN ±0.5

V peak

difference

Input Impedance (DC) CLKIN = 10 MHz 500 590 kΩ

Bandwidth (−3 dB) CLKIN/256, CLKIN = 10 MHz 14 kHz

ADC Offset Error1, 2 ±25 mV

Gain Error External 2.5 V reference, IA = IB = IC = 500 mV dc ±9 % ideal

REFERENCE INPUT

REFIN/OUT Input Voltage Range 2.4 V + 8% 2.6 V

2.4 V − 8% 2.2 V

Input Impedance 3.3 kΩ

Input Capacitance 10 pF

ON-CHIP REFERENCE Nominal 2.4 V

Reference Error ±200 mV

Temperature Coefficient 25 ppm/°C

CLKIN (INPUT CLOCK FREQUENCY) All specifications for CLKIN of 10 MHz 10 MHz

LOGIC INPUTS3

SCF, S0, S1, and ABS

Input High Voltage, VINH V

DD = 5 V ± 5% 2.4 V

Input Low Voltage, VINL V

DD = 5 V ± 5% 0.8 V

Input Current, IIN Typically 10 nA, VIN = 0 V to VDD ±3 μA

Input Capacitance, CIN 10 pF

LOGIC OUTPUTS3

F1 and F2

Output High Voltage, VOH I

SOURCE = 10 mA, VDD = 5 V 4.5 V

Output Low Voltage, VOL I

SINK = 10 mA, VDD = 5 V 0.5 V

CF and REVP

Output High Voltage, VOH V

DD = 5 V, ISOURCE = 5 mA 4.5 V

Output Low Voltage, VOL V

DD = 5 V, ISINK = 5 mA 0.5 V

POWER SUPPLY For specified performance

VDD 5 V ± 5% 4.75 5.25 V

IDD 8.5 10 mA

1 See the Terminology section for explanation of specifications.

2 See the plots in the Typical Performance Characteristics section.

3 Sample tested during initial release and after any redesign or process changes that might affect this parameter.

ADE7752B

Rev. 0 | Page 4 of 24

TIMING CHARACTERISTICS

VDD = 5 V ± 5%, AGND = DGND = 0 V, on-chip reference, CLKIN = 10 MHz, TMIN to TMAX = −40°C to +85°C, unless otherwise noted.

Table 2.

Parameter1,2 Conditions Specification Unit

t1 3 F1 and F2 pulse width (logic high) 120 ms

t2 Output pulse period (see the Transfer Function section) See Figure 2 sec

t3 Time between F1 rising edge and F2 rising edge ½ t2 sec

t43, 4 CF pulse width (logic high) 90 ms

t55 CF pulse period (see the Transfer Function section) See Table 7 sec

t6 Minimum time between F1 and F2 pulse 4/CLKIN sec

1 Sample tested during initial release and after any redesign or process changes that might affect this parameter.

2 See Figure 2.

3 The pulse widths of F1, F2, and CF are not fixed for higher output frequencies (see the Frequency Outputs section).

4 CF is not synchronous to F1 or F2 frequency outputs.

5 The CF pulse is always 1 μs in the high frequency mode (see the Frequency Outputs section).

05905-002

Figure 2. Timing Diagram for Frequency Outputs

ADE7752B

Rev. 0 | Page 5 of 24

ABSOLUTE MAXIMUM RATINGS

TA = 25°C, unless otherwise noted.

Table 3.

Parameter Rating

VDD to AGND −0.3 V to +7 V

VDD to DGND −0.3 V to +7 V

Analog Input Voltage to AGND

VA P, V B P, V C P, V N , IA P, I A N , I B P, I B N , I C P,

and ICN

−6 V to +6 V

Reference Input Voltage to AGND −0.3 V to VDD + 0.3 V

Digital Input Voltage to DGND −0.3 V to VDD + 0.3 V

Digital Output Voltage to DGND −0.3 V to VDD + 0.3 V

Operating Temperature Range, Industrial −40°C to +85°C

Storage Temperature Range −65°C to +150°C

Junction Temperature 150°C

24-Lead SOIC, Power Dissipation 63 mW

θJA Thermal Impedance 55°C/W

Lead Temperature, Soldering

Vapor Phase (60 sec) 215°C

Infrared (15 sec) 220°C

Stresses above those listed under Absolute Maximum Ratings

may cause permanent damage to the device. This is a stress

rating only; functional operation of the device at these or any

other conditions above those indicated in the operational

section of this specification is not implied. Exposure to absolute

maximum rating conditions for extended periods may affect

device reliability.

ESD CAUTION

ADE7752B

Rev. 0 | Page 6 of 24

PIN CONFIGURATION AND FUNCTION DESCRIPTIONS

DGND

DD 3

REVP

IAP

IAN

IBP

IBN

ICP

CLKOUT

ICN

CLKIN

AGND

SCF

REF

IN/OUT 12

ABS

VCP

VAP

VBP

ADE7752B

TOP VIEW

(Not to Scale)

5905-004

Figure 3. Pin Configuration

Table 4. Pin Function Descriptions

Pin No. Mnemonic Description

1 CF Calibration Frequency Logic Output. The CF logic output gives instantaneous active power information.

This output is intended to be used for calibration purposes.

2 DGND This provides the ground reference for the digital circuitry in the ADE7752B, that is, multipliers, filters,

and digital-to-frequency converters. Because the digital return currents in the ADE7752B are small, it is

acceptable to connect this pin to the analog ground plane of the whole system.

3 VDD Power Supply. This pin provides the supply voltage for the digital circuitry in the ADE7752B. The supply

voltage should be maintained at 5 V ± 5% for specified operation. This pin should be decoupled to

DGND with a 10 μF capacitor in parallel with a 100 nF ceramic capacitor.

4 REVP This logic output goes logic high when negative power is detected on the sum of the three phase

powers. This output is not latched and resets when positive power is once again detected (see the

Negative Total Power Detection section).

5, 6;

7, 8;

9, 10

IAP, IAN;

IBP, IBN;

ICP, ICN

Analog Inputs for Current Channels. These channels are intended for use with current transducers and

are referenced in this document as current channels. These inputs are fully differential voltage inputs

with maximum differential input signal levels of ±0.5 V (see the Analog Inputs section). Both inputs

have internal ESD protection circuitry; in addition, an overvoltage of ±6 V can be sustained on these

inputs without risk of permanent damage.

11 AGND This pin provides the ground reference for the analog circuitry in the ADE7752B (ADCs and reference).

This pin should be tied to the analog ground plane or the quietest ground reference in the system. This

quiet ground reference should be used for all analog circuitry, such as antialiasing filters and current

and voltage transducers. To keep ground noise around the ADE7752B to a minimum, the quiet ground

plane should connect to the digital ground plane at only one point. It is acceptable to place the entire

device on the analog ground plane.

12 REFIN/OUT This pin provides access to the on-chip voltage reference. The on-chip reference has a nominal value of

2.4 V ± 8% and a typical temperature coefficient of 25 ppm/°C. An external reference source can also be

connected at this pin. In either case, this pin should be decoupled to AGND with a 1 μF ceramic

capacitor.

13, 14, 15,

VN, VCP, VBP, VAP Analog Inputs for the Voltage Channels. These channels are intended for use with voltage transducers

and are referenced in this document as voltage channels. These inputs are single-ended voltage inputs

with a maximum signal level of ±0.5 V with respect to VN for specified operation. All inputs have

internal ESD protection circuitry; in addition, an overvoltage of ±6 V can be sustained on these inputs

without risk of permanent damage.

17 ABS This logic input is used to select the method by which the three active energies from each phase are

summed. It selects between the arithmetical sum of the three energies (ABS logic high) or the sum of

the absolute values (ABS logic low). See the Mode Selection of the Sum of the Three Active Energies section.

18 SCF Select Calibration Frequency. This logic input is used to select the frequency on the calibration output

CF. Table 7 shows how the calibration frequencies are selected.

19 CLKIN Master Clock for the ADCs and Digital Signal Processing. An external clock can be provided at this logic

input. Alternatively, a parallel resonant AT crystal can be connected across CLKIN and CLKOUT to

provide a clock source for the ADE7752B. The clock frequency for the specified operation is 10 MHz.

Ceramic load capacitors between 22 pF and 33 pF should be used with the gate oscillator circuit. Refer

to the crystal manufacturer’s data sheet for the load capacitance requirements.

ADE7752B

Rev. 0 | Page 7 of 24

Pin No. Mnemonic Description

20 CLKOUT A crystal can be connected across this pin and CLKIN as described for Pin 19 to provide a clock source

for the ADE7752B. The CLKOUT pin can drive one CMOS load when an external clock is supplied at

CLKIN or when a crystal is used.

21, 22 S0, S1 These logic inputs are used to select one of four possible frequencies for the digital-to-frequency

conversion for design flexibility.

23, 24 F2, F1 Low Frequency Logic Outputs. F1 and F2 supply average active power information. These logic outputs

can be used to drive electromechanical counters and 2-phase stepper motors directly (see the Transfer

Function section).

ADE7752B

Rev. 0 | Page 8 of 24

TYPICAL PERFORMANCE CHARACTERISTICS

0.1 1 10 100

05905-007

% ERROR

CURRENT CHANNEL (% of Full Scale)

–0.5

–0.4

–0.3

–0.2

–0.1

0.1

0.2

0.3

0.4

0.5

PHASE B

PHASE A + B + C

PHASE C

PHASE A

Figure 4. Error As a Percent of Reading

with Internal Reference (Wye Connection)

0.1 1 10 100

05905-008

% ERROR

CURRENT CHANNEL (% of Full Scale)

–0.4

–0.2

0.2

0.4

0.6

0.8

1.0

+25°C, POWER FACTOR = 0.5

+85°C, POWER FACTOR = 0.5

+25°C, POWER FACTOR = 1

–40°C, POWER FACTOR = 0.5

Figure 5. Error As a Percent of Reading over Power Factor

with Internal Reference (Wye Connection)

0.1 1 10 100

05905-009

% ERROR

CURRENT CHANNEL (% of Full Scale)

–1.0

–0.8

–0.5

–0.4

–0.2

0.2

0.4

0.6

0.8

1.0

+85°C, POWER FACTOR = 1

+25°C, POWER FACTOR = 1

–40°C, POWER FACTOR = 1

Figure 6. Error As a Percent of Reading over Temperature

with Internal Reference (Wye Connection)

–0.5

–0.4

–0.3

–0.2

–0.1

0.1

0.2

0.3

0.4

0.5

0.1 1 10 100

05905-010

% ERROR

CURRENT CHANNEL (% of Full Scale)

+85°C, POWER FACTOR = 1

+25°C, POWER FACTOR = 1

–40°C, POWER FACTOR = 1

Figure 7. Error As a Percent of Reading over Temperature

with External Reference (Wye Connection)

–1.5

–1.0

–0.5

0.5

1.0

45 50 55 60 65

05905-011

% ERROR

LINE FREQUENCY (Hz)

POWER FACTOR = 0.5

POWER FACTOR = 1

Figure 8. Error As a Percent of Reading over Frequency

with an Internal Reference (Wye Connection)

0.1 1 10 100

05905-012

% ERROR

CURRENT CHANNEL (% of Full Scale)

–0.5

–0.4

–0.3

–0.2

–0.1

0.1

0.2

0.3

0.4

0.5

5.25V

4.75V

Figure 9. Error As a Percent of Reading over Power Supply

with Internal Reference (Wye Connection)

ADE7752B

Rev. 0 | Page 9 of 24

TERMINOLOGY

Measurement Error

The error associated with the energy measurement made by the

ADE7752B is defined by the following formula:

Percentage Error =

%100

⎟

⎠

⎞

⎜

⎝

⎛

yTrue Energ

yTrue Energ– ADE7762istered byEnergy Reg (1)

Error Between Channels

The high-pass filter (HPF) in the current channel has a phase

lead response. To offset this phase response and equalize the

phase response between channels, a phase correction network

is placed in the current channel. The phase correction network

ensures a phase match between the current channels and the

voltage channels to within ±0.1° over a range of 45 Hz to 65 Hz

and ±0.2° over a range of 40 Hz to 1 kHz (see Figure 21 and

Figure 22).

Power Supply Rejection (PSR)

This quantifies the ADE7752B measurement error as a

percentage of reading when the power supplies are varied.

For the ac PSR measurement, a reading at a nominal supply

(5 V) is taken. A 200 mV rms/100 Hz signal is then introduced

onto the supply and a second reading is obtained under the

same input signal levels. Any error introduced is expressed as a

percentage of reading. See the definition for Measurement Error.

For the dc PSR measurement, a reading at nominal supplies

(5 V) is taken. The supply is then varied ±5% and a second

reading is obtained with the same input signal levels. Any error

introduced is again expressed as a percentage of reading.

ADC Offset Error

This refers to the dc offset associated with the analog inputs to

the ADCs. It means that with the analog inputs connected to

AGND, the ADCs still see an analog input signal offset.

However, because the HPF is always present, the offset is

removed from the current channel and the power calculation is

not affected by this offset.

Gain Error

The gain error of the ADE7752B is defined as the difference

between the measured output frequency (minus the offset) and

the ideal output frequency. The difference is expressed as a

percentage of the ideal frequency. The ideal frequency is

obtained from the ADE7752B transfer function (see the

Transfer Function section).

ADE7752B

Rev. 0 | Page 10 of 24

TEST CIRCUIT

ABS

REF

IN/OUT

33nF

100nF

33nF

1kΩ

820Ω

1kΩ

10µF

AGND DGND

317

CLKOUT

CLKIN

SCF

10MHz

22pF

ADE7752B

FREQUENCY

COUNTER

IAP

IAN

IBP

IBN

ICP

ICN

SAME AS

IAP, IAN

SAME AS

IAP, IAN

SAME AS VAP

REVP 0.1µF 10µF

VAP

VBP

VCP

33nF

1kΩ

1MΩ

220

33nF

SAME AS VAP

LOAD

05905-015

Figure 10. Test Circuit for Performance Curves

ADE7752B

Rev. 0 | Page 11 of 24

THEORY OF OPERATION

The six signals from the current and voltage transducers are

digitized with ADCs. These ADCs are 16-bit, second-order

∑-Δ with an oversampling rate of 833 kHz. This analog input

structure greatly simplifies transducer interface by providing a

wide dynamic range and bipolar input for direct connection to

the transducer. High-pass filters in the current channels remove

the dc component from the current signals. This eliminates any

inaccuracies in the active power calculation due to offsets in the

voltage or current signals (see the HPF and Offset Effects section).

The active power calculation is derived from the instantaneous

power signal. The instantaneous power signal is generated by a

direct multiplication of the current and voltage signals of each

phase. To extract the active power component, the dc compo-

nent, the instantaneous power signal is low-pass filtered on

each phase. Figure 11 illustrates the instantaneous active power

signal and shows how the active power information can be

extracted by low-pass filtering the instantaneous power signal.

This method is used to extract the active power information

on each phase of the polyphase system. The total active power

information is then obtained by adding the individual phase

active power. This scheme correctly calculates active power

for nonsinusoidal current and voltage waveforms at all power

factors. All signal processing is carried out in the digital domain

for superior stability over temperature and time.

The low frequency output of the ADE7752B is generated by

accumulating the total active power information. This low

frequency inherently means a long accumulation time between

output pulses. The output frequency is therefore proportional to

the average active power. This average active power information

can, in turn, be accumulated (for example, by a counter) to

generate active energy information. Because of its high output

frequency and, therefore, shorter integration time, the CF

output is proportional to the instantaneous active power. This

pulse is useful for system calibration purposes that take place

under steady load conditions.

POWER FACTOR CONSIDERATIONS

Low-pass filtering, the method used to extract the active power

information from the individual instantaneous power signal, is

still valid when the voltage and current signals of each phase are

not in phase. Figure 12 displays the unity power factor condi-

tion and a displacement power factor (DPF) = 0.5, that is,

current signal lagging the voltage by 60°, for one phase of the

polyphase. Assuming that the voltage and current waveforms

are sinusoidal, the active power component of the instantaneous

power signal (the dc term) is given by

()

°×

⎟

⎠

⎞

⎜

⎝

⎛×60cos

1V (2)

This is the correct active power calculation.

TIME

IAP

IAN

VAP

HPF

LPF

IBP

IBN

VBP

ICP

ICN

VCP

INSTANTANEOUS

ACTIVE POWER SIGNAL

INSTANTANEOUS

POWER SIGNAL - p(t) VA × IA + VB × IB +

VC × IC

ABS

|X|

LPF

|X|

p(t) = i(t) × v(t)

WHERE:

{1+ cos (2ωt)}

v(t) = V × cos (ωt)

i(t) = I × cos (ωt)

p(t) = V × I

V×I

V×I V × I

MULTIPLIER

HPF

ADC

ADC INSTANTANEOUS

TOTAL POWER

SIGNAL

DIGITAL-TO-FREQUENCY

05905-016

Figure 11. Signal Processing Block Diagram

ADE7752B

Rev. 0 | Page 12 of 24

INSTANTANEOUS

ACTIVE POWER SIGNAL

INSTANTANEOU

POWER SIGNAL

INSTANTANEOUS

ACTIVE POWER SIGNAL

INSTANTANEOUS

POWER SIGNAL

V× I

2× cos(60°)

V× I

60° CURRENT

CURRENT

VOLTAGE

05905-017

Figure 12. DC Component of Instantaneous Power Signal

NONSINUSOIDAL VOLTAGE AND CURRENT

The active power calculation method also holds true for non-

sinusoidal current and voltage waveforms. All voltage and

current waveforms in practical applications have some

harmonic content. Using the Fourier transform, instantaneous

voltage and current waveforms can be expressed in terms of

their harmonic content

()

OαtnVVtv +ω××+= ∑

∞

sin2)(

(3)

where:

v(t) is the instantaneous voltage.

VO is the average value.

Vn is the rms value of voltage harmonic n.

α n is the phase angle of the voltage harmonic.

()

OtnIIti βω××+= ∑

∞

sin2

(4)

where:

i(t) is the instantaneous current.

IO is the dc component.

In is the rms value of current harmonic n.

βn is the phase angle of the current harmonic.

Using Equation 3 and Equation 4, the active power, P, can be

expressed in terms of its fundamental active power (P1) and

harmonic active power (PH).

P = P1 + PH

where:

111

1111

φcos

β−α=

P (5)

IVP

β−α=

×= ∑

∞

φcos

1 (6)

As can be seen from Equation 6, a harmonic active power

component is generated for every harmonic, provided that

harmonic is present in both the voltage and current waveforms.

The power factor calculation has been shown to be accurate in

the case of a pure sinusoid. Therefore, the harmonic active

power also correctly accounts for power factor because harmonics

are made up of a series of pure sinusoids. A limiting factor on

harmonic measurement is the bandwidth. On the ADE7752B,

the bandwidth of the active power measurement is 14 kHz with

a master clock frequency of 10 MHz.

ADE7752B

Rev. 0 | Page 13 of 24

ANALOG INPUTS

CURRENT CHANNELS

The voltage outputs from the current transducers are connected

to the ADE7752B current channels, which are fully differential

voltage inputs. IAP, IBP, and ICP are the positive inputs for IAN,

IBN, and ICN, respectively.

The maximum peak differential signal on the current channel

should be less than ±500 mV (353 mV rms for a pure sinusoidal

signal) for the specified operation.

DIFFERENTIAL INPUT

±500mV MAX PEAK

+500mV

AGND

IAP

–500mV

COMMON-MODE

±25mV MAX

IAN

IAP–IAN

05905-018

Figure 13. Maximum Signal Levels, Current Channel

The maximum signal levels on IAP and IAN are shown in

Figure 13. The maximum differential voltage between IAP

and IAN is ±500 mV. The differential voltage signal on the

inputs must be referenced to a common mode, for example,

AGND. The maximum common-mode signal shown in

Figure 13 is ±25 mV.

VOLTAGE CHANNELS

The output of the line voltage transducer is connected to the

voltage inputs of the ADE7752B. Voltage channels are pseudo-

differential voltage inputs. VAP, VBP, and VCP are the positive

inputs with respect to VN.

The maximum peak differential signal on the voltage channel is

±500 mV (353 mV rms for a pure sinusoidal signal) for speci-

fied operation.

Figure 14 illustrates the maximum signal levels that can be

connected to the ADE7752B voltage channels.

DIFFERENTIAL INPUT

±500mV MAX PEAK

+500mV

AGND

VCM

VAP

–500mV

COMMON-MODE

±25mV MAX

AP–VN

5905-019

Figure 14. Maximum Signal Levels, Voltage Channel

Voltage channels must be driven from a common-mode voltage,

that is, the differential voltage signal on the input must be refer-

enced to a common mode (usually AGND). The analog inputs

of the ADE7752B can be driven with common-mode voltages of

up to 25 mV with respect to AGND. However, best results are

achieved using a common mode equal to AGND.

ADE7752B

Rev. 0 | Page 14 of 24

TYPICAL CONNECTION DIAGRAMS

CURRENT CHANNEL CONNECTION

Figure 15 shows a typical connection diagram for the current

channel (IA). A current transformer (CT) is the current trans-

ducer selected for this example. Notice that the common-mode

voltage for the current channel is AGND and is derived by

center-tapping the burden resistor to AGND. This provides the

complementary analog input signals for IAP and IAN. The CT

turns ratio and burden resistor Rb are selected to give a peak

differential voltage of ±500 mV at maximum load.

In theory, it is better to center tap Rb; however, this requires

very careful attention to the layout and matching of the resistors

to ensure that the channels have the same resistance. A single

resistor may be more practical and is a valid design choice.

IAP

±500mV

NEUTRALPHASE

IAN

05905-020

Figure 15. Typical Connection for Current Channels

VOLTAGE CHANNEL CONNECTION

Figure 16 shows two typical connections for the voltage channel.

The first option uses a potential transformer (PT) to provide

complete isolation from the main voltage. In the second option,

the ADE7752B is biased around the neutral wire, and a resistor

divider is used to provide a voltage signal proportional to the

line voltage. Adjusting the ratio of Ra, Rb, and VR is a convenient

way of carrying out a gain calibration on the meter. VR can be

implemented using either a potentiometer or a binary weighted

series of resistors. Either configuration works, however, the

potentiometer is subject to noise over time. Two fixed value

resistors can be used in place of VR to minimize the noise.

±500mV

Ra*

Rb*

VR*

VAP

AGND

NEUTRALPHASE

VAP

NEUTRALPHASE

*Ra >> Rf + VR; *Rb + VR = Rf

±500mV

05905-021

Figure 16. Typical Connections for Voltage Channels

METER CONNECTIONS

In 3-phase service, two main power distribution services exist:

3-phase, 4-wire or 3-phase, 3-wire. The additional wire in the

3-phase, 4-wire arrangement is the neutral wire. The voltage

lines have a phase difference of ±120° (±2π/3 radians) between

each other (see Equation 7).

()

(

)

tVtV l

AA ω××= cos2

()

⎟

⎠

⎞

⎜

⎝

⎛π

+ω××= 3

cos2 tVtV l

BB (7)

()

⎟

⎠

⎞

⎜

⎝

⎛π

+ω××= 3

cos2 tVtV l

where VA, VB, and VC represent the voltage rms values of the

different phases.

The current inputs are represented by

()

(

)

AA tItI φcos2 +ω×=

()

⎟

⎠

⎞

⎜

⎝

⎛+

+ω×= B

BB tItI φ

cos2 (8)

()

⎟

⎠

⎞

⎜

⎝

⎛+

+ω×= C

CC tItI φ

cos2

where:

IA, IB, and IC represent the rms value of the current of each phase.

φA, φB, and φC represent the phase difference of the current and

voltage channel of each phase.

The instantaneous powers can then be calculated as follows:

PA(t) = VA(t) × IA(t)

PB(t) = VB(t) × IB(t)

PC(t) = VC(t) × IC(t)

Then:

(

)

(

)

(

)

AAAAAA tIVIVtP

××−

2coscos

(

)

tPB

()

⎟

⎠

⎞

⎜

⎝

⎛φ+

+ω××−φ×× B

BBBBB tIVIV 3

2coscos (9)

()

⎟

⎠

⎞

⎜

⎝

⎛φ+

+ω××−φ××= C

CCCCCC tIVIVtP 3

2coscos

As shown in Equation 9, the active power calculation per phase

is made when current and voltage inputs of one phase are

connected to the same channel (A, B, or C). Then the

summation of each individual active power calculation gives the

total active power information, P(t) = PA(t) + PB(t) + PC(t).

ADE7752B

Rev. 0 | Page 15 of 24

Figure 17 shows the connections of the ADE7752B analog

inputs with the power lines in a 3-phase, 3-wire delta service.

Rb*

IAP

IAN

SOURCE

Rb*

Ra*

Rb*

VR*

Rf Cf

Ra*

VR*

LOAD

PHASE A

PHASE B

PHASE C

Rb*

VAP

VBP

ANTIALIASING

FILTERS

IBN

IBP

*Ra >> Rf + VR; *Rb + VR = Rf

ANTIALIASING

FILTERS

05905-022

Figure 17. 3-Phase, 3-Wire Meter Connection with ADE7752B

Note that only two current inputs and two voltage inputs of the

ADE7752B are used in this case. The active power calculated by

the ADE7752B does not depend on the selected channels.

Figure 18 shows the connections of the ADE7752B analog

inputs with the power lines in a 3-phase, 4-wire Wye service.

SOURCE

ICP

ICN

LOAD

IBP

IBN

PHASE A

PHASE B

PHASE C

Rb*

Ra*

VR*

VAP

Rb*

ANTIALIASING

FILTERS

IAP

IAN

Rb*

Ra*

VR*

VCP

Rb*

Ra*

VR*

VBP

Rb*

*Ra >> Rf + VR;

Rb + VR = Rf

ANTIALIASING

FILTERS

ANTIALIASING

FILTERS

5905-023

Figure 18. 3-Phase, 4-Wire Meter Connection with ADE7752B

ADE7752B

Rev. 0 | Page 16 of 24

POWER SUPPLY MONITOR

The ADE7752B contains an on-chip power supply monitor. The

power supply (VDD) is monitored continuously. At power-up,

when the supply is less than 4 V ± 2% and VREF is less than 1.9 V

(typical), the outputs of the ADE7752B are inactive and the data

path is held in reset. Once VDD is greater than 4 V ± 2% and

VREF is greater than 1.9 V (typical), the chip is active and energy

accumulation begins. At power-down, when VDD falls below 4 V

or VREF falls below 1.9 V (typical), the data path is again held in

reset. This implementation ensures correct device operation at

power-up and at power-down. The power supply monitor has

built-in hysteresis and filtering. This gives a high degree of

immunity to false triggering due to noisy supplies.

The power supply and decoupling for the part should be such

that the ripple at VDD does not exceed ±5% as specified for

normal operation.

REF

INTERNAL

RESET ACTIVE INACTIVE

2.4V

1.9V

INACTIVE

05905-024

Figure 19. On-Chip Power Supply Monitor

ADE7752B

Rev. 0 | Page 17 of 24

HPF AND OFFSET EFFECTS

Figure 20 shows the effect of offsets on the active power

calculation. An offset on the current channel and the voltage

channel contributes a dc component after multiplication, as

shown in Figure 20. Because this dc component is extracted by

the LPF and is used to generate the active power information

for each phase, the offsets can contribute a constant error to the

total active power calculation. The HPF in the current channels

avoids this problem easily. By removing the offset from at least

one channel, no error component can be generated at dc by the

multiplication. Error terms at cos(ωt) are removed by the LPF

and the digital-to-frequency conversion (see the Digital-to-

Frequency Conversion section).

(

)

{

}

(

)

{

}

() ()

()

tVItIVIV

ItIVtV

OSOSOSOS

OSOS

ω×

ω×+ω×+×+

=+ω×+ω

2cos

coscos

(10)

×I

× I

× V

2ω

FREQUENCY (RAD/sec)

V× I

DC COMPONENT (INCLUDING ERROR TERM)

IS EXTRACTED BY THE LPF FOR REAL

POWER CALCULATION

05905-026

Figure 20. Effect of Channel Offset on the Active Power Calculation

The HPF in the current channels has an associated phase response

that is compensated for on-chip. Figure 21 and Figure 22 show the

phase error between channels with the compensation network.

The ADE7752B is phase compensated up to 1 kHz as shown. This

ensures correct active harmonic power calculation even at low

power factors.

FREQUENCY (Hz)

0.07

0.06

–0.01 0 1000200 400 600 800

PHASE (Degrees)

0.03

0.02

0.01

0.05

0.04

100 300 500 700 900

05905-031

Figure 21. Phase Error Between Channels (0 Hz to 1 kHz)

FREQUENCY (Hz)

0.010

0.008

–0.004 40 7045 50

PHASE (Degrees)

0.002

–0.002

0.006

0.004

55 60 65

05905-032

Figure 22. Phase Error Between Channels (40 Hz to 70 Hz)

ADE7752B

Rev. 0 | Page 18 of 24

DIGITAL-TO-FREQUENCY CONVERSION

After multiplication, the digital output of the low-pass filter

contains the active power information of each phase. However,

because this LPF is not an ideal brick wall filter implementation,

the output signal also contains attenuated components at the line

frequency and its harmonics, that is, cos(hωt), where h = 1, 2, 3 …

The magnitude response of the filter is given by

()

⎭

⎬

⎫

⎩

⎨

⎧

fH (11)

where the −3 dB cutoff frequency of the low-pass filter is 8 Hz.

For a line frequency of 50 Hz, this gives an attenuation of the 2ω

(100 Hz) component of approximately −22 dB. The dominating

harmonic is twice the line frequency, that is, cos(2ωt), due to

the instantaneous power signal. Figure 23 shows the instantane-

ous active power signal at the output of the CF, which still contains

a significant amount of instantaneous power information,

cos(2ωt).

This signal is then passed to the digital-to-frequency converter

where it is integrated (accumulated) over time to produce an

output frequency. This accumulation of the signal suppresses or

averages out any nondc component in the instantaneous active

power signal.

The average value of a sinusoidal signal is zero. Thus, the

frequency generated by the ADE7752B is proportional to the

average active power. Figure 23 shows the digital-to-frequency

conversion for steady load conditions, that is, constant voltage

and current.

The frequency output CF varies over time, even under steady load

conditions (see Figure 23). This frequency variation is primarily

due to the cos(2ωt) components in the instantaneous active power

signal. The output frequency on CF can be up to 160× higher than

the frequency on F1 and F2. The higher output frequency is

generated by accumulating the instantaneous active power signal

over a much shorter time, while converting it to a frequency. This

shorter accumulation period means less averaging of the cos(2ωt)

component. Therefore, some of this instantaneous power signal

passes through the digital-to-frequency conversion.

Where CF is used for calibration purposes, the frequency counter

should average the frequency to remove the ripple and obtain a

stable frequency. If CF is being used to measure energy, for

example, in a microprocessor-based application, the CF output

should also be averaged to calculate power. Because the outputs F1

and F2 operate at a much lower frequency, significant averaging of

the instantaneous active power signal is carried out. The result is a

greatly attenuated sinusoidal content and a virtually ripple-free

frequency output on F1 and F2, which are used to measure energy

in a stepper motor-based meter.

LPF TO EXTRACT

REAL POWER

(DC TERM)

MULTIPLIER

LPF

MULTIPLIER

LPF

MULTIPLIER

LPF

DIGITAL-TO-

FREQUENCY

DIGITAL-TO-

FREQUENCY

TIME

ω2ω

FREQUENCY (RAD/sec)

V × I

INSTANTANEOUS REAL POWER SIGNAL

(FREQUENCY DOMAIN)

|X|

ABS

TIME

cos(2ωt)

ATTENUATED BY LPF

5905-029

Figure 23. Active Power-to-Frequency Conversion

ADE7752B

Rev. 0 | Page 19 of 24

ACCUMULATION OF 3-PHASE POWER

Power Measurement Considerations

Calculating and displaying power information always have some

associated ripple that depends on the integration period used in the

MCU to determine average power as well as the load. For example,

at light loads, the output frequency can be 10 Hz. With an integra-

tion period of 2 seconds, only about 20 pulses are counted. The

possibility of missing one pulse always exists because the

ADE7752B output frequency is running asynchronously to the

MCU timer. This results in a 1-in-20 or 5% error in the power

measurement. To remedy this, an appropriate integration time

should be considered to achieve the desired accuracy.

Mode Selection of the Sum of the Three Active Energies

The ADE7752B can be configured to execute the arithmetic

sum of the three active energies, Wh = WhΦA + WhΦB + WhΦC,

or the sum of the absolute value of these energies, Wh = |WhΦA|

+ |WhΦB| + |WhΦC|. The selection between the two modes can

be made by setting the ABS pin. Logic high and logic low

applied on the ABS pin correspond to the arithmetic sum and

the sum of absolute values, respectively.

When the sum of the absolute values is selected, the active

energy from each phase is always counted positive in the total

active energy. It is particularly useful in 3-phase, 4-wire installa-

tion where the sign of the active power should always be the

same. If the meter is misconnected to the power lines, that is, if

CT is connected in the wrong direction, the total active energy

recorded without this solution can be reduced by two-thirds.

The sum of the absolute values assures that the active energy

recorded represents the actual active energy delivered. In this

mode, the reverse power pin still detects when the arithmetic

sum of the active powers is negative, but energy continues to

accumulate regardless of the sign.

Negative Total Power Detection

The ADE7752B detects when total power, calculated as the

arithmetic sum of the three phases, is negative. This detection

is independent of the mode of sum of the three powers (arithmetic

or absolute). This mechanism can detect an incorrect connec-

tion of the meter or generation of negative active energy. When

the sum of the powers of the three phases is negative, the REVP

pin output goes active high. When the sum of the powers of the

three phases is positive, the REVP pin output is reset to low.

The REVP pin output changes state at the same time as a pulse

is issued on CF. If the sum of the powers of the three phases is

negative, then the REVP pin output stays high until the sum is

positive or all three phases are below the no-load threshold.

ADE7752B

Rev. 0 | Page 20 of 24

TRANSFER FUNCTION

FREQUENCY OUTPUTS F1 AND F2

The ADE7752B calculates the product of six voltage signals

(on current channel and voltage channel) and then low-pass

filters this product to extract active power information. This

active power information is then converted to a frequency.

The frequency information is output on F1 and F2 in the form

of active high pulses. The pulse rate at these outputs is relatively

low, for example, 2.09 Hz maximum for ac signals with SCF =

S0 = 0; S1 = 1 (see Table 6). This means that the frequency at

these outputs is generated from active power information

accumulated over a relatively long period. The result is an

output frequency that is proportional to the average active

power. The averaging of the active power signal is implicit to

the digital-to-frequency conversion. The output frequency or

pulse rate is related to the input voltage signals by the following

equation:

(

)

181.6

REF

7to1

CCN

BBN

AAN

fIVIVIV

Freq ××+×+××

=(12)

where:

Freq is the output frequency on F1 and F2 (Hz).

VAN, VBN, and VCN are the differential rms voltage signals on

voltage channels (V).

IA, IB, and IC are the differential rms voltage signals on current

channels (V).

VREF is the reference voltage (2.4 V ± 8%) (V).

f1 to 7 is one of seven possible frequencies selected by using the

logic inputs SCF, S0, and S1 (see Table 5).

Table 5. f1 to 7 Frequency Selection1

SCF S1 S0 f1 to 7 (Hz)

0 0 0 2.24

1 0 0 4.49

0 0 1 1.12

1 0 1 4.49

0 1 0 5.09

1 1 0 1.12

0 1 1 0.56

1 1 1 0.56

1 f1 to 7 is a fraction of the master clock and therefore varies if the specified

CLKIN frequency is altered.

Example 1

In this example, with ac voltages of ±500 mV peak applied to

the voltage channels and current channels, the expected output

frequency is calculated as follows:

()

valuereferencenominalV4.2

rmsV

5.0

acpeakmV500

1,Hz56.0

=====

REF

ICIBIAVVV

S1S0SCFf 7to1

(13)

Note that if the on-chip reference is used, actual output fre-

quencies can vary from device to device due to reference

tolerance of ±8%.

Hz230.0

4.222

58.05.05.0313.6

32=

××

×=Freq (14)

As can be seen from these two example calculations, the maximum

output frequency for ac inputs is always half of that for dc input

signals. The maximum frequency also depends on the number

of phases connected to the ADE7752B. In a 3-phase, 3-wire delta

service, the maximum output frequency is different from the maxi-

mum output frequency in a 3-phase, 4-wire Wye service. The

reason is that there are only two phases connected to the analog

inputs, but also that in a delta service, the current channel input

and voltage channel input of the same phase are not in phase in

normal operation.

ADE7752B

Rev. 0 | Page 21 of 24

Example 2

In this example, the ADE7752B is connected to a 3-phase,

3-wire delta service as shown in Figure 17. The total active

energy calculation processed in the ADE7752B can be

expressed as

Total Active Power = (VA – VC) × IA + (VB – VC) × IB

where:

VA, VB, and VC represent the voltage on Phase A, Phase B, and

Phase C, respectively.

IA and IB represent the current on Phase A and Phase B,

respectively.

With respect to the voltage and current inputs in Equation 7

and Equation 8, the total active power (P) is

()

(

)

(

)

(

)

()

⎟

⎠

⎞

⎜

⎝

⎛π

+ω××

⎟

⎠

⎞

⎜

⎝

⎛⎟

⎠

⎞

⎜

⎝

⎛π

+ω××−

⎟

⎠

⎞

⎜

⎝

⎛π

+ω××

⎟

⎠

⎞

⎜

⎝

⎛⎟

⎠

⎞

⎜

⎝

⎛π

+ω××−ω××=

−×−+−−=

cos2

cos2cos2

tVvt

tVtVP

IIVVIIVVP

BNBP

ANAPCA

(15)

For simplification, assume that ΦA = ΦB = ΦC = 0 and

VA = VB = VC = V. The preceding equation becomes

()

⎟

⎠

⎞

⎜

⎝

⎛π

+ω×π+ω×

⎟

⎠

⎞

⎜

⎝

⎛π

×××

+ω×

⎟

⎠

⎞

⎜

⎝

⎛π

+ω×

⎟

⎠

⎞

⎜

⎝

⎛π

×××=

cossin

sin2

cos

sin

sin2

ttIV

ttIVP

(16)

P then becomes

⎟

⎠

⎞

⎜

⎝

⎛⎟

⎠

⎞

⎜

⎝

⎛π

+ω+

⎟

⎠

⎞

⎜

⎝

⎛π

××

⎟

⎠

⎞

⎜

⎝

⎛⎟

⎠

⎞

⎜

⎝

⎛π

+ω+

⎟

⎠

⎞

⎜

⎝

⎛π

××=

2sin

sin

2sin

sin

tIV

tIVP

BBN

AAN

(17)

where:

VAN = V × sin(2π/3)

VBN = V × sin(π/3)

As the LPF on each channel eliminates the 2ωl component of

the equation, the active power measured by the ADE7752B is

3××+××= BBN

AAN IVIVP (18)

If full-scale ac voltage of ±500 mV peak is applied to the voltage

channels and current channels, the expected output frequency

is calculated as follows:

valuereferencenominal V4.2

rmsV

5.0

acpeakVm500

1,Hz56.0

======

====

REF

CCN

7to1

IIIVV

S1S0SCFf

(19)

Note that if the on-chip reference is used, actual output

frequencies can vary from device to device due to a reference

tolerance of ±8%.

Hz133.0

4.222

56.05.05.0313.6

22=×

××

×××

×=Freq (20)

Table 6 shows a complete listing of all maximum output

frequencies when using all three channel inputs.

Table 6. Maximum Output Frequency on F1 and F2

SCF S1 S0 Maximum Frequency for AC Inputs (Hz)

0 0 0 0.92

1 0 1 1.84

0 0 1 0.46

1 0 1 1.84

0 1 0 2.09

1 1 0 0.46

0 1 1 0.23

1 1 1 0.23

FREQUENCY OUTPUT CF

The pulse output calibration frequency (CF) is intended for use

during calibration. The output pulse rate on CF can be up to

64× the pulse rate on F1 and F2. Table 7 shows how the two

frequencies are related, depending on the states of the logic

inputs S0, S1, and SCF. Because of its relatively high pulse rate,

the frequency at this logic output is proportional to the instantane-

ous active power. As is the case with F1 and F2, the frequency is

derived from the output of the low-pass filter after multiplication.

However, because the output frequency is high, this active

power information is accumulated over a much shorter time.

Thus, less averaging is carried out in the digital-to-frequency

conversion. The CF output is much more responsive to power

fluctuations with much less averaging of the active power signal

(see Figure 11).

Table 7. Maximum Output Frequency on CF

SCF S1 S0 f1 to 7 (Hz) CF Maximum for AC Signals (Hz)

0 0 0 2.24 16 × F1, F2 = 14.76

1 0 0 4.49 8 × F1, F2 = 14.76

0 0 1 1.12 32 × F1, F2 = 14.76

1 0 1 4.49 16 × F1, F2 = 29.51

0 1 0 5.09 160 × F1, F2 = 334

1 1 0 1.12 16 × F1, F2 = 7.38

0 1 1 0.56 32 × F1, F2 = 7.38

1 1 1 0.56 16 × F1, F2 = 3.69

ADE7752B

Rev. 0 | Page 22 of 24

SELECTING A FREQUENCY FOR AN ENERGY METER APPLICATION

As shown in Table 5, the user can select one of seven frequencies.

This frequency selection determines the maximum frequency

on F1 and F2. These outputs are intended to be used to drive

the energy register (electromechanical or other). Because seven

different output frequencies can be selected, the available

frequency selection has been optimized for a 3-phase, 4-wire

service with a meter constant of 100 imp/kWhr and a maxi-

mum current of between 10 A and 100 A. Table 8 shows the

output frequency for several maximum currents (IMAX) with a

line voltage of 220 V (phase neutral). In all cases, the meter

constant is 100 imp/kWhr.

Table 8. F1 and F2 Frequency at 100 imp/kWhr

IMAX (A) F1 and F2 (Hz)

10 0.18

25 0.46

40 0.73

60 1.10

80 1.47

100 1.83

The f1 to 7 frequencies allow complete coverage of this range of

output frequencies on F1 and F2. When designing an energy

meter, the nominal design voltage on the voltage channels

should be set to half scale to allow for calibration of the meter

constant. The current channel should also be no more than half

scale when the meter sees maximum load. This allows overcurrent

signals and signals with high crest factors to be accommodated.

Table 9 shows the output frequency on F1 and F2 when all six

analog inputs are half scale.

Table 9. F1 and F2 Frequency with Half-Scale AC Inputs

SCF S1 S0 f1 to 7 (Hz)

Frequency on F1 and F2

(Half-Scale AC Inputs) (Hz)

0 0 0 2.24 0.23

1 0 0 4.49 0.46

0 0 1 1.12 0.12

1 0 1 4.49 0.46

0 1 0 5.09 0.52

1 1 0 1.12 0.12

0 1 1 0.56 0.06

1 1 1 0.56 0.06

When selecting a suitable f1 to 7 frequency for a meter design, the

frequency output at IMAX (maximum load) with a 100 imp/kWhr

meter constant should be compared with Column 5 of Table 9.

The frequency that is closest in Table 9 determines the best

choice of frequency (f1 to 7). For example, if a 3-phase, 4-wire

Wye meter with a 25 A maximum current is being designed,

the output frequency on F1 and F2 with a 100 imp/kWhr meter

constant is 0.46 Hz at 25 A and 220 V (see Table 8). Looking at

Table 9, the closest frequency to 0.46 Hz in Column 5 is 0.46 Hz.

Therefore, f1 to 7 = 4.49 Hz is selected for this design.

FREQUENCY OUTPUTS

Figure 2 shows a timing diagram for the various frequency

outputs. The outputs F1 and F2 are the low frequency outputs

that can be used to directly drive a stepper motor or electro-

mechanical impulse counter. The F1 and F2 outputs provide

two alternating high going pulses. The pulse width (t1) is set at

120 ms, and the time between the rising edges of F1 and F2 (t3)

is approximately half the period of F1 (t2). If, however, the

period of F1 and F2 falls below 550 ms (1.81 Hz), the pulse

width of F1 and F2 is set to half of their period. The maximum

output frequencies for F1 and F2 are shown in Table 6.

The high frequency CF output is intended to be used for

communications and calibration purposes. CF produces a

90 ms-wide active high pulse (t4) at a frequency proportional

to active power. The CF output frequencies are given in Table 7.

As in the case of F1 and F2, if the period of CF (t5) falls below

190 ms, the CF pulse width is set to half the period. For example,

if the CF frequency is 20 Hz, the CF pulse width is 25 ms.

ADE7752B

Rev. 0 | Page 23 of 24

NO-LOAD THRESHOLD

The ADE7752B includes an innovative no-load threshold detection

scheme that detects if a current input, when multiplied with any

of the three voltages inputs, cannot create power larger than a no-

load threshold. This threshold represents 0.0075% of the full-

scale output frequency.

For example, if the A, B and C voltage phases are 50% of full-

scale input and 120° apart, and Current Phase A is 10% of full

scale with a PF = 0, this detection scheme detects that VA × IA is

below the no-load threshold but that VB × IA and VC × IA are not.

Therefore, the ADE7752B does not detect a no-load threshold

for VA × IA and lets this phase contribute to the total power.

However, in the same voltage conditions, if current Phase A is

0.0075% of full scale with a PF = 1, this detection scheme detects

that VA × IA is below the no-load threshold and because VB × IA

and VC × IA are as well, VA × IA is detected as below the no-load

threshold and its contribution to the total power is stopped.

The no-load threshold is given as 0.0075% of the full-scale output

frequency for each of the f1 to 7 frequencies (see Table 10). For

example, for an energy meter with a 100 imp/kWhr meter

constant using f1 to 7 (4.49 Hz), the minimum output frequency

at F1 or F2 is 1.38 × 10−4 Hz. This is 2.21 × 10−3 Hz at CF

(16 × F1 Hz). In this example, the no-load threshold is equiva-

lent to 4.8 W of load, or a start-up current of 20.7 mA at 240 V.

Table 10. CF, F1, and F2 Minimum Frequency at No-Load

Threshold

SCF S1 S0 F1, F2 Minimum (Hz) CF Minimum (Hz)

0 0 0 6.92E − 05 1.11E − 03

1 0 0 1.38E − 04 1.11E − 03

0 0 1 3.46E − 05 1.11E − 03

1 0 1 1.38E − 04 2.21E − 03

0 1 0 1.57E − 04 2.51E − 02

1 1 0 3.46E − 05 5.53E − 04

0 1 1 1.73E − 05 5.53E − 04

1 1 1 1.753 − 05 2.77E − 04

ADE7752B

Rev. 0 | Page 24 of 24

OUTLINE DIMENSIONS

COMPLIANT TO JEDEC STANDARDS MS-013-AD

CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS

(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR

REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.

15.60 (0.6142)

15.20 (0.5984)

0.30 (0.0118)

0.10 (0.0039)

2.65 (0.1043)

2.35 (0.0925)

10.65 (0.4193)

10.00 (0.3937)

7.60 (0.2992)

7.40 (0.2913)

0.75 (0.0295)

0.25 (0.0098)

45°

1.27 (0.0500)

0.40 (0.0157)

COPLANARITY

0.10 0.33 (0.0130)

0.20 (0.0079)

0.51 (0.0201)

0.31 (0.0122)

SEATING

PLANE

8°

0°

24 13

1.27 (0.0500)

BSC

060706-A

Figure 24. 24-Lead Standard Small Outline Package [SOIC_W]

Wide Body

(RW-24)

Dimensions shown in millimeters and (inches)

ORDERING GUIDE

Model Temperature Range Package Description Package Option

ADE7752BARWZ1 −40°C to +85°C 24-Lead Standard Small Outline Package [SOIC_W] RW-24

ADE7752BARWZ-RL1 −40°C to +85°C 24-Lead [SOIC_W], on 13” Reel RW-24

1 Z = RoHS Compliant Part.

registered trademarks are the property of their respective owners.

D05905-0-8/07(0)