www.fairchildsemi.com
Rev. 1.5
©2001 Fairchild S e m icon du ctor Corporation
Features
• 85% efficiency at 50m A
• Start-up voltages as low as 900mV
• ±2.5% accurate outputs
• Complete switcher design with only 3 external
components
• 50, 1 00 and 180kHz s witching fre quency versi ons
available
• Shutdown to 0.5µA Iq
• External transistor option allows several hundred
milliamp switcher design
Applications
• Cellular Phones, Pagers
• Por ta ble Cam era s and Video Recorders
• Palmtops and PDAs
Description
100mA boost converter in 5-lead SOT-89 package using both
PFM and PWM conversion techniques. In normal operation
the ILC6 380 r uns in PW M mode running at o ne of three fixed
frequencies. At lig ht loads the ILC63 80 senses when the duty
cycle drops to approximately 10%, and automatically
switches into a power-saving PFM switching technique. This
maintains high efficiencies both at full load and in system
sleep conditions.
Only 3 external components are needed to complete the
switcher design, and standard voltage options of 2.5, 3.3, and
5.0V at ±2.5% accuracy feature on-chip phase compensation
and soft-start design.
ILC6381 drives an external transistor for higher current
switcher design, with all of the features and benefits of the
ILC6380.
Typic al Appli ca tions
L
VIN
SD
+
VOUT
CE
1
32
45
ILC6380 CL
GND
L
VIN
SD
+
VOUT
CE
132
45
ILC6381 CL
Tr
GND
RB
CB
Figure 1:
L: 100µH (SUMIDA, CD-54)
SD: Diode (Schottky diode; MATSUSHITA MA735)
CL: 16V 47µF (Tantalum Capacitor; NICHICON, F93)
Figure 2:
L: 47µH (SUMIDA, CD-54)
SD: Diode (Schottky diode; MATSUSHITA MA735)
CL: 16V 47µF (Tantalum Capacitor; NICHICON, F93)
RB: 1kW
CB: 3300pF
Tr: 2SC32 79, 2SDI628G
ILC6380/81
SOT-89 Step-up Dual-Mode Switcher with Shutdown
©2001 Fairchild S e m icon du ctor Corporation
ILC6380/81
2
©2001 Fair chi l d Semi co nductor Corporation
Pin Assignments
Internal Block Diagram
Absolute Maximum Ratings (TA = 25°C)
Electrical Characteristics
VOUT = 5.0V, FOSC = 100kHz TA - 25°C. Unless otherwise specified, VIN = VOUT x 0.6, IOUT = 50mA. See schematic, figure 3.
Parameter Symbol Ratings Units
VOUT Input Voltage VOUT 12 V
Voltage on pin LXVLX 12 V
Current on pin LXILX 400 mA
Voltage on pin EXT VEXT VSS-0.3~VOUT+0.3 V
Current on pin EXT IEXT ±50 mA
CE Input Voltage VCE 12 V
Continuous Total Power Dissipation PD500 mW
Operating Ambient Temperature TOPR -30~+80 °C
Storage Temperature TSTG -40~+125 °C
Parameter Symbol Conditions Min. Typ. Max. Units
Output Voltage VOUT 4.875 5.000 5.125 V
Input Voltage VIN 10 V
Oscillation Startup
Voltage VST LX = 10kΩ pull-up to 5V, VOUT = VST 0.8 V
Operation Startup
Voltage VST1 IOUT = 1mA 0.9 V
No-Load Input Current IIN IOUT = 0mA (Note 1) 23.0 46.0 µA
Supply Current 1
(Note 2) IDD1L
X = 10kΩ pull-up to 5V, VOUT = 4.5V 78.6 131.1 µA
Supply Current 2 IDD2L
X = 10kΩ pull-up to 5V, VOUT = 5.5V 6.9 13.8 µA
VLX LIMITER
PWM/PFM Con trolled
BUFFER
LX
VSS
EXT
+
-
CHIP ENABLE
OSC
50/100/180KHz
VDD
VOUT
CE
Phase com
Vref
Slow Start
VDD is internally connected to the VOUT pin.
SOT -89-5
(TOP VIEW)
132
VOUT CE
LX
45
VSS
N/C
SOT -89-5
(TOP VIEW)
132
VOUT CE
EXT
45
VSS
N/C
ILC6380 ILC6381
ILC6380/81
3
©2001 Fair c hi ld Semicondu c to r Corporation
Notes:
1. The Schottky diode (S.D.), in figure 3 must be type MA735, with Reverse current (IR) < 1.0µA at reverse voltage (VR)=10.0V
2. “Supply Current 1” is the supply current while the oscillator is continuously oscillating. In actual operation the oscillator
periodically operates which results in less average power consumption.
The current that is actually provided by external VIN source is represented by “No-Load Input Current (IIN)”
3. Switching frequency is determined by delay time of internal comparator to turn LX “off”, and minimum “on” time as determined
by MAXDTY spec.
Electrical Characteristics ILC6380BP-50
VOUT = 5.0V, FOSC = 100kHz TA = 25°C. Unless ot herwise spec ified, V IN = VOUTX0.6, I OUT = 50mA. See the schematic, fi gure 4.
LX Switch-On Resistance RSWON LX = 10kΩ pull-up to 5V, VOUT = 4.5V 1.3 2.3 Ω
LX Leakage Current ILXL No external components, VOUT = VLX =
10V 1.0 µA
Oscillator Freq. FOSC LX = 10kΩ pull-up to 5V, VOUT = 4.5V,
Measuring of LX waveform 85 100 115 kHz
Maximum Duty Ration MAXDTY LX = 10kΩ pull-up to 5V, VOUT = 4.5V,
Measuring of LX on-time 80 87 92 %
PFM Duty Ration PFMDTY VIN = 4.75V, Measuring of LX on-time 5 10 20 %
Stand-by Current ISTB LX = 10kΩ pull-up to 5V, VOUT = 4.5V 0.5 µA
CE “High” Voltage VCEH LX = 10kΩ pull-up to 5V, VOUT = 4.5V,
Existence of LX Oscillation 0.75 V
CE “Low” Voltage VCEL LX = 10kΩ pull-up to 5V, VOUT = 4.5V,
Stopped LX Oscillation 0.20 V
CE “High” Current ICEH LX = 10kΩ pull-up to 5V, VOUT = VCE =
4.5V 0.25 µA
CE “Low” Current ICEL LX = 10kΩ pull-up to 5V, VOUT = 4.5V,
VCE = 0V -0.25 µA
LX Limit Voltage VLXLMT LX = 10kΩ pull-up to 5V, VOUT = 4.5V,
FOSC > FOSC x 2 (Note 2) 0.7 1.1 V
Efficiency EFFI 85 %
Slow Start Time TSS 10 msec
Parameter Symbol Conditions Min. Typ. Max. Units
Output Voltage VOUT Test Circuit Figure 2 4.875 5.000 5.125 V
Input Voltage VIN 10 V
Oscillation Startup
Voltage VST2 VOUT = VST2 0.8 V
Operation Startup
Voltage VST1 IOUT = 1mA 0.9 V
Supply Current 1
(Note 1) IDD1EXT = 10k
Ω pull-up 5V,
VOUT = 4.5V 78.6 131.1 µA
Supply Current 2 IDD2EXT = 10k
Ω pull-up 5V,
VOUT = 5.5V 6.9 13.8 µA
EXT “High” On-
Resistance REXTH EXT = 10kΩ pull-up to 5V,
VOUT = 4.5V, VEXT = VOUT - 0.4V 30 50 Ω
Parameter Symbol Conditions Min. Typ. Max. Units
Electrical Characteristics (continued)
ILC6380/81
4
©2001 Fair ch i l d Semicond uctor Corporation
EXT “Low” On-
Resistance REXTL EXT = 10kΩ pull-up to 5V,
VOUT = 4.5V, VEXT = VOUT - 0.4V 30 50 Ω
Oscillator Frequency FOSC EXT = 10kΩ pull-up to 5V,
VOUT = 4.5V, Measuring of EXT
waveform
85 100 115 kHz
Maximum Duty Ratio MAXDTY EXT = 10kΩ pull-up to 5V,
VOUT = 4.5V, Measuring of EXT high
state
80 87 92 %
CE “High” Voltage VCEH EXT = 10kΩ pull-up to 5V,
VOUT = 4.5V, Existence of Oscillation 0.75 V
CE “Low” Voltage VCEL EXT = 10kΩ pull-up to 5V,
VOUT = 4.5V, Stopped EXT Oscillation 0.20 V
CE “High” Current ICEH EXT = 10kΩ pull-up to 5V,
VOUT = 4.5V, VCE = VOUT x 0.95V 0.25 µA
CE “Low” Current ICEL EXT = 10kΩ pull-up to 5V,
VOUT = 4.5V, VCE = 0V -0.25 µA
Efficiency EFFI 85 %
Slow Start Time TSS 10 msec
Parameter Symbol Conditions Min. Typ. Max. Units
Electrical Characteristics ILC6380BP-50 (continued)
Notes:
1. The Schottky diode (S.D.), in figure 3 must be type MA735, with Reverse current (IR) < 1.0µA at reverse voltage
(VR)=10.0V
2. “Supply Current 1” is the supply current while the oscillator is continuously oscillating. In actual operation the oscillator
periodically operates which results in less average power consumption.
The current that is actually provided by external VIN source is represented by “No-Load Input Current (IIN)”
ILC6380/81
5
©2001 Fair c hi ld Semicondu c to r Corporation
Functio ns and O peration
The ILC6380 per fo rms boost DC - DC co n v e rs io n b y cont rol-
ling the switch element shown in the circuit below
When the switch is closed, current is built up through the
inductor. When the switch opens, this current has to go
somewhere and is forced through the diode to the output. As
this on and off switching continues, the output capacitor
voltage builds up due to the charge it is storing from the
inductor current. In this way, the output voltage gets boosted
relative to the input. The ILC6380 monitors the voltage on
the output capacitor to determine how much and how often
to drive the switch.
In general, the switching characteristic is determined by the
output voltage desired and the current required by the load.
Specifically the energy transfer is determined by the power
stored in the coil during each switching cycle.
PL = ƒ(tON, VIN)
The ILC6380 and ILC6381 use a PWM or Pulse Width
Modulation technique. The parts come in one of three fixed
internal frequencies: 50, 100, or 180kHz. The switches are
constantly driven at these frequencies. The control circuitry
varies the power being delivered to the load by varying the
on-time, or duty cycle, of the switch. Since more on-time
translates to higher current build-up in the inductor, the max-
imum duty cycle of the switch determines the maximum load
current that the device can support. The ILC6380 and
ILC 6381 both sup port up to 87% d uty cy cles , for m aximu m
usabl e range of lo ad currents .
There are two key advantages of the PWM type con trollers.
First, because the controller automatically varies the duty
cycle of the switch’s on-time in response to changing load
conditions, the PWM controller will always have an opti-
mized waveform for a steady-state load. This translates to
very good efficiency at high currents and minimal ripple on
the output. [Ripple is due to the output cap constantly
accepting and storing the charge received from the inductor,
and delivering charge as required by the load. The “pump-
ing” action of the switch produces a sawtooth-shaped volt-
age as s een by t h e outp u t .]
The other key advantage of the PWM type controllers is that
the radiated noise due to the switching transients will always
occur at the (fixed) switching f requency. Many applications
do not ca re m u ch abo ut s wi tch ing noi se, but ce rta in t yp es of
applications, especially communication equipment, need to
minimize the high frequency interference within their system
as much as is possible. Using a boost converter requires a
certain amount of higher frequency noise to be generated;
using a PWM converter makes that noise highly predictable;
thus e a s i e r to fi l ter out.
Dual Mode Operation
But there are downsides of PWM approaches, especially at
very low currents. Because the PWM technique relies on
con stant swit ching and varyi ng duty c ycle to ma tch the loa d
conditions, there is some point where the load current gets
too small to be handled efficiently. An actual switch con-
sumes some finite amount of current to switch on and off; at
very low currents this can be of the same magnitude as the
load current itself, driving switching efficiencies down to
50% and below. The ILC6380 and ILC6381 overcome this
limitation by automatically switching over to a PFM, or
Pulse Frequency Modulation, technique at low currents. This
technique conserves power loss by only switching the output
if the current drain requires it. As shown in the diagram
below, the wavefo rm actually skips pulses depending on t he
power needed by the output. [This technique is also called
“pulse skipping” because of this characteristic.]
In the ILC6380 and ILC6381, this switchover is internally
set to be at the point where the PWM waveform hits
approximately 10% duty cycle. So the PFM mode is running
at 10% duty cycle at the rated frequency; for 100kHz part
this means a constant on-time of 1msec. This not only is
ideal for efficiency at these low currents, but a 10% duty
cycle will have much better output ripple characteristics than
a similarly configured PFM part, such as the ILC6390 and
ILC6391.
The Dual-Mode architecture was designed specifically for
those applications, like communications, which need the
spectral predictability of a PWM -type DC-DC converter, yet
which also needs the highest efficiencies possible, especially
in Shutdown or Standby mode. [For other conversion
techniques, please see the ILC6370/71 and ILC6390/91
datasheets.]
Other Considerations
The other limitation of PWM techniques is that, while the
fundamental switching frequency is easier to filter out since
it’s constant, the higher order harmonics of PWM will be
present and may have to be filtered out, as well. Any filtering
V
SET
V
OUT
Switch
Waveform
ILC6380/81
6
©2001 Fair ch i l d Semicond uctor Corporation
requirements, though, will vary by app lication an d by actual
system design and layout, so generalizations in this area are
difficult, at best.
However, PWM control for boost DC-DC conversion is
widely used, especially in audio-no ise sensitive applications
or applications requiring strict filtering of the high frequency
components. Impala’s products give very good efficiencies
of 85% at 50µ A output (5V product), 87% maximum duty
cycles for high load conditions, while maintaining very low
shutdown current levels of 0.5µA. The only difference
between the ILC6380 and IL C6381 parts is that the 6381 is
configured to drive an external transistor as the switch
element. Since larger transistors can be selected for this
element, higher effective loads can be regulated.
Start-up Mod e
The ILC6380 has an internal soft-start mode which sup-
presses ringing or overshoot on the output during start-up.
The following diagram illustrates this start-up condition’s
typical performance:
External Components and Layout
Consideration
The ILC6380 is designed to provide a complete DC-DC con-
vertor s olu tio n with a m ini mum of e xte rnal co mp o nents. Id e-
ally, only three externals are required: the inductor, a pass
diode, and an output capacitor.
The inductor needs to be of low DC Resistance type, typi-
cally 1Ω value. Toroidal wound inductors have better field
containment (less high frequency noise radiated out) but tend
to be more expensive. Some manufacturers like Coilcraft
have new bobbin-wound inductors with shielding included,
which may be an ideal fit for these app lications. Co ntact the
manufacturer for more information.
The inductor size needs to be in the range of 47µ H to 1µH.
In general, larger inductor sizes deliver less current, so the
load current will determine t he inductor size used.
For load currents higher than 10mA, use an inductor from
47mH to 100µH. [The 100µH inductor shown in the
datasheet is the most typical used for this application.]
For load currents of around 5mA, such as pagers, use an
inductor in the range of 100µH to 330µH. 220µH is the most
typical value used here.
For lighter loads, an inductor of up to 1mH can be used. The
use of a larger inductor will increase overall conv ersion effi-
ciency, due to the reduction in switching currents through the
device.
For the ILC6381, using an external transistor, the use of a
47µH inductor is recommended based on our experience
with the part. Note that these values are recommended for
both 50kHz and 100kHz operation. If using the ILC6380 or
ILC6381 at 180kHz, the inductor size can be reduced to
approximately ha lf of these stated values.
The capacitor should, in general, always be tantalum type, as
tantalum has much better ESR and temperature stability than
other capacitor types. NEVER use electrolytics or chemical
caps, as the C-value changes below 0×C so much as to make
the overall design unstable.
Diff e rent C-values will directly impact the ripple seen on the
output at a given load current, due to the direct charge-to-
voltage relationship of this element. Different C-values will
also indirectly affect system reliability, as the lifetime of the
capacitor can be degraded by constant high current influx
and outflux. Running a capacitor near its maximum rated
voltage can deteriorate lifetime as well; this is especially true
for tantalum caps which are particularly sensitive to over-
voltage conditions.
In general, then, this capacitor should always be 4 7µF, Tan-
talum, 16V rating.
The diode must be of shottkey type for fast recovery and
minimal loss. A diode rated at great e r than 200mA and ma x-
imum voltage greater than 30V is recommended for the fast-
est switching time and best reliability over time. Different
diodes may introduce different levels of high frequency
swit ching noise into the ou tput wav eform, so trying out sev -
eral sources may make the most sense for your system.
For the IL6381, much of the component selection is as
descr i be d above, w it h t he addi ti on of the e xt er nal NP N t r an -
sistor and the base drive network. The transistor needs to be
of NPN t ype, and should be rated for currents of 2A or more.
[This translates to lower effective on resistance and, there-
fore, higher overall efficiencies.] The base components
should remain at 1kΩ and 3300pF; any changes need to be
verified prior to imp lem entation.
As for actual physical component layout, in general, the
more compact the layout is, the better the overall perfor-
mance will be. It is important to rememb er that everything in
the circuit depends on a common and solid ground reference.
Ground bounce can directly affect the output regulation and
presents difficult behavior to predict. Keeping all ground
V
IN
- V
f
V
OUT MIN
T
SOFT-START
(~10msec)
t = 0
ILC6380/81
7
©2001 Fair c hi ld Semicondu c to r Corporation
traces wide will eliminate ground bounce problems.
It is also critical that the ground pin of CL and the VSS pin of
the device be the same point on the board, as this capacitor
serves two functions: that of the output load capacitor, and
that of the input supply bypass capacitor.
Layouts for DC-DC converter designs are critical for ov erall
performance, but following these simple guidelines can sim-
plify the task by avoiding some of the more common mis-
takes made in these cases. Once actual performance is
completed, though, be sure to double-check the design on
actual manufacturing prototype product to verify that noth-
ing has changed which can affect the performance.
OUTPUT CURRENT IOUT (mA)
0
2.7
OUTPUT VOLTAGE VOUT (V)
2.9
40
3.1
80 200
VIN=1.0V
3.0
2.8
2.6
120 160
L=100µH
C=47µF(Tantalum)
VIN=1.5V
VIN=2.0V
3.2
OUTPUT CURRENT IOUT (mA)
0
40
EFFICIENCY: EFFI (%)
80
40 80
100
60
20
0120 160
L=100µH
C=47µF(Tantalum)
VIN=1.0V VIN=1.5V
VIN=2.0V
OUTPUT CURRENT IOUT (mA)
0
40
RIPPLE Vr (mVp-p)
80
40 80 160
VIN=1.0V
100
60
20
0120
L=100µH
C=47µF(Tantalum)
VIN=1.5V
VIN=2.0V
RIPPLE VOLTAGE vs OUTPUT CURRENT
INPUT VOLTAGE VIN (V)
1.0
20
INPUT CUR RENT (µA)
40
1.2 1.4 2.0
50
30
10
01.6 1.8
RL=0
L=100µH
INPUT CU RREN T vs INPUT VOLTAGE
ILC6380CP-30 ILC6380CP-30
EFFICIENCY vs OUTPUT CURRENT
ILC6380CP-30
OUTPUT VOLTAGE vs OUTPUT CURRENT
ILC6380CP-30
C=47µF(Tantalum)
Iout = 0 (no load)
Ty pic al Performanc e C h ar acteristics General conditions for all curves
ILC6380/81
10/15/01 0.0m 001
Stock#DSxxxxxxxx
2001 Fairch i l d Semiconductor Co rporation
LIFE SUPPORT POLICY
FAIRCHILD’S P RODUCTS ARE NOT AUTHORIZED FOR USE AS C RITICAL COM PONENTS I N LIFE SUPPORT DEVI CES
OR SYSTEMS WITHOUT THE EXPRESS WRITTE N APPROV AL OF THE PRES ID ENT OF FAIRCH ILD SEMI C ON DUCTOR
CORPORATION. As used herein:
1. Life support devices or systems are devices or systems
which, (a ) are intended for surgical implant into the body,
or (b) support or sustain life, and (c) whose failure to
perform when properly used in accordance with
instructions for use provided in the labeling, can be
reasonably expected to result in a significant injury of the
user.
2. A critical component in any component of a life support
device or system whose fail ure to perform can be
reasonably expected to cause the failure of the life support
device or system, or to affect its safety or effectiveness.
www.fairchildsemi.com
DISCLAIMER
FAIRCHILD SEMICONDUCTOR RESERVES THE RIGHT TO MAKE CHANGES WITHOUT FURTHER NOTICE TO
ANY PRODUC TS HEREIN TO IMPROVE RELIAB IL IT Y , FUNC TI ON OR DESIGN. FAIRC HILD DOES NOT AS SUME
ANY LIABILITY ARISING OU T OF THE APPLICATION O R USE OF ANY PRODUCT OR CIRCUIT DESCRIBED HERE IN;
NEITHER DOES IT CONVEY ANY LICENSE UNDER ITS PATENT RIGHTS, NOR THE RIGHTS OF OTHERS.
Ordering Information*
*Standard product offering comes in tape & reel, quantity 1000 per reel,
orientation right for SOT-89
Product Number Package
ILC6380CP-25 2.5V ± 2.5%@50kHz
ILC6380CP-33 3.3V ± 2.5%@50kHz
ILC6380CP-50 5.0V ± 2.5%@50kHz
ILC6380CP-25 2.5V ± 2.5%@100kHz
ILC6380CP-33 3.3V ± 2.5%@100kHz
ILC6380CP-50 5.0V ± 2.5%@100kHz
ILC6380CP-25 2.5V ± 2.5%@180kHz
ILC6380CP-33 3.3V ± 2.5%@180kHz
ILC6380CP-50 5.0V ± 2.5%@180kHz
ILC6381CP-25 2.5V ± 2.5%@50kHz, external xtor
ILC6381CP-33 3.3V ± 2.5%@50kHz, external xtor
ILC6381CP-50 5.0V ± 2.5%@50kHz, external xtor
ILC6381BP-25 2.5V ± 2.5%@100kHz, external xtor
ILC6381BP-33 3.3V ± 2.5%@100kHz, external xtor
ILC6381BP-50 5.0V ± 2.5%@100kHz, external xtor
ILC6381AP-25 2.5V ± 2.5%@180kHz, external xtor
ILC6381AP-33 3.3V ± 2.5%@180kHz, external xtor
ILC6381AP-50 5.0V ± 2.5%@180kHz, external xtor
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Contents
General description | Features | Applications |
Product status/pricing/packaging
General description
100mA boost converter in 5-lead SOT-89
package using both PFM and PWM conversion
techniques. In normal operation the ILC6380
runs in PWM mode running at one of three
fixed frequencies. At light loads the ILC6380
senses when the duty cycle drops to
approximately 10%, and automatically
switches into a power-saving PFM switching
technique. This maintains high efficiencies
both at full load and in system sleep
conditions.
Only 3 external components are needed to
complete the switcher design, and standard
voltage options of 2.5, 3.3, and 5.0V at ±2.5%
accuracy feature on-chip phase compensation
and soft-start design.
ILC6381 drives an external transistor for
higher current switcher design, with all of the
features and benefits of the ILC6380.
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Features
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Product Folder - Fairchild P/N ILC6381CP50 - Product information
● 85% efficiency at 50mA
● Start-up voltages as low as 900mV
● ±2.5% accurate outputs
● Complete switcher design with only 3
external components
● 50, 100 and 180kHz switching
frequency versions available
● Shutdown to 0.5µA Iq
● External transistor option allows several
hundred milliamp switcher design
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Applications
● Cellular Phones, Pagers
● Portable Cameras and Video Recorders
● Palmtops and PDAs
back to top
Product status/pricing/packaging
Product Product status Pricing* Leads Packing method
ILC6381CP50X Not recommended for new designs $2.09 3 TAPE REEL
* 1,000 piece Budgetary Pricing
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