ADE7768ARZ - ANALOG DEVICES

Energy Metering IC with Integrated

Oscillator and Positive Power Accumulation

ADE7768

Rev. A

Information furnished by Analog Devices is believed to be accurate and reliable.

However, no responsibility is assumed by Analog Devices for its use, nor for any

infringements of patents or other rights of third parties that may result from its use.

Specifications subject to change without notice. No license is granted by implication

or otherwise under any patent or patent rights of Analog Devices. Trademarks and

registered trademarks are the property of their respective owners.

One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.

Tel: 781.329.4700 www.analog.com

FEATURES

On-chip oscillator as clock source

High accuracy, supports 50 Hz/60 Hz IEC62053-21

Less than 0.1% error over a dynamic range of 500 to 1

Supplies positive-only average real power on frequency

outputs F1 and F2

High frequency output CF calibrates and supplies

instantaneous, positive-only real power

Logic output REVP indicates potential miswiring or negative

power

Direct drive for electromechanical counters and 2-phase

stepper motors (F1 and F2)

Proprietary ADCs and DSPs provide high accuracy over

large variations in environmental conditions and time

On-chip power supply monitoring

On-chip creep protection (no-load threshold)

On-chip reference 2.45 V (20 ppm/°C typical) with

external overdrive capability

Single 5 V supply, low power (20 mW typical)

Low cost CMOS process

GENERAL DESCRIPTION

The ADE77681 is a high accuracy, electrical energy metering IC.

It is a pin reduction version of the ADE7755, enhanced with a

precise oscillator circuit that serves as a clock source to the chip.

The ADE7768 eliminates the cost of an external crystal or

resonator, thus reducing the overall cost of a meter built with

this IC. The chip directly interfaces with the shunt resistor.

1U.S. Patents 5,745,323; 5,760,617; 5,862,069; 5,872,469; others pending.

The ADE7768 specifications surpass the accuracy require-

ments of the IEC62053-21 standard. The AN-679 Application

Note can be used as a basis for a description of an IEC61036

(equivalent to IEC62053-21) low cost, watt-hour meter

reference design.

The only analog circuitry used in the ADE7768 is in the Σ-Δ

ADCs and reference circuit. All other signal processing, such as

multiplication and filtering, is carried out in the digital domain.

This approach provides superior stability and accuracy over

time and extreme environmental conditions.

The ADE7768 supplies positive-only average real power

information on the low frequency outputs, F1 and F2. These

outputs can be used to directly drive an electromechanical

counter or interface with an MCU. The high frequency CF logic

output, ideal for calibration purposes, provides instantaneous

positive-only, real power information.

The ADE7768 includes a power supply monitoring circuit on

the VDD supply pin. The ADE7768 remains inactive until the

supply voltage on VDD reaches approximately 4 V. If the supply

falls below 4 V, the ADE7768 also remains inactive and the F1,

F2, and CF outputs are in their nonactive modes.

Internal phase matching circuitry ensures that the voltage and

current channels are phase matched, while the HPF in the

current channel eliminates dc offsets. An internal no-load

threshold ensures that the ADE7768 does not exhibit creep

when no load is present. When REVP is logic high, the

ADE7768 does not generate any pulse on F1, F2, and CF.

The ADE7768 comes in a 16-lead, narrow body SOIC package.

FUNCTIONAL BLOCK DIAGRAM

MULTIPLIER

REVP

V2P

V2N

V1P

RCLKIN

REFIN/OUT F1 F2

SCF S0 S1

PHASE

CORRECTION

4kΩ

...110101...

SIGNAL

PROCESSING

BLOCK

POWER

SUPPLY MONITOR

Σ-Δ

ADC

V1N

ADE7768

...11011001...

2.5V

REFERENCE

VDD AGND DGND

INTERNAL

OSCILLATOR

Σ-Δ

ADC

LPF

HPF

1 6 13

7 11 8 10 12 14 16 159

DIGITAL-TO-FREQUENCY

CONVERTER

05331-001

Figure 1.

ADE7768

Rev. A | Page 2 of 20

TABLE OF CONTENTS

Specifications..................................................................................... 3

Timing Characteristics ................................................................ 4

Absolute Maximum Ratings............................................................ 5

ESD Caution.................................................................................. 5

Terminology...................................................................................... 6

Pin Configuration and Function Descriptions............................. 7

Typical Performance Characteristics ............................................. 8

Functional Description..................................................................10

Theory of Operation.................................................................. 10

Analog Inputs.............................................................................. 11

Power Supply Monitor............................................................... 12

Internal Oscillator (OSC).......................................................... 14

Transfer Function....................................................................... 14

Selecting a Frequency for an Energy Meter Application ...... 15

No-Load Threshold.................................................................... 16

Negative Power Information..................................................... 16

Evaluation Board and Reference Design Board..................... 16

Outline Dimensions....................................................................... 17

Ordering Guide .......................................................................... 17

Revision History

8/05—Sp0 to Rev. A

ADE7768

Rev. A | Page 3 of 20

SPECIFICATIONS

VDD = 5 V ± 5%, AGND = DGND = 0 V, on-chip reference, RCLKIN = 6.2 kΩ, 0.5% ± 50 ppm/°C, TMIN to TMAX = −40°C to +85°C,

unless otherwise noted.

Table 1.

Parameter Value Unit Test Conditions/Comments

ACCURACY1, 2

Measurement Error on Channel V1 0.1 % reading typ Channel V2 with full-scale signal (±165 mV),

25°C over a dynamic range 500 to 1,

line frequency = 45 Hz to 65 Hz

Phase Error1 Between Channels

V1 Phase Lead 37° (PF = 0.8 Capacitive) ±0.1 Degrees (°) max

V1 Phase Lag 60° (PF = 0.5 Inductive) ±0.1 Degrees (°) max

AC Power Supply Rejection1

Output Frequency Variation (CF) 0.2 % reading typ S0 = S1 = 1, V1 = 21.2 mV rms, V2 = 116.7 mV rms @

50 Hz, ripple on VDD of 200 mV rms @ 100 Hz

DC Power Supply Rejection1

Output Frequency Variation (CF) ±0.3 % reading typ S0 = S1 = 1, V1 = 21.2 mV rms, V2 = 116.7 mV rms,

VDD = 5 V ± 250 mV

ANALOG INPUTS See the Analog Inputs section

Channel V1 Maximum Signal Level ±30 mV max V1P and V1N to AGND

Channel V2 Maximum Signal Level ±165 mV max V2P and V2N to AGND

Input Impedance (DC) 320 kΩ min OSC = 450 kHz, RCLKIN = 6.2 kΩ, 0.5% ± 50 ppm/°C

Bandwidth (–3 dB) 7 kHz nominal OSC = 450 kHz, RCLKIN = 6.2 kΩ, 0.5% ± 50 ppm/°C

ADC Offset Error1, 2±18 mV max See the Terminology and the Typical Performance

Characteristics sections

Gain Error1±4 % ideal typ External 2.5 V reference, V1 = 21.2 mV rms,

V2 = 116.7 mV rms

OSCILLATOR FREQUENCY (OSC) 450 kHz nominal RCLKIN = 6.2 kΩ, 0.5% ± 50 ppm/°C

Oscillator Frequency Tolerance1±12 % reading typ

Oscillator Frequency Stability1±30 ppm/°C typ

REFERENCE INPUT

REFIN/OUT Input Voltage Range 2.65 V max 2.45 V nominal

2.25 V min 2.45 V nominal

Input Capacitance 10 pF max

ON-CHIP REFERENCE 2.45 V nominal

Reference Error ±200 mV max

Temperature Coefficient ±20 ppm/°C typ

LOGIC INPUTS3

SCF, S0, S1

Input High Voltage, VINH 2.4 V min VDD = 5 V ± 5%

Input Low Voltage, VINL 0.8 V max VDD = 5 V ± 5%

Input Current, IIN ±1 μA max Typically 10 nA, VIN = 0 V to VDD

Input Capacitance, CIN 10 pF max

LOGIC OUTPUTS3

F1 and F2

Output High Voltage, VOH 4.5 V min ISOURCE = 10 mA, VDD = 5 V, ISINK = 10 mA, VDD = 5 V

Output Low Voltage, VOL 0.5 V max

Output High Voltage, VOH 4 V min ISOURCE = 5 mA, VDD = 5 V, ISINK = 5 mA, VDD = 5 V

Output Low Voltage, VOL 0.5 V max

Frequency Output Error1, 2 (CF) ±10 % ideal typ External 2.5 V reference, V1 = 21.2 mV rms,

V2 = 116.7 mV rms

ADE7768

Rev. A | Page 4 of 20

Parameter Value Unit Test Conditions/Comments

POWER SUPPLY For specified performance

VDD 4.75 V min 5 V – 5%

5.25 V max 5 V + 5%

IDD 5 mA max Typically 4 mA

1 See the Terminology section for an explanation of specifications.

2 See the figures in the Typical Performance Characteristics section.

3 Sample tested during initial release and after any redesign or process change that may affect this parameter.

TIMING CHARACTERISTICS

VDD = 5 V ± 5%, AGND = DGND = 0 V, on-chip reference, RCLKIN = 6.2 kΩ, 0.5% ± 50 ppm/°C, TMIN to TMAX = –40°C to +85°C,

unless otherwise noted. Sample tested during initial release and after any redesign or process change that may affect this parameter.

See Figure 2.

Table 2.

Parameter Specifications Unit Test Conditions/Comments

t11120 ms F1 and F2 pulse width (logic low)

t2 See Table 6 sec Output pulse period. See the Transfer Function section.

t3 1/2 t2 sec Time between the F1 and F2 falling edges.

t41, 290 ms CF pulse width (logic high).

t5 See Table 7 sec CF pulse period. See the Transfer Function section.

t6 2 μs Minimum time between the F1 and F2 pulses.

1 The pulse widths of F1, F2, and CF are not fixed for higher output frequencies. See the Frequency Outputs section.

2 The CF pulse is always 35 μs in high frequency mode. See the Frequency Outputs section and Table 7.

05331-002

Figure 2. Timing Diagram for Frequency Outputs

ADE7768

Rev. A | Page 5 of 20

ABSOLUTE MAXIMUM RATINGS

TA = 25°C, unless otherwise noted.

Table 3.

Parameter Value

VDD to AGND −0.3 V to +7 V

VDD to DGND −0.3 V to +7 V

Analog Input Voltage to AGND,

V1P, V1N, V2P, and V2N −6 V to +6 V

Reference Input Voltage to AGND −0.3 V to VDD + 0.3 V

Digital Input Voltage to DGND −0.3 V to VDD + 0.3 V

Digital Output Voltage to DGND −0.3 V to VDD + 0.3 V

Operating Temperature Range −40°C to +85°C

Storage Temperature Range −65°C to +150°C

Junction Temperature 150°C

16-Lead Plastic SOIC, Power Dissipation 350 mW

θJA Thermal Impedance1124.9°C/W

Package Temperature Soldering See J-STD-20

1 JEDEC 1S standard (2-layer) board data.

Stresses above those listed under Absolute Maximum Ratings

may cause permanent damage to the device. This is a stress

rating only and functional operation of the device at these or

any other conditions above those indicated in the operational

section of this specification is not implied. Exposure to absolute

maximum rating conditions for extended periods may affect

device reliability.

ESD CAUTION

ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on

the human body and test equipment and can discharge without detection. Although this product features

proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy

electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degrada-

tion or loss of functionality.

ADE7768

Rev. A | Page 6 of 20

TERMINOLOGY

Measurement Error

The error associated with the energy measurement made by the

ADE7768 is defined by the following formula:

%100

7768

%×

−

=EnergyTrue

EnergyTrueADEbyRegisteredEnergy

Error

Phase Error Between Channels

The high-pass filter (HPF) in the current channel (Channel V1)

has a phase-lead response. To offset this phase response and

equalize the phase response between channels, a phase-

correction network is also placed in Channel V1. The phase-

correction network matches the phase to within 0.1° over a

range of 45 Hz to 65 Hz, and 0.2° over a range 40 Hz to 1 kHz

(see Figure 24 and Figure 25).

Power Supply Rejection (PSR)

This quantifies the ADE7768 measurement error as a

percentage of reading when the power supplies are varied.

For the ac PSR measurement, a reading at nominal supplies

(5 V) is taken. A 200 mV rms/100 Hz signal is then introduced

onto the supplies and a second reading is obtained under the

same input signal levels. Any error introduced is expressed as a

percentage of reading—see the Measurement Error definition.

For the dc PSR measurement, a reading at nominal supplies

(5 V) is taken. The supplies are then varied 5% and a second

reading is obtained with the same input signal levels. Any error

introduced is again expressed as a percentage of the reading.

ADC Offset Error

This refers to the small dc signal (offset) associated with the

analog inputs to the ADCs. However, the HPF in Channel V1

eliminates the offset in the circuitry. Therefore, the power

calculation is not affected by this offset.

Frequency Output Error (CF)

The frequency output error of the ADE7768 is defined as the

difference between the measured output frequency (minus the

offset) and the ideal output frequency. The difference is

expressed as a percentage of the ideal frequency. The ideal

frequency is obtained from the ADE7768 transfer function.

Gain Error

The gain error of the ADE7768 is defined as the difference

between the measured output of the ADCs (minus the offset)

and the ideal output of the ADCs. The difference is expressed

as a percentage of the ideal of the ADCs.

Oscillator Frequency Tolerance

The oscillator frequency tolerance of the ADE7768 is defined as

the part-to-part frequency variation in terms of percentage at

room temperature (25°C). It is measured by taking the differ-

ence between the measured oscillator frequency and the

nominal frequency defined in the Specifications section.

Oscillator Frequency Stability

Oscillator frequency stability is defined as frequency variation

in terms of the parts-per-million drift over the operating

temperature range. In a metering application, the temperature

range is −40°C to +85°C. Oscillator frequency stability is

measured by taking the difference between the measured

oscillator frequency at −40°C and +85°C and the measured

oscillator frequency at +25°C.

ADE7768

Rev. A | Page 7 of 20

PIN CONFIGURATION AND FUNCTION DESCRIPTIONS

DD 1

V2P

V2N

V1N

DGND

V1P

REVP

AGND

RCLKIN

REF

IN/OUT 7

SCF

ADE7768

TOP VIEW

(Not to Scale)

05331-003

Figure 3. Pin Configuration

Table 4. Pin Function Descriptions

Pin No. Mnemonic Description

1 VDD Power Supply. This pin provides the supply voltage for the circuitry in the ADE7768. The supply voltage

should be maintained at 5 V ± 5% for specified operation. This pin should be decoupled with a 10 μF

capacitor in parallel with a 100 nF ceramic capacitor.

2, 3 V2P, V2N Analog Inputs for Channel V2 (Voltage Channel). These inputs provide a fully differential input pair. The

maximum differential input voltage is ±165 mV for specified operation. Both inputs have internal ESD

protection circuitry; an overvoltage of ±6 V can be sustained on these inputs without risk of permanent

damage.

4, 5 V1N, V1P Analog Inputs for Channel V1 (Current Channel). These inputs are fully differential voltage inputs with a

maximum signal level of ±30 mV with respect to the V1N pin for specified operation. Both inputs have

internal ESD protection circuitry and, in addition, an overvoltage of ±6 V can be sustained on these inputs

without risk of permanent damage.

6 AGND This pin provides the ground reference for the analog circuitry in the ADE7768, that is, the ADCs and

reference. This pin should be tied to the analog ground plane of the PCB. The analog ground plane is the

ground reference for all analog circuitry, such as antialiasing filters, current and voltage sensors, and so forth.

For accurate noise suppression, the analog ground plane should be connected to the digital ground plane at

only one point. A star ground configuration helps to keep noisy digital currents away from the analog

circuits.

7 REFIN/OUT This pin provides access to the on-chip voltage reference. The on-chip reference has a nominal value of 2.45 V

and a typical temperature coefficient of 20 ppm/°C. An external reference source may also be connected at

this pin. In either case, this pin should be decoupled to AGND with a 1 μF tantalum capacitor and a 100 nF

ceramic capacitor. The internal reference cannot be used to drive an external load.

8 SCF Select Calibration Frequency. This logic input is used to select the frequency on the calibration output CF.

See Table 7.

9, 10 S1, S0 These logic inputs are used to select one of four possible frequencies for the digital-to-frequency conversion.

With this logic input, designers have greater flexibility when designing an energy meter. See the Selecting a

Frequency for an Energy Meter Application section.

11 RCLKIN To enable the internal oscillator as a clock source to the chip, a precise low temperature drift resistor at a

nominal value of 6.2 kΩ must be connected from this pin to DGND.

12 REVP This logic output goes high when negative power is detected, that is, when the phase angle between the

voltage and current signals is greater than 90°. This output is not latched and is reset when positive power is

once again detected. The output goes high or low at the same time that a pulse is issued on CF.

13 DGND This pin provides the ground reference for the digital circuitry in the ADE7768, that is, the multiplier, filters,

and digital-to-frequency converter. This pin should be tied to the digital ground plane of the PCB. The digital

ground plane is the ground reference for all digital circuitry, such as counters (mechanical and digital), MCUs,

and indicator LEDs. For accurate noise suppression, the analog ground plane should be connected to the

digital ground plane at one point only—a star ground.

14 CF Calibration Frequency Logic Output. The CF logic output provides instantaneous, positive-only real power

information. This output is intended for calibration purposes. See the SCF pin description.

15, 16 F2, F1 Low Frequency Logic Outputs. F1 and F2 supply average positive-only real power information. The logic

outputs can be used to directly drive electromechanical counters and 2-phase stepper motors. See the

Transfer Function section.

ADE7768

Rev. A | Page 8 of 20

TYPICAL PERFORMANCE CHARACTERISTICS

6.2kΩ

V2N

200Ω

20V

150nF

V2P

200Ω

602kΩ

V1P

V1N

350μΩ

40A TO

40mA

REF

IN/OUT

100nF

1μF

100nF 10μF

DGND

REVP

RCLKIN

SCF 10nF 10nF 10nF

PS2501-1

ADE7768

10kΩ

200Ω

150nF

AGND

150nF

820Ω

613

2 3

05331-004

Figure 4. Test Circuit for Performance Curves

–1.0

–0.8

–0.6

–0.4

–0.2

ERROR (% of Reading)

0.2

0.4

0.6

05331-019

CURRENT CHANNEL (% of Full Scale)

0.1 101 100

0.8

1.0

+25°C

+85°C

–40°C

PF = 1

ON-CHIP REFERENCE

Figure 5. Error as a % of Reading over Temperature

with On-Chip Reference (PF = 1)

–1.0

–0.8

–0.6

–0.4

–0.2

ERROR (% of Reading)

0.2

0.4

0.6

05331-020

CURRENT CHANNEL (% of Full Scale)

0.1 101 100

0.8

1.0

–40°C, PF = 0.5 IND

+25°C, PF = 1

+85°C, PF = 0.5 IND +25°C, PF = 0.5 IND

PF = 0.5 IND

ON-CHIP REFERENCE

Figure 6. Error as a % of Reading over Temperature

with On-Chip Reference (PF = 0.5 IND)

–1.0

–0.8

–0.6

–0.4

–0.2

ERROR (% of Reading)

0.2

0.4

0.6

05331-021

CURRENT CHANNEL (% of Full Scale)

0.1 101 100

0.8

1.0

+25°C

+85°C

–40°C

PF = 1

EXTERNAL REFERENCE

Figure 7. Error as a % of Reading over Temperature

with External Reference (PF = 1)

–1.0

–0.8

–0.6

–0.4

–0.2

ERROR (% of Reading)

0.2

0.4

0.6

05331-022

CURRENT CHANNEL (% of Full Scale)

0.1 101 100

0.8

1.0

+25°C, PF = 1

–40°C, PF = 0.5 IND

+25°C, PF = 0.5 IND

+85°C, PF = 0.5 IND

PF = 0.5 IND

EXTERNAL REFERENCE

Figure 8. Error as a % of Reading over Temperature

with External Reference (PF = 0.5 IND)

ADE7768

Rev. A | Page 9 of 20

–0.5

–0.4

–0.3

–0.2

–0.1

0.1

0.2

0.3

0.4

0.5

ERROR (% of Reading)

FREQUENCY (Hz)

5045 55 60 65

05331-018

PF = 0.5 IND

PF = 0.5 CAP

PF = 1

Figure 9. Error as a % of Reading over Input Frequency

–1.0

–0.8

–0.6

–0.4

–0.2

ERROR (% of Reading)

0.2

0.4

0.6

05331-023

CURRENT CHANNEL (% of Full Scale)

0.1 101 100

0.8

1.0

5.25V

4.75V

PF = 1

ON-CHIP REFERENCE

Figure 10. PSR with On-Chip Reference, PF = 1

–1.0

–0.8

–0.6

–0.4

–0.2

ERROR (% of Reading)

0.2

0.4

0.6

05331-024

CURRENT CHANNEL (% of Full Scale)

0.1 101 100

0.8

1.0

5.25V

4.75V

PF = 1

EXTERNAL REFERENCE

Figure 11. PSR with External Reference, PF = 1

FREQUENCY

CHANNEL V1 OFFSET (mV)

05331-025

–5–4–3–2–10123456789

EXTERNAL REFERENCE

TEMPERATURE = 25°C

DISTRIBUTION CHARACTERISTICS

MEAN = 2.247828

SDs = 1.367176

MIN = –2.09932

MAX = +5.28288

NO. OF POINTS = 100

Figure 12. Channel V1 Offset Distribution

FREQUENCY

CHANNEL V2 OFFSET (mV)

05331-026

–12–10–8–6–4–2024681012

EXTERNAL REFERENCE

TEMPERATURE = 25°C

DISTRIBUTION CHARACTERISTICS

MEAN = –1.563484

SDs = 2.040699

MIN = –6.82969

MAX = +2.6119

NO. OF POINTS = 100

Figure 13. Channel V2 Offset Distribution

–10–8–6–4–2024681012

200

400

600

800

1000

FREQUENCY

DEVIATION FROM MEAN (%)

05331-027

EXTERNAL REFERENCE

TEMPERATURE = 25°C

DISTRIBUTION CHARACTERISTICS

MEAN = 0%

SDs = 1.55%

MIN = –11.79%

MAX = +6.08%

NO. OF POINTS = 3387

Figure 14. Part-to-Part CF Deviation from Mean

ADE7768

Rev. A | Page 10 of 20

FUNCTIONAL DESCRIPTION

THEORY OF OPERATION

The two ADCs in the ADE7768 digitize the voltage signals from

the current and voltage sensors. These ADCs are 16-bit Σ-Δs

with an oversampling rate of 450 kHz. This analog input

structure greatly simplifies sensor interfacing by providing a

wide dynamic range for direct connection to the sensor and

by simplifying the antialiasing filter design. A high-pass filter

in the current channel removes any dc component from the

current signal. This eliminates any inaccuracies in the real

power calculation due to offsets in the voltage or current

signals.

The real power calculation is derived from the instantaneous

power signal. The instantaneous power signal is generated by

a direct multiplication of the current and voltage signals. To

extract the real power component (the dc component), the

instantaneous power signal is low-pass filtered. Figure 15

illustrates the instantaneous real power signal and shows how

the real power information can be extracted by low-pass

filtering the instantaneous power signal. In the ADE7768,

this signal is compared to 0 and only positive real power is

accumulated for F1, F2, and CF pulse outputs. This scheme

correctly calculates real power for sinusoidal current and

voltage waveforms at all power factors. All signal processing

is carried out in the digital domain for superior stability over

temperature and time.

TIME TIME

ADC

CH1

CH2

MULTIPLIER

DIGITAL-TO-

FREQUENCY

DIGITAL-TO-

FREQUENCY

INSTANTANEOUS REAL

POWER SIGNAL

INSTANTANEOUS

POWER SIGNAL – p(t)

LPF

HPF

05331-005

≥0

Figure 15. Signal Processing Block Diagram

The low frequency outputs (F1 and F2) are generated by

accumulating positive-only real power information. This low

frequency inherently means a long accumulation time between

output pulses. Consequently, the resulting output frequency is

proportional to the average positive-only real power. This

average positive-only real power information is then accumu-

lated (by a counter) to generate real energy information (see

Figure 16). Conversely, due to its high output frequency and

shorter integration time, the CF output frequency is propor-

tional to the instantaneous positive-only real power. This is

useful for system calibration, which can be done faster under

steady load conditions.

ACTIVE ENERGY

INSTANTANEOUS

POWER

MAGNITUDEMAGNITUDE

0Wh

05331-028

Figure 16. Positive-Only Energy Accumulation

Power Factor Considerations

The method used to extract the real power information from

the instantaneous power signal (that is, by low-pass filtering) is

still valid even when the voltage and current signals are not in

phase. Figure 17 displays the unity power factor condition and a

displacement power factor (DPF) = 0.5 (a current signal lagging

the voltage by 60°). Assuming that the voltage and current

waveforms are sinusoidal, the real power component of the

instantaneous power signal (that is, the dc term) is given by

(

°×

⎟

⎠

⎞

⎜

⎝

⎛×60cos

)

(1)

This is the correct real power calculation.

V× I

POWER

CURRENT

VOLTAGE

POWER

TIME

VOLTAGE CURRENT

V× I

2COS (60°)

INSTANTANEOUS

POWER SIGNAL INSTANTANEOUS REAL

POWER SIGNAL

INSTANTANEOUS

POWER SIGNAL

INSTANTANEOUS REAL

POWER SIGNAL

60°

05331-006

Figure 17. DC Component of Instantaneous Power Signal Conveys

Real Power Information, PF < 1

ADE7768

Rev. A | Page 11 of 20

Nonsinusoidal Voltage and Current

The real power calculation method also holds true for non-

sinusoidal current and voltage waveforms. All voltage and

current waveforms in practical applications have some

harmonic content. Using the Fourier transform, instantaneous

voltage and current waveforms can be expressed in terms of

their harmonic content.

(

0h h

0αthωVVtv +××+= ∑

∞

≠

sin2)(

)

(2)

where:

v(t) is the instantaneous voltage.

V0 is the average value.

Vh is the rms value of voltage harmonic h.

is the phase angle of the voltage harmonic.

(

∑

∞

≠

+××+=

hhO βthIIti

sin2)(

)

(3)

where:

i(t) is the instantaneous current.

I0 is the dc component.

Ih is the rms value of current harmonic h.

is the phase angle of the current harmonic.

Using Equations 2 and 3, the real power (P) can be expressed in

terms of its fundamental real power (P1) and harmonic real

power (PH) as P = P1 + PH

where:

(4)

cos

111 IVP ×=

111

βαφ

−=

and

(5)

hH IVP

cos×= ∑

∞

≠

hhh

βαφ

−=

In Equation 5, a harmonic real power component is generated

for every harmonic, provided that harmonic is present in both

the voltage and current waveforms. The power factor calcul-

ation has previously been shown to be accurate in a pure

sinusoid. Therefore, the harmonic real power must also

correctly account for the power factor, because it is made up

of a series of pure sinusoids.

Note that the input bandwidth of the analog inputs is 7 kHz at

the nominal internal oscillator frequency of 450 kHz.

ANALOG INPUTS

Channel V1 (Current Channel)

The voltage output from the current sensor is connected to the

ADE7768 here. Channel V1 is a fully differential voltage input.

V1P is the positive input with respect to V1N.

The maximum peak differential signal on Channel V1 should

be less than ±30 mV (21 mV rms for a pure sinusoidal signal)

for specified operation.

30mV

–

30mV

VCM

DIFFERENTIAL INPUT

±30mV MAX PEAK

COMMON-MODE

±6.25mV MAX

V1P

V1N

VCM

AGND

05331-007

Figure 18. Maximum Signal Levels, Channel V1

Figure 18 shows the maximum signal levels on V1P and V1N.

The maximum differential voltage is ±30 mV. The differential

voltage signal on the inputs must be referenced to a common

mode, such as AGND. The maximum common-mode signal is

±6.25 mV.

Channel V2 (Voltage Channel)

The output of the line voltage sensor is connected to the device

at this analog input. Channel V2 is a fully differential voltage

input with a maximum peak differential signal of ±165 mV.

Figure 19 shows the maximum signal levels that can be

connected to the ADE7768 Channel V2.

+165mV

–165mV

DIFFERENTIAL INPUT

±165mV MAX PEAK

COMMON-MODE

±25mV MAX

V2P

V2N

AGND

05331-008

Figure 19. Maximum Signal Levels, Channel V2

Channel V2 is usually driven from a common-mode voltage,

that is, the differential voltage signal on the input is referenced

to a common mode (usually AGND). The analog inputs of the

ADE7768 can be driven with common-mode voltages of up to

25 mV with respect to AGND. However, best results are

achieved using a common mode equal to AGND.

ADE7768

Rev. A | Page 12 of 20

Typical Connection Diagrams

Figure 20 shows a typical connection diagram for Channel V1.

A shunt is the current sensor selected for this example because

of its low cost compared to other current sensors, such as the

current transformer (CT). This IC is ideal for low current

meters.

V1P

V1N

±30mV

SHUNT

AGND

PHASE NEUTRAL

05331-009

Figure 20. Typical Connection for Channel V1

Figure 21 shows a typical connection for Channel V2. Typically,

the ADE7768 is biased around the phase wire, and a resistor

divider is used to provide a voltage signal that is proportional to

the line voltage. Adjusting the ratio of RA, RB, and RBF is also a

convenient way of carrying out a gain calibration on a meter.

V2P

V2N

PHASENEUTRAL

±165mV

>> R

+ R

05331-010

Figure 21. Typical Connections for Channel V2

POWER SUPPLY MONITOR

The ADE7768 contains an on-chip power supply monitor.

The power supply (VDD) is continuously monitored by the

ADE7768. If the supply is less than 4 V, the ADE7768 becomes

inactive. This is useful to ensure proper device operation at

power-up and power-down. The power supply monitor has

built-in hysteresis and filtering, which provide a high degree

of immunity to false triggering from noisy supplies.

In Figure 22, the trigger level is nominally set at 4 V. The toler-

ance on this trigger level is within ±5%. The power supply and

decoupling for the part should be such that the ripple at VDD

does not exceed 5 V ± 5%, as specified for normal operation.

TIME

INACTIVE ACTIVE INACTIVE

INTERNAL

CTIVATION

05331-011

Figure 22. On-Chip Power Supply Monitor

HPF and Offset Effects

Figure 23 shows the effect of offsets on the real power calcula-

tion. As can be seen, offsets on Channel V1 and Channel V2

contribute a dc component after multiplication. Because this dc

component is extracted by the LPF and used to generate the real

power information, the offsets contribute a constant error to the

real power calculation. This problem is easily avoided by the

built-in HPF in Channel V1. By removing the offsets from at

least one channel, no error component can be generated at dc

by the multiplication. Error terms at the line frequency (ω) are

removed by the LPF and the digital-to-frequency conversion

(see the Digital-to-Frequency Conversion section).

Equation 6 shows how the power calculation is affected by the

dc offsets in the current and voltage channels.

(

)()

}cos{}cos{ OSOS ItIVtV +ω

(6)

() ()

tVItIVIV

OSOSOSOS ω×+ω×+×+

=coscos

()

IV ω×

+2cos

DC COMPONENT (INCLUDING ERROR TERM)

IS EXTRACTED BY THE LPF FOR REAL

POWER CALCULATION

× V

× I

V× I

0FREQUENCY (RAD/s)

05331-012

Figure 23. Effect of Channel Offset on the Real Power Calculation

The HPF in Channel V1 has an associated phase response that

is compensated for on chip. Figure 24 and Figure 25 show the

phase error between channels with the compensation network

activated. The ADE7768 is phase compensated up to 1 kHz as

shown. This ensures correct active harmonic power calculation

even at low power factors.

FREQUENCY (Hz)

0.30

PHASE (Degrees)

0.25

0.20

0.15

0.10

0.05

–0.05

–0.100 100 200 300 400 500 600 700 800 900 1000

05331-013

Figure 24. Phase Error Between Channels (0 Hz to 1 kHz)

ADE7768

Rev. A | Page 13 of 20

FREQUENCY (Hz)

0.30

PHASE (Degrees)

0.25

0.20

0.15

0.10

0.05

–0.05

–0.1040 45 50 55 60 65 70

05331-014

Figure 25. Phase Error Between Channels (40 Hz to 70 Hz)

Digital-to-Frequency Conversion

As previously described, the digital output of the low-pass filter

after multiplication contains the positive-only real power

information. However, because this LPF is not an ideal brick

wall filter implementation, the output signal also contains

attenuated components at the line frequency and its harmonics,

that is, cos(hωt) where h = 1, 2, 3, ... and so on.

The magnitude response of the filter is given by

()

45.4

= (7)

For a line frequency of 50 Hz, this gives an attenuation of

the 2ω (100 Hz) component of approximately 22 dB. The

dominating harmonic is twice the line frequency (2ω) due to

the instantaneous power calculation.

Figure 26 shows the instantaneous positive-only real power

signal at the output of the LPF that still contains a significant

amount of instantaneous power information, that is, cos(2ωt).

This signal is then passed to the digital-to-frequency converter

where it is compared to 0 and only positive real power is inte-

grated (accumulated) over time to produce an output frequency.

The accumulation of the signal suppresses or averages out any

non-dc components in the instantaneous positive-only real

power signal. The average value of a sinusoidal signal is 0. Thus,

the frequency generated by the ADE7768 is proportional to the

average positive-only real power. Figure 26 shows the digital-to-

frequency conversion for steady load conditions, that is, the

constant voltage and current.

DIGITAL-TO-

FREQUENCY

DIGITAL-TO-

FREQUENCY

MULTIPLIER

TIME

FREQUENCY FREQUENCY

0FREQUENCY (RAD/s)

ω2ω

COS (2ω)

ATTENUATED BY LPF

V× I

LPF TO EXTRACT

REAL POWER

(DC TERM)

INSTANTANEOUS REAL POWER SIGNAL

(FREQUENCY DOMAIN)

LPF

05331-015

≥0

Figure 26. Positive-Only, Real Power-to-Frequency Conversion

In Figure 26, the frequency output CF varies over time, even

under steady load conditions. This frequency variation is

primarily due to the cos(2ωt) component in the instantaneous

positive-only real power signal. The output frequency on CF

can be up to 2048 times higher than the frequency on F1 and

F2. This higher output frequency is generated by accumulating

the instantaneous positive-only real power signal over a much

shorter time while converting it to a frequency. This shorter

accumulation period means less averaging of the cos(2ωt)

component. Consequently, some of this instantaneous power

signal passes through the digital-to-frequency conversion. This

is not a problem in the application. Where CF is used for

calibration purposes, the frequency should be averaged by the

frequency counter, which removes any ripple. If CF is used to

measure energy, such as in a microprocessor-based application,

the CF output should also be averaged to calculate power.

Because the F1 and F2 outputs operate at a much lower

frequency, much more averaging of the instantaneous positive-

only real power signal is carried out. The result is a greatly

attenuated sinusoidal content and a virtually ripple-free

frequency output.

Connecting to a Microcontroller for Energy

Measurement

The easiest way to interface the ADE7768 to a microcontroller

is to use the CF high frequency output with the output

frequency scaling set to 2048 × F1, F2. This is done by setting

SCF = 0 and S0 = S1 = 1 (see Table 7). With full-scale ac

signals on the analog inputs, the output frequency on CF is

approximately 2.867 kHz. Figure 27 illustrates one scheme that

could be used to digitize the output frequency and carry out the

necessary averaging mentioned in the previous section.

ADE7768

Rev. A | Page 14 of 20

TIME

±10%

FREQUENCY

RIPPLE

AVERAGE

FREQUENCY

ADE7768

COUNTER

TIMER

MCU

05331-016

Figure 27. Interfacing the ADE7768 to an MCU

As shown in Figure 27, the frequency output CF is connected

to an MCU counter or port. This counts the number of pulses

in a given integration time, which is determined by an MCU

internal timer. The average power proportional to the average

frequency is given by

Time

Counter

PowerAverageFrequencyAverage == (8)

The energy consumed during an integration period is given by

)9(CounterTime

Time

Counter

TimePowerAverageEnergy =×=×=

For the purpose of calibration, this integration time could be

10 seconds to 20 seconds, to accumulate enough pulses to

ensure correct averaging of the frequency. In normal operation,

the integration time could be reduced to 1 second or 2 seconds,

depending, for example, on the required update rate of a

display. With shorter integration times on the MCU, the

amount of energy in each update may still have some small

amount of ripple, even under steady load conditions. However,

over a minute or more the measured energy has no ripple.

Power Measurement Considerations

Calculating and displaying power information always has some

associated ripple, which depends on the integration period used

in the MCU to determine average power and also on the load.

For example, at light loads, the output frequency may be 10 Hz.

With an integration period of 2 seconds, only about 20 pulses

are counted. The possibility of missing one pulse always exists,

because the ADE7768 output frequency is running asynchro-

nously to the MCU timer. This results in a 1-in-20 or 5% error

in the power measurement. When REVP is logic high, the

ADE7768 does not generate any pulse on F1, F2, and CF.

INTERNAL OSCILLATOR (OSC)

The nominal internal oscillator frequency is 450 kHz when

used with RCLKIN, with a nominal value of 6.2 kΩ. The

frequency outputs are directly proportional to the oscillator

frequency, thus RCLKIN must have low tolerance and low

temperature drift to ensure stability and linearity of the chip.

The oscillator frequency is inversely proportional to the

RCLKIN, as shown in Figure 28. Although the internal

oscillator operates when used with RCLKIN values between

5.5 kΩ and 20 kΩ, choosing a value within the range of the

nominal value, as shown in Figure 28, is recommended.

RESISTANCE (kΩ)

5.8 5.9 6.1 6.3 6.7

FREQUENCY (kHz)

420

430

440

450

460

480

470

490

6.0 6.2 6.4 6.5 6.6

410

400

05331-017

Figure 28. Effect of RCLKIN on Internal Oscillator Frequency (OSC)

TRANSFER FUNCTION

Frequency Outputs F1 and F2

The ADE7768 calculates the product of two voltage signals

(on Channel V1 and Channel V2) and then low-pass filters this

product to extract positive-only real power information. This

positive-only real power information is then converted to a

frequency. The frequency information is output on F1 and F2

in the form of active low pulses. The pulse rate at these outputs

is relatively low—for example, 0.175 Hz maximum for ac signals

with S0 = S1 = 0 (see Table 6). This means that the frequency at

these outputs is generated from positive-only real power

information accumulated over a relatively long period of time.

The result is an output frequency that is proportional to the

average positive-only real power. The averaging of the positive-

only real power signal is implicit to the digital-to-frequency

conversion. The output frequency or pulse rate is related to the

input voltage signals by the following equation:

75.494

REF

41rmsrms

FV2V1

Freq −

= (10)

where:

Freq is the output frequency on F1 and F2 (Hz).

V1rms is the differential rms voltage signal on Channel V1 (V).

V2rms is the differential rms voltage signal on Channel V2 (V).

VREF is the reference voltage (2.45 V ± 200 mV) (V).

F1–4 are one of four possible frequencies selected by using the

S0 and S1 logic inputs (see Table 5).

ADE7768

Rev. A | Page 15 of 20

Table 5. F1–4 Frequency Selection

S1 S0 OSC Relation1F1–4 at Nominal OSC (Hz)2

0 0 OSC/219 0.86

0 1 OSC/218 1.72

1 0 OSC/217 3.43

1 1 OSC/216 6.86

1 F1–4 is a binary fraction of the internal oscillator frequency.

2 Values are generated using the nominal frequency of 450 kHz.

Example

In this example, with ac voltages of ±30 mV peak applied to

V1 and ±165 mV peak applied to V2, the expected output

frequency is calculated as follows:

F1–4 = OSC/219 Hz, S0 = S1 = 0

V1rms = 0.03/√2 V

V2rms = 0.165/√2 V

VREF = 2.45 V (nominal reference value)

Note that if the on-chip reference is used, actual output

frequencies may vary from device to device due to the

reference tolerance of ±200 mV.

175.0204.0

45.222

165.003.075.494

2=×=

××

×××

Freq (11)

Table 6. Maximum Output Frequency on F1 and F2

S1 S0 OSC Relation Max Frequency1 or AC Inputs (Hz)

0 0 0.204 × F1 0.175

0 1 0.204 × F2 0.35

1 0 0.204 × F3 0.70

1 1 0.204 × F4 1.40

1 Values are generated using the nominal frequency of 450 kHz.

Frequency Output CF

The pulse output CF (calibration frequency) is intended for

calibration purposes. The output pulse rate on CF can be up

to 2048 times the pulse rate on F1 and F2. The lower the F1–4

frequency selected, the higher the CF scaling (except for the

high frequency mode SCF = 0, S1 = S0 = 1). Table 7 shows

how the two frequencies are related, depending on the states

of the logic inputs S0, S1, and SCF. Due to its relatively high

pulse rate, the frequency at the CF logic output is proportional

to the instantaneous positive-only real power. As with F1 and

F2, CF is derived from the output of the low-pass filter after

multiplication. However, because the output frequency is

high, this positive-only real power information is accumulated

over a much shorter time. Therefore, less averaging is carried

out in the digital-to-frequency conversion. With much less

averaging of the positive-only real power signal, the CF output

is much more responsive to power fluctuations (see the signal

processing block diagram in Figure 15).

Table 7. Maximum Output Frequency on CF

SCF S1 S0 CF Max for AC Signals (Hz) 1

1 0 0 128 × F1, F2 = 22.4

0 0 0 64 × F1, F2 = 11.2

1 0 1 64 × F1, F2 = 22.4

0 0 1 32 × F1, F2 = 11.2

1 1 0 32 × F1, F2 = 22.4

0 1 0 16 × F1, F2 = 11.2

1 1 1 16 × F1, F2 = 22.4

0 1 1 2048 × F1, F2 = 2.867 kHz

1 Values are generated using the nominal frequency of 450 kHz.

SELECTING A FREQUENCY FOR AN ENERGY

METER APPLICATION

As shown in Table 5, the user can select one of four frequencies.

This frequency selection determines the maximum frequency

on F1 and F2. These outputs are intended for driving an energy

different output frequencies can be selected, the available

frequency selection has been optimized for a meter constant

of 100 imp/kWh with a maximum current of between 10 A

and 120 A. Table 8 shows the output frequency for several

maximum currents (IMAX) with a line voltage of 220 V. In all

cases, the meter constant is 100 imp/kWh.

Table 8. F1 and F2 Frequency at 100 imp/kWh

IMAX (A) F1 and F2 (Hz)

12.5 0.076

25.0 0.153

40.0 0.244

60.0 0.367

80.0 0.489

120.0 0.733

The F1–4 frequencies allow complete coverage of this range of

output frequencies (F1, F2). When designing an energy meter,

the nominal design voltage on Channel V2 (voltage) should be

set to half-scale to allow calibration of the meter constant. The

current channel should also be no more than half scale when

the meter sees maximum load. This allows overcurrent signals

and signals with high crest factors to be accommodated. Table 9

shows the output frequency on F1 and F2 when both analog

inputs are half scale. The frequencies in Table 9 align very well

with those in Table 8 for maximum load.

Table 9. F1 and F2 Frequency with Half-Scale AC Inputs

S1 S0 F1–4 (Hz)

Frequency on F1 and F2—

CH1 and CH2 Half-Scale AC Input1

0 0 0.86 0.051 × F1 0.044 Hz

0 1 1.72 0.051 × F2 0.088 Hz

1 0 3.43 0.051 × F3 0.176 Hz

1 1 6.86 0.051 × F4 0.352 Hz

1 Values are generated using the nominal frequency of 450 kHz.

ADE7768

Rev. A | Page 16 of 20

When selecting a suitable F1–4 frequency for a meter design, the

frequency output at IMAX (maximum load) with a meter constant

of 100 imp/kWh should be compared with Column 4 of

Table 9. The closest frequency in Table 9 determines the best

choice of frequency (F1–4). For example, if a meter with a max-

imum current of 25 A is being designed, the output frequency

on F1 and F2 with a meter constant of 100 imp/kWh is 0.153 Hz

at 25 A and 220 V (from Table 8). In Table 9, the closest fre-

quency to 0.153 Hz in Column 4 is 0.176 Hz. Therefore, as

shown in Table 5, F3 (3.43 Hz) is selected for this design.

Frequency Outputs

Figure 2 shows a timing diagram for the various frequency

outputs. The F1 and F2 outputs are the low frequency outputs

that can be used to directly drive a stepper motor or electro-

mechanical impulse counter. The F1 and F2 outputs provide

two alternating low frequency pulses. The F1 and F2 pulse

widths (t1) are set such that if they fall below 240 ms (0.24 Hz),

they are set to half of their period. The maximum output

frequencies for F1 and F2 are shown in Table 6.

The high frequency CF output is intended for communications

and calibration purposes. CF produces a 90-ms-wide active

high pulse (t4) at a frequency proportional to active power. The

CF output frequencies are given in Table 7. As with F1 and F2,

if the period of CF (t5) falls below 180 ms, the CF pulse width is

set to half the period. For example, if the CF frequency is 20 Hz,

the CF pulse width is 25 ms.

When high frequency mode is selected (SCF = 0, S1 = S0 = 1),

the CF pulse width is fixed at 35 μs. Therefore, t4 is always 35 μs,

regardless of output frequency on CF.

NO-LOAD THRESHOLD

The ADE7768 includes a no-load threshold and start-up

current feature that eliminates any creep effects in the meter.

The ADE7768 is designed to issue a minimum output

frequency. Any load generating a frequency lower than this

minimum frequency does not cause a pulse to be issued on F1,

F2, or CF. The minimum output frequency is given as 0.00244%

for each of the F1–4 frequency selections (see Table 5).

For example, for an energy meter with a meter constant of

100 imp/kWh on F1, F2 using F3 (3.43 Hz), the minimum

output frequency at F1 or F2 would be 0.00244% of 3.43 Hz or

8.38 × 10–5 Hz. This would be 2.68 × 10–3 Hz at CF (32 × F1 Hz)

when SCF = S0 = 1, S1 = 0. In this example, the no-load

threshold would be equivalent to 3 W of load or a start-up

current of 13.72 mA at 220 V. Compare this value to the

IEC62053-21 specification which states that the meter must

start up with a load equal to or less than 0.4% Ib. For a 5 A (Ib)

meter, 0.4% of Ib is equivalent to 20 mA.

NEGATIVE POWER INFORMATION

The ADE7768 detects when the current and voltage channels

have a phase shift greater than 90°. This mechanism can detect

an incorrect meter connection or the generation of negative

power. The REVP pin output goes active high when negative

power is detected and active low if positive power is detected.

The REVP pin output changes state as a pulse is issued on CF.

EVALUATION BOARD AND REFERENCE DESIGN

BOARD

An evaluation board can be used to verify the functionality and

the performance of the ADE7768. Download documentation

for the board from http://www.analog.com/ADE7768.

In addition, the reference design board ADE7768ARN-REF

and Application Note AN-679 can be used in the design

of a low cost watt-hour meter that surpasses IEC62053-21

accuracy specifications. Download the application note from

http://www.analog.com/ADE7768.

ADE7768

Rev. A | Page 17 of 20

OUTLINE DIMENSIONS

CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS

(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR

REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN

COMPLIANT TO JEDEC STANDARDS MS-012-AC

16 9

4.00 (0.1575)

3.80 (0.1496)

10.00 (0.3937)

9.80 (0.3858)

1.27 (0.0500)

BSC

6.20 (0.2441)

5.80 (0.2283)

SEATING

PLANE

0.25 (0.0098)

0.10 (0.0039)

0.51 (0.0201)

0.31 (0.0122)

1.75 (0.0689)

1.35 (0.0531)

8°

0°

0.50 (0.0197)

0.25 (0.0098)

1.27 (0.0500)

0.40 (0.0157)

0.25 (0.0098)

0.17 (0.0067)

COPLANARITY

0.10

× 45°

Figure 29. 16-Lead Standard Small Outline Package [SOIC_N]

Narrow Body (R-16)

Dimensions shown in millimeters and (inches)

ORDERING GUIDE

Model Temperature Range Package Description Package Option

ADE7768AR −40°C to +85°C 16-Lead Standard Small Outline Package [SOIC_N] R-16

ADE7768AR-RL −40°C to +85°C 16-Lead Standard Small Outline Package [SOIC_N] REEL R-16

ADE7768ARZ1−40°C to +85°C 16-Lead Standard Small Outline Package [SOIC_N] R-16

ADE7768ARZ-RL1 −40°C to +85°C 16-Lead Standard Small Outline Package [SOIC_N] REEL R-16

ADE7768AR-REF Reference Board

EVAL-ADE7768EB Evaluation Board

1 Z = Pb-free part.

ADE7768

Rev. A | Page 18 of 20

NOTES

ADE7768

Rev. A | Page 19 of 20

NOTES

ADE7768

Rev. A | Page 20 of 20

NOTES

registered trademarks are the property of their respective owners.

D05331–0–8/05(A)