LTC2066/LTC2067 10A Supply Current, Low IB, Zero-Drift Operational Amplifier FEATURES DESCRIPTION Low Supply Current: 10A Maximum (per Amplifier) nn Offset Voltage: 5V Maximum nn Offset Voltage Drift: 0.02V/C Maximum nn Input Bias Current: nn 5pA Typical nn 50pA Maximum, -40C to 85C nn 150pA Maximum, -40C to 125C nn Integrated EMI Filter (90dB Rejection at 1.8GHz) nn Shutdown Current: 170nA Maximum (per Amplifier) nn Rail-to-Rail Input and Output nn 1.7V to 5.25V Operating Supply Range nn A VOL: 140dB Typical nn Low-Charge Power-Up for Duty Cycled Applications nn Specified Temperature Ranges: nn -40C to 85C nn -40C to 125C nn SC70, TSOT-23, MS8 and DFN Packages The LTC(R)2066/LTC2067 are single and dual low power, zero-drift, 100kHz amplifiers. The LTC2066/LTC2067 enable high resolution measurement at extremely low power levels. nn APPLICATIONS Signal Conditioning in Wireless Mesh Networks Portable Instrumentation Systems nn Low-Power Sensor Conditioning nn Gas Detection nn Temperature Measurement nn Medical Instrumentation nn Energy Harvesting Applications nn Low Power Current Sensing nn nn Typical supply current is 7.5A per amplifier with a maximum of 10A. The available shutdown mode has been optimized to minimize power consumption in duty-cycled applications and features low charge loss during powerup, reducing total system power. The LTC2066/LTC2067's self-calibrating circuitry results in very low input offset (5V max) and offset drift (0.02V/C). The maximum input bias current is only 35pA and does not exceed 150pA over the full specified temperature range. The extremely low input bias current of the LTC2066/LTC2067 allows the use of high value power-saving resistors in the feedback network. With its ultralow quiescent current and outstanding precision, the LTC2066/LTC2067 can serve as a signal chain building block in portable, energy harvesting and wireless sensor applications. The LTC2066 is available in 6-lead SC70 and 5-lead TSOT23 packages. The LTC2067 is available in 8-lead MSOP and 10-lead DFN packages. These devices are fully specified over the -40C to 85C and -40C to 125C temperature ranges. All registered trademarks and trademarks are the property of their respective owners. TYPICAL APPLICATION Output Voltage vs Sense Current 2.5 Precision Micropower Low Side Current Sense VIN ISENSE 100A TO 250mA 3.3V - LOAD 10k* 0.1% 100m 0.1% 1 1M 0.1% LTC2066 VOUT = 10 * ISENSE 1mV TO 2.5V + 2066 TA01a OUTPUT VOLTAGE, VOUT (V) 10k 0.1% *RESISTOR CANCELS OUT PARASITIC SEEBECK EFFECT VOLTAGE 0.1 0.01 0.001 0.1 1 10 ISENSE (mA) 100 250 2066 TA01b Rev A Document Feedback For more information www.analog.com 1 LTC2066/LTC2067 ABSOLUTE MAXIMUM RATINGS (Note 1) Total Supply Voltage (V+ to V-).................................5.5V Differential Input Current (+IN to -IN) (Note 2)..... 10mA Differential Input Voltage (+IN to -IN).......................5.5V Input Voltage +IN, -IN, SHDN....................(V-) - 0.3V to (V+) + 0.3V Input Current +IN, -IN, SHDN (Note 2)................................... 10mA Output Short-Circuit Duration (Note 3)...........................................Thermally Limited Operating and Specified Temperature Range (Note 4) LTC2066I/LTC2067I..............................-40C to 85C LTC2066H/LTC2067H......................... -40C to 125C Maximum Junction Temperature........................... 150C Storage Temperature Range................... -65C to 150C PIN CONFIGURATION LTC2066 TOP VIEW 6 V+ +IN 1 + - V- 2 TOP VIEW 5 SHDN -IN 3 V 4 OUT -2 LTC2067 TOP VIEW 8 V+ A B 4 -IN S5 PACKAGE 5-LEAD PLASTIC TSOT-23 JA = 215C/W (Note 5) LTC2067 1 2 3 4 + +IN 3 SC6 PACKAGE 6-LEAD PLASTIC SC70 JA = 265C/W (Note 5) OUTA -INA +INA V- 5 V+ OUT 1 - LTC2066 7 OUTB 6 -INB 5 +INB MS8 PACKAGE 8-LEAD PLASTIC MSOP JA = 163C/W, JC = 40C/W (Note 5) TOP VIEW OUTA 1 -INA 2 +INA 3 V- 4 NC 5 10 V+ A 9 OUTB 11 B 8 -INB 7 +INB 6 SHDN DD PACKAGE 10-LEAD (3mm x 3mm) PLASTIC DFN JA = 43C/W, JC = 5.5C/W (Note 5) EXPOSED PAD (PIN 11) IS CONNECTED TO V- (PIN 4) (PCB CONNECTION OPTIONAL) ORDER INFORMATION TAPE AND REEL (MINI) TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LTC2066ISC6#TRMPBF LTC2066ISC6#TRPBF LHDB 6-Lead Plastic SC70 -40C to 85C LTC2066HSC6#TRMPBF LTC2066HSC6#TRPBF LHDB 6-Lead Plastic SC70 -40C to 125C LTC2066IS5#TRMPBF LTC2066IS5#TRPBF LTHCZ 5-Lead Plastic TSOT-23 -40C to 85C LTC2066HS5#TRMPBF LTC2066HS5#TRPBF LTHCZ 5-Lead Plastic TSOT-23 -40C to 125C LTC2067IMS8#TRMPBF LTC2067IMS8#TRPBF LTHDC 8-Lead Plastic MSOP -40C to 85C LTC2067HMS8#TRMPBF LTC2067HMS8#TRPBF LTHDC 8-Lead Plastic MSOP -40C to 125C LTC2067IDD#TRMPBF LTC2067IDD#TRPBF LHDD 10-Lead (3mm x 3mm) Plastic DFN -40C to 85C LTC2067HDD#TRMPBF LTC2067HDD#TRPBF LHDD 10-Lead (3mm x 3mm) Plastic DFN -40C to 125C Contact the factory for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. Parts ending with PBF are RoHS and WEEE compliant. Tape and reel specifications. Some packages are available in 500 unit reels through designated sales channels with #TRMPBF suffix. 2 Rev A For more information www.analog.com LTC2066/LTC2067 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. Unless otherwise noted, VS = 1.8V, VCM = VOUT = VS/2, VSHDN = 1.8V, RL to VS/2. SYMBOL PARAMETER CONDITIONS VOS VS = 1.7V Input Offset Voltage (Note 6) TYP MAX UNITS 1 l 5 10 V V l l 0.03 0.05 VOS/T Input Offset Voltage Drift (Note 6) IB Input Bias Current (Note 7) 2 pA IOS Input Offset Current (Note 7) 4 pA in Input Noise Current Spectral Density f 100Hz 35 fA/Hz en Input Noise Voltage Spectral Density f 100Hz 90 nV/Hz en P-P Input Noise Voltage DC to 10Hz 1.9 VP-P CIN Input Capacitance Differential Common Mode 3.3 3.5 pF pF VCMR Input Voltage Range Guaranteed by CMRR CMRR PSRR Common Mode Rejection Ratio (Note 8) Power Supply Rejection Ratio -40C to 85C -40C to 125C MIN l (V-) - 0.1 VCM RL = 499k 103 100 123 l dB dB VS = 1.7V to 5.25V RL = 499k 108 106 126 l dB dB = (V-) - 0.1V to (V+) + 0.1V (V+) + 0.1 V/C V/C V AVOL Open Loop Gain VOUT = (V-) + 0.1V to (V+) - 0.1V, RL = 499k 135 dB VOL Output Voltage Swing Low (VOUT - V-) RL = 499k 0.05 mV RL = 10k 3 l VOH Output Voltage Swing High (V+ - VOUT) RL = 499k 0.1 RL = 10k 4.5 l ISC Output Short Circuit Current 10 20 Sourcing mV mV mV 10 50 mV mV 5.8 4 7.5 l mA mA 10.4 5 13 l mA mA Sinking SR Slew Rate AV = +1 17.5 V/ms GBW Gain Bandwidth Product RL = 499k 100 kHz tON Power-Up Time 0.4 ms fC Internal Chopping Frequency 25 kHz VS Supply Voltage Range Guaranteed by PSRR IS Supply Current per Amplifier No Load -40C to 85C -40C to 125C l l In Shutdown (SHDN = V-) -40C to 85C -40C to 125C l l l VH SHDN Pin Threshold, Logic High (Referred to V-) l VL SHDN Pin Threshold, Logic Low (Referred to V-) l ISHDN SHDN Pin Current VSHDN = 0V l 1.7 5.25 V 7.4 10 12.5 20 A A A 90 170 250 500 nA nA nA 1.0 -150 V 0.65 V -20 nA Rev A For more information www.analog.com 3 LTC2066/LTC2067 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. Unless otherwise noted, VS = 5V, VCM = VOUT = VS/2, VSHDN = 5V, RL to VS/2. SYMBOL PARAMETER CONDITIONS VOS VS = 5.25V Input Offset Voltage (Note 6) VOS/T Input Offset Voltage Drift (Note 6) IB Input Bias Current IOS Input Offset Current MIN TYP MAX UNITS 1 l 5 10 V V -40C to 85C -40C to 125C l l 0.02 0.04 V/C V/C -40C to 85C -40C to 125C 5 l l 35 50 150 pA pA pA -40C to 85C -40C to 125C 10 l l 35 50 150 pA pA pA in Input Noise Current Spectral Density f 100Hz 35 fA/Hz en Input Noise Voltage Spectral Density f 100Hz 80 nV/Hz en P-P Input Noise Voltage DC to 10Hz 1.7 VP-P CIN Input Capacitance Differential Common Mode 3.3 3.5 pF pF VCMR Input Voltage Range Guaranteed by CMRR CMRR PSRR Common Mode Rejection Ratio Power Supply Rejection Ratio l (V-) - 0.1 VCM RL = 499k 111 108 134 l dB dB VS = 1.7V to 5.25V RL = 499k 108 106 126 l dB dB 66 79 90 76 dB dB dB dB 140 dB dB = (V-) - 0.1V to (V+) + 0.1V EMIRR EMI Rejection Ratio VRF = 100mVPK EMIRR = 20 * log(VRF/VOS) f = 400MHz f = 900MHz f = 1800MHz f = 2400MHz AVOL Open Loop Gain VOUT = (V-) + 0.1V to (V+) - 0.1V, RL = 499k l VOL Output Voltage Swing Low (VOUT - V-) 112 110 (V+) + 0.1 RL = 499k 0.1 RL = 10k 5.5 l VOH Output Voltage Swing High (V+ - VOUT) RL = 499k 7 l ISC Output Short Circuit Current mV 15 20 0.15 RL = 10k Sourcing V mV mV mV 15 20 mV mV 30 16 51 l mA mA 20 5 48 l mA mA Sinking SR Slew Rate AV = +1 17.5 V/ms GBW Gain Bandwidth Product RL = 499k 100 kHz tON Power-Up Time 0.4 ms fC Internal Chopping Frequency VS Supply Voltage Range Guaranteed by PSRR l IS Supply Current per Amplifier No Load -40C to 85C -40C to 125C l l In Shutdown (SHDN = V-) -40C to 85C -40C to 125C l l 4 25 1.7 kHz 5.25 V 7.5 10 12.5 20 A A A 90 170 250 500 nA nA nA Rev A For more information www.analog.com LTC2066/LTC2067 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. Unless otherwise noted, VS = 5V, VCM = VOUT = VS/2, VSHDN = 5V, RL to VS/2. SYMBOL PARAMETER CONDITIONS MIN VH SHDN Pin Threshold, Logic High (Referred to V-) l VL SHDN Pin Threshold, Logic Low (Referred to V-) l ISHDN SHDN Pin Current VSHDN = 0V Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The inputs are protected by two series connected ESD protection diodes to each power supply. The input current should be limited to less than 10mA. The input voltage should not exceed 300mV beyond the power supply. Note 3: A heat sink may be required to keep the junction temperature below the absolute maximum rating when the output is shorted indefinitely. Note 4: The LTC2066I/LTC2067I is guaranteed to meet specified performance from -40C to 85C. The LTC2066H/LTC2067H is guaranteed to meet specified performance from -40C to 125C. l TYP MAX 1.8 -150 UNITS V 0.8 V -20 nA Note 5: Thermal resistance varies with the amount of PC board metal connected to the package. The specified values are for short traces connected to the leads. Note 6: These parameters are guaranteed by design. Thermocouple effects preclude measurements of these voltage levels during automated testing. VOS is measured to a limit determined by test equipment capability. Note 7: Input Bias Current, Input Offset Current and Open Loop Gain are only production tested at 5V. Input Bias Current and Input Offset Current at 1.8V are expected to meet 5V specifications. Note 8: Minimum specifications for these parameters are limited by noise and the capabilities of the automated test system. Rev A For more information www.analog.com 5 LTC2066/LTC2067 TYPICAL PERFORMANCE CHARACTERISTICS 80 70 260 TYPICAL UNITS 70 VS = 5V 60 NUMBER OF AMPLIFIERS 50 40 30 20 40 30 20 10 0 0 3 4 5 2066 G01 Input Offset Voltage Drift Distribution (H-Grade) 120 80 60 40 -5 -4 -3 -2 -1 0 1 VOS (V) 0 5 60 50 40 30 20 0 5 120 40 5 4 3 100 80 60 40 20 0 5 0 10 15 20 25 30 35 40 45 50 VOS TC (nV/C) 6 1 2 VOS (V) 1 0 -1 0 -2 -2 -4 -3 -3 -6 -4 -4 -8 -5 -0.5 0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 5.5 VCM (V) -5 -0.5 0.5 5 TYPICAL UNITS VCM = VS/2 TA = 25C 8 4 0 10 15 20 25 30 35 40 45 50 VOS TC (nV/C) 10 5 TYPICAL UNITS VS = 1.8V TA = 25C -2 6 5 Input Offset Voltage vs Supply Voltage 2 2066 G07 0 2066 G06 2 -1 260 TYPICAL UNITS VS = 1.8V TA = -40C TO 85C 2066 G05 5 TYPICAL UNITS VS = 5V TA = 25C 10 15 20 25 30 35 40 45 50 VOS TC (nV/C) 2066 G03 Input Offset Voltage vs Input Common Mode Voltage 0 5 Input Offset Voltage Drift Distribution (I-Grade) 60 0 10 15 20 25 30 35 40 45 50 VOS TC (nV/C) 0 2066 G02 20 VOS (V) VOS (V) 3 4 80 Input Offset Voltage vs Input Common Mode Voltage 4 3 100 2066 G04 5 2 260 TYPICAL UNITS VS = 5V TA = -40C TO 85C 120 20 0 70 10 140 NUMBER OF AMPLIFIERS NUMBER OF AMPLIFIERS 100 80 Input Offset Voltage Drift Distribution (I-Grade) 260 TYPICAL UNITS VS = 1.8V TA = -40C TO 125C 260 TYPICAL UNITS VS = 5V TA = -40C TO 125C 90 50 10 2 100 260 TYPICAL UNITS VS = 1.8V NUMBER OF AMPLIFIERS NUMBER OF AMPLIFIERS 60 -5 -4 -3 -2 -1 0 1 VOS (V) Input Offset Voltage Drift Distribution (H-Grade) Input Offset Voltage Distribution NUMBER OF AMPLIFIERS Input Offset Voltage Distribution 1 VCM (V) 1.5 2 2.5 2066 G08 -10 1 1.5 2 2.5 3 3.5 VS (V) 4 4.5 5 5.5 2066 G09 Rev A For more information www.analog.com LTC2066/LTC2067 TYPICAL PERFORMANCE CHARACTERISTICS Input Bias Current Distribution 1500 6276 TYPICAL UNITS VS = 5V TA = 25C 6276 TYPICAL UNITS VS = 1.8V TA = 25C 1250 NUMBER OF AMPLIFIERS 1250 NUMBER OF AMPLIFIERS Input Bias Current Distribution 1500 1000 750 500 1000 250 750 500 250 0 -20 -16 -12 -8 -4 0 4 8 12 16 20 INPUT BIAS CURRENT (pA) 0 -10 -8 -6 -4 -2 0 2 4 6 INPUT BIAS CURRENT (pA) 2066 G10 Input Bias Current vs Input Common Mode Voltage 20 VS = 5V 10 15 IB (-IN) 10 IB (+IN) 5 IB (+IN) IB (pA) IB (pA) VS = 5V TA = 25C 15 20 5 0 IB (-IN) -5 0 -10 -5 -15 -10 -50 -25 0 25 50 75 TEMPERATURE (C) 100 -20 -0.5 0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 5.5 VCM (V) 125 2066 G13 2066 G12 Input Bias Current vs Input Common Mode Voltage 10 8 Input Bias Current vs Supply Voltage 10 VS = 1.8V TA = 25C 6 4 IB (pA) 0 IB (+IN) -2 IB (+IN) 4 IB (-IN) 2 2 0 -4 -6 -6 -8 IB (-IN) -2 -4 -10 -0.5 VCM = VS/2 TA = 25C 8 6 IB (pA) 10 2066 G11 Input Bias Current vs Temperature 25 8 -8 0 0.5 1 1.5 VCM (V) 2 2.5 -10 1 1.5 2066 G14 2 2.5 3 3.5 VS (V) 4 4.5 5 5.5 2066 G15 Rev A For more information www.analog.com 7 LTC2066/LTC2067 TYPICAL PERFORMANCE CHARACTERISTICS 10 Input Offset and Average Current vs Input Common Mode Voltage 5 VS = 5V TA = 25C 8 3 IB (pA) IB (pA) 0 -2 -4 1 0 -1 -2 IOS -6 IAVG 2 IAVG 2 VS = 1.8V TA = 25C 4 6 4 IOS -3 -4 -8 -5 -0.5 -10 -0.5 0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 5.5 VCM (V) 0 0.5 1 1.5 VCM (V) 2 Input Referred Voltage Noise Density 1k VS = 0.9V VS = 2.5V 1 10 100 1k FREQUENCY (Hz) 10k VS = 5V VCM = 2.5V 40 1 10 100 1k 10k 100k FREQUENCY (Hz) 120 0 0.1 -PSRR 20 1 10 100 1k 10k 100k 1M 10M FREQUENCY (Hz) 2066 G22 1 RF FREQUENCY (GHz) 4 2066 G21 0 70 50 40 30 20 10 0 AV = +100 AV = +10 AV = +1 -10 AV = -1 -20 10 100 1k 10k FREQUENCY (Hz) 100k 1M 2066 G23 VS = 5V RL = 499k RF = 1M AV = +1000 60 CLOSED LOOP GAIN (dB) +PSRR 60 40 20 0.1 Closed Loop Gain vs Frequency 80 PSRR (dB) CMRR (dB) VS = 5V 40 20 0.05 1M VS = 5V RL = 499k 100 VS = 1.8V 60 100 Power Supply Rejection Ratio vs Frequency RL = 499k 60 80 2066 G20 120 80 VIN = 100mVPK EMIRR = 20log(100mV/VOS) 1k 10 0.1 100k EMI Rejection vs Frequency 100 Common Mode Rejection Ratio vs Frequency 100 2066 G18 120 2066 G19 140 TIME (1s/DIV) EMIRR (dB) CURRENT NOISE DENSITY (fA/Hz) VOLTAGE NOISE DENSITY (nV/Hz) 10k 10 0.1 2.5 Input Referred Current Noise Density 10k 100 VS = 2.5V 2066 G17 2066 G16 8 DC to 10Hz Voltage Noise INPUT REFERRED VOLTAGE NOISE (0.5V/DIV) Input Offset and Average Current vs Input Common Mode Voltage -30 10 100 1k 10k 100k FREQUENCY (Hz) 1M 10M 2066 G24 Rev A For more information www.analog.com LTC2066/LTC2067 TYPICAL PERFORMANCE CHARACTERISTICS Open Loop Gain and Phase vs Frequency Open Loop Gain and Phase vs Frequency 140 100 -90 100 80 -135 80 60 -180 60 40 -225 20 -270 GAIN 0 -20 -40 CL = 0pF CL = 47pF CL = 100pF -60 1m 10m100m 1 GAIN (dB) PHASE VS = 1.8V RL = 499k 120 PHASE () GAIN (dB) 120 -360 -20 -405 -40 -450 10 100 1k 10k 100k 1M 10M FREQUENCY (Hz) -120 0 -210 CL = 0pF CL = 47pF CL = 100pF -60 1m 10m 100m 1 -240 -270 10 100 1k 10k 100k 1M 10M FREQUENCY (Hz) 150 -40 OPEN LOOP GAIN (dB) CROSSTALK (dB) -20 -60 -80 -100 -120 -140 100 B to A A to B 1k 10k 100k FREQUENCY (Hz) 2066 G26 Shutdown Transient with Sinusoidal Input Open Loop Gain vs Load RL = 10k 1M VS = 5V 145 VSHDN 5V/DIV 140 IS 5A/DIV 135 VOUT, VIN 0.1V/DIV 130 125 120 400s/DIV 1 2066 G66 Shutdown Transient with Sinusoidal Input 10 RLOAD (k) 100 500 2066 G27 Enable Transient with Sinusoidal Input VSHDN 5V/DIV IS 5A/DIV VSHDN 2V/DIV IS 5A/DIV IS 5A/DIV VOUT, VIN 0.1V/DIV VOUT, VIN 0.2V/DIV VOUT, VIN 1V/DIV 400s/DIV VS = 0.9V AV = +1 2066 G28 VS = 2.5V AV = +1 Enable Transient with Sinusoidal Input VSHDN 2V/DIV -150 -180 2066 G25 LTC2067 Crosstalk vs Frequency -90 GAIN 20 0 -30 -60 PHASE 40 -315 0 PHASE () 0 VS = 5V RL = 499k -45 140 2066 G29 400s/DIV VS = 2.5V AV = +1 2066 G30 400s/DIV 2066 G31 VS = 0.9V AV = +1 Rev A For more information www.analog.com 9 LTC2066/LTC2067 TYPICAL PERFORMANCE CHARACTERISTICS Closed Loop Output Impedance vs Frequency 1M Output Impedance in Shutdown vs Frequency 1G VS = 5V AV = +1 100k 100M 10M 1k ZOUT () ZOUT () 10k 100 1M 100k 10 10k 1 0.1 VS = 5V AV = +1 10 100 1k 10k 100k FREQUENCY (Hz) 1M 1k 10M 10 100 1k 10k 100k FREQUENCY (Hz) AV = +1 VS = 2.5V VOUT = 2V -40 -60 -80 -100 -120 RL = 10k RL = 499k 20 100 FREQUENCY (Hz) 1k 2k Maximum Undistorted Output Amplitude vs Frequency Supply Current vs Supply Voltage 6 12.5 5 10.0 4 3 2 AV = +1 VS = 2.5V THD < -40dB RL = 499k 1 0 100 1k FREQUENCY (Hz) 2066 G35 10 9 8 7 6 5 -50 VS = 5V Supply Current vs SHDN Pin Voltage 60 40 30 20 10 -25 0 25 50 75 TEMPERATURE (C) 100 125 0 VS = 1.8V 14 50 12 125C 85C 25C -40C 10 8 6 4 2 0 0.5 1 1.5 2 2.5 3 3.5 4 SHDN PIN VOLTAGE (V) 4.5 2066 G37 10 16 125C 85C 25C -40C 70 IS PER AMPLIFIER (A) IS PER AMPLIFIER (A) 80 VS = 1.8V VS = 5V TA = 125C TA = 85C TA = 25C TA = -40C 2066 G36 Supply Current vs SHDN Pin Voltage Supply Current vs Temperature 11 5.0 0 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 VS (V) 10k 2066 G34 12 7.5 2.5 IS PER AMPLIFIER (A) TOTAL HARMONIC DISTORTION (dB) -20 10M 2066 G33 IS PER AMPLIFIER (A) THD vs Frequency MAXIMUM UNDISTORTED OUTPUT VOLTAGE (VP-P) 2066 G32 1M 5 2066 G38 0 0 0.2 0.4 0.6 0.8 1 1.2 1.4 1.6 1.8 SHDN PIN VOLTAGE (V) 2066 G39 Rev A For more information www.analog.com LTC2066/LTC2067 TYPICAL PERFORMANCE CHARACTERISTICS SHDN Pin Pull-Up Current vs SHDN Pin Voltage 20 VS = 5V 0 -10 -20 0 -20 -50 -40 -50 -60 -60 -70 -70 -80 -80 -90 -90 0 1 2 3 VSHDN (V) 4 5 -100 6 -1 0.5 1 1.5 -80 -50 2 100 250 200 150 100 10 125C 85C 25C -40C VS = 1.8V VS = 5V -25 0 25 50 75 TEMPERATURE (C) 100 0.1 0.01 125 0.1 2066 G44 Output Voltage Swing Low vs Load Current 4000 VS = 0.9V 125 VS = 2.5V 1 2066 G43 Output Voltage Swing High vs Load Current 100 1000 50 -50 0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 5.5 VS (V) 0 25 50 75 TEMPERATURE (C) Output Voltage Swing High vs Load Current 4000 100 50 -25 2066 G42 300 150 VS = 1.8V VS = 5V 2066 G41 350 200 1000 -60 Shutdown Supply Current vs Temperature 250 0 0 VSHDN (V) IS PER AMPLIFIER (nA) IS PER AMPLIFIER (nA) 300 -0.5 2066 G40 125C 85C 25C -40C 350 -50 -70 Shutdown Supply Current vs Supply Voltage 400 VSHDN = 0V -40 -30 ISHDN (nA) ISHDN (nA) -40 -1 125C 85C 25C -40C -10 -30 -100 VS = 1.8V 10 125C 85C 25C -40C ISHDN (nA) 10 SHDN Pin Current vs Temperature -30 V+ - VOH (mV) 20 SHDN Pin Pull-Up Current vs SHDN Pin Voltage 1 ISOURCE (mA) 10 100 2066 G45 Output Voltage Swing Low vs Load Current 1000 VS = 2.5V VS = 0.9V 1000 100 10 1 0.1 0.01 125C 85C 25C -40C 0.1 1 ISOURCE (mA) 10 100 2066 G46 100 VOL - V- (mV) VOL - V- (mV) V+ - VOH (mV) 100 10 125C 85C 25C -40C 1 0.1 0.01 0.1 1 ISINK (mA) 10 100 2066 G47 10 1 0.1 0.01 125C 85C 25C -40C 0.1 1 ISINK (mA) 10 100 2066 G48 Rev A For more information www.analog.com 11 LTC2066/LTC2067 TYPICAL PERFORMANCE CHARACTERISTICS Output Short Circuit Current vs Temperature No Phase Reversal 90 AV = +1 VS = 2.5V VIN = 5.6VP-P Output Short Circuit Current vs Temperature 20 VS = 2.5V 80 70 VS = 0.9V 15 ISC (mA) ISC (mA) VOLTAGE (1V/DIV) 60 50 40 10 30 5 20 SOURCING SINKING 10 VOUT VIN 0 -50 -25 1ms/DIV 0 25 50 75 TEMPERATURE (C) 100 0 -50 125 SINKING SOURCING -25 0 25 50 75 TEMPERATURE (C) 2066 G50 2066 G49 Large Signal Response Small Signal Response VS = 2.5V VIN = 40mVP-P AV = +1 VOUT (0.5V/DIV) VOUT (10mV/DIV) VS = 0.9V AV = +1 VOUT (1V/DIV) 125 2066 G51 Large Signal Response VS = 2.5V AV = +1 100 CL = 3.9pF CL = 100pF 200s/DIV 200s/DIV 20s/DIV 2066 G52 2066 G53 2066 G54 Small Signal Overshoot vs Load Capacitance Small Signal Response 80 VS = 0.9V VIN = 40mVP-P AV = +1 Small Signal Overshoot vs Load Capacitance 60 VS = 2.5V VIN = 40mVP-P AV = +1 70 VS = 0.9V VIN = 40mVP-P AV = +1 50 OVERSHOOT (%) OVERSHOOT (%) VOUT (10mV/DIV) 60 50 40 30 40 30 20 20 10 CL = 3.9pF CL = 100pF 0 20s/DIV 2066 G55 12 +OS -OS 1 10 100 CL (pF) 1000 2066 G56 10 0 +OS -OS 1 10 100 CL (pF) 1000 2066 G57 Rev A For more information www.analog.com LTC2066/LTC2067 TYPICAL PERFORMANCE CHARACTERISTICS Positive Output Overload Recovery VOUT 0.5V/DIV VOUT 1V/DIV VIN 50mV/DIV VOUT 1V/DIV VIN 50mV/DIV VIN 50mV/DIV 200s/DIV Negative Output Overload Recovery Positive Output Overload Recovery 2066 G58 2066 G59 400s/DIV 200s/DIV 2066 G60 VS = 2.5V AV = -100 VS = 0.9V AV = -100 VS = 2.5V AV = -100 Negative Output Overload Recovery Positive Input Overload Recovery Positive Input Overload Recovery VOUT 0.5V/DIV VIN 50mV/DIV 400s/DIV VIN 1V/DIV VIN 0.5V/DIV VOUT 1V/DIV VOUT 0.5V/DIV 2066 G61 VS = 0.9V AV = -100 2066 G62 100s/DIV VS = 2.5V AV = +1 40s/DIV 2066 G63 VS = 0.9V AV = +1 Negative Input Overload Recovery Negative Input Overload Recovery VIN 0.5V/DIV VIN 1V/DIV VOUT 0.5V/DIV VOUT 1V/DIV 100s/DIV VS = 2.5V AV = +1 2066 G64 40s/DIV 2066 G65 VS = 0.9V AV = +1 Rev A For more information www.analog.com 13 LTC2066/LTC2067 PIN FUNCTIONS V-: Negative Power Supply. A bypass capacitor should be used between supply pins and ground. OUT: Amplifier Output -IN: Inverting Amplifier Input +IN: Noninverting Amplifier Input V+: Positive Power Supply. A bypass capacitor should be used between supply pins and ground. SHDN: Shutdown Control Pin. The SHDN pin threshold is referenced to V-. If tied to V+, the part is enabled. If tied to V-, the part is disabled and draws less than 170nA of supply current per amplifier. It is recommended not to float this pin. BLOCK DIAGRAM Amplifier Shutdown Circuit V+ V+ V+ 50nA 10k SHDN +IN V- 7k V- V+ EMI FILTER 7k SHDN V+ V+ 2066 BDb V- + OUT - 2066 BDa V- V- -IN V- 14 Rev A For more information www.analog.com LTC2066/LTC2067 APPLICATIONS INFORMATION Using the LTC2066/LTC2067 The LTC2066/LTC2067 are single and dual zero-drift operational amplifiers with the open-loop voltage gain and bandwidth characteristics of a conventional operational amplifier. Advanced circuit techniques allow the LTC2066/ LTC2067 to operate continuously through its entire bandwidth while self-calibrating unwanted errors. Input Voltage Noise Zero-drift amplifiers like the LTC2066/LTC2067 achieve low input offset voltage and 1/f noise by heterodyning DC and flicker noise to higher frequencies. In early zero-drift amplifiers, this process resulted in idle tones at the selfcalibration frequency, often referred to as the chopping frequency. These artifacts made early zero-drift amplifiers difficult to use. The advanced circuit techniques used by the LTC2066/LTC2067 suppress these spurious artifacts, allowing for trouble-free use. Input Current Noise For applications with high source and feedback impedances, input current noise can be a significant contributor to total output noise. For this reason, it is important to consider noise current interaction with circuit elements placed at the amplifier's inputs. CURRENT NOISE DENSITY (fA/Hz) 10k VS = 5V VCM = 2.5V 1k 100 10 0.1 1 10 100 1k 10k 100k FREQUENCY (Hz) 1M 2066 F01 Figure 1. Input Current Noise Spectrum The current noise spectrum of the LTC2066/LTC2067 is shown in Figure 1. Low input current noise is achieved through the use of MOSFET input devices and self-calibration techniques to eliminate 1/f current noise. As with all zero-drift amplifiers, there is an increase in current noise at the offset-nulling frequency. This phenomenon is discussed in the Input Bias Current and Clock Feedthrough section. Input current noise also rises with frequency due to capacitive coupling of MOSFET channel thermal noise. Input Bias Current and Clock Feedthrough The input bias current of zero-drift amplifiers has different characteristics than that of a traditional operational amplifier. The specified input bias current is the DC average of transient currents which conduct due to the input stage's switching circuitry. In addition to this, junction leakages can contribute additional input bias current at elevated temperatures. Through careful design and the use of an innovative boot-strap circuit the input bias current of the LTC2066/LTC2067 does not exceed 35pA at room and 150pA over the full temperature range. This minimizes bias current induced errors even in high impedance circuits. Transient switching currents at the input interact with source and feedback impedances producing error voltages which are indistinguishable from a valid input signal. The resulting error voltages are amplified by the amplifier's closed-loop gain, which acts as a filter, attenuating frequency components above the circuit bandwidth. This phenomenon is known as clock feedthrough and is present in all zero-drift amplifiers. Understanding the cause and effect of clock feedthrough is important when using zero-drift amplifiers. For zero-drift amplifiers, clock feedthrough is proportional to source and feedback impedances, as well as the magnitude of the transient currents. These transient currents have been minimized in the LTC2066/LTC2067 to allow use with high source and feedback impedances. Many circuit designs require high feedback impedances Rev A For more information www.analog.com 15 LTC2066/LTC2067 APPLICATIONS INFORMATION In order to achieve accuracy on the microvolt level, thermocouple effects must be considered. Any connection of dissimilar metals forms a thermoelectric junction and generates a small temperature-dependent voltage. Also known as the Seebeck Effect, these thermal EMFs can be the dominant error source in low-drift circuits. Connectors, switches, relay contacts, sockets, resistors, and solder are all candidates for significant thermal EMF generation. Even junctions of copper wire from different manufacturers can generate thermal EMFs of 200nV/C, which significantly exceeds the maximum drift specification of the LTC2066/LTC2067. Figures 2 and 3 illustrate the potential magnitude of these voltages and their sensitivity to temperature. In order to minimize thermocouple-induced errors, attention must be given to circuit board layout and component selection. It is good practice to minimize the number of junctions in the amplifier's input signal path and avoid connectors, sockets, switches, and relays whenever possible. If such components are required, they should be selected for low thermal EMF characteristics. Furthermore, the number, type, and layout of junctions should be matched for both inputs with respect to thermal gradients on the circuit board. Doing so may involve deliberately introducing dummy junctions to offset unavoidable junctions. Air currents can also lead to thermal gradients and cause significant noise in measurement systems. It is important to prevent airflow across sensitive circuits. Doing so will often reduce thermocouple noise substantially. A summary of techniques can be found in Figure 4. 16 3.0 2.8 2.6 2.4 2.2 2.0 1.8 1.6 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0 MICROVOLTS REFERRED TO 25C Thermocouple Effects 25 35 30 40 45 TEMPERATURE (C) 2066 F02 Figure 2. Thermal EMF Generated by Two Copper Wires from Different Manufacturers THERMALLY PRODUCED VOLTAGE IN MICROVOLTS to minimize power consumption and/or require a sensor which is intrinsically high impedance. In these cases, a capacitor can be used, either at the input or across the feedback resistor, to limit the bandwidth of the closedloop system. Doing so will effectively filter out the clock feedthrough signal. 100 SLOPE 1.5V/C BELOW 25C 50 0 64% SN/36% Pb 60% Cd/40% SN SLOPE 160nV/C BELOW 25C -50 -100 10 30 0 40 50 20 SOLDER-COPPER JUNCTION DIFFERENTIAL TEMPERATURE SOURCE: NEW ELECTRONICS 02-06-77 2066 F03 Figure 3. Solder-Copper Thermal EMFs Leakage Effects Leakage currents into high impedance signal nodes can easily degrade measurement accuracy of sub-nanoamp signals. High voltage and high temperature applications are especially susceptible to these issues. Quality insulation materials should be used, and insulating surfaces should be cleaned to remove fluxes and other residues. For humid environments, surface coating may be necessary to provide a moisture barrier. Rev A For more information www.analog.com LTC2066/LTC2067 APPLICATIONS INFORMATION HEAT SOURCE/ POWER DISSIPATOR RG** +- VIN THERMAL GRADIENT +IN OUT LTC2066 NC VTHERMAL RL -IN RG +- VTHERMAL RF RELAY ** # RF MATCHING RELAY # * 2066 F04 * CUT SLOTS IN PCB FOR THERMAL ISOLATION. ** INTRODUCE DUMMY JUNCTIONS AND COMPONENTS TO OFFSET UNAVOIDABLE JUNCTIONS OR CANCEL THERMAL EMFs. ALIGN INPUTS SYMMETRICALLY WITH RESPECT TO THERMAL GRADIENTS. INTRODUCE DUMMY TRACES AND COMPONENTS FOR SYMMETRICAL THERMAL HEAT SINKING. LOADS AND FEEDBACK CAN DISSIPATE POWER AND GENERATE THERMAL GRADIENTS. BE AWARE OF THEIR THERMAL EFFECTS. # COVER CIRCUIT TO PREVENT AIR CURRENTS FROM CREATING THERMAL GRADIENTS. Figure 4. Techniques for Minimizing Thermocouple-Induced Errors NO SOLDER MASK OVER GUARD RING GUARD RING LEAKAGE CURRENT VBIAS -IN HIGH-Z SENSOR RF +IN V- V+ V- OUT VOUT V+ NO LEAKAGE CURRENT, V-IN = V+IN AVOID DISSIPATING SIGNIFICANT AMOUNTS OF POWER IN THIS RESISTOR. IT WILL GENERATE THERMAL GRADIENTS WITH RESPECT TO THE INPUT PINS AND LEAD TO THERMOCOUPLE-INDUCED ERROR. THERMALLY ISOLATE OR ALIGN WITH INPUTS IF RESISTOR WILL CAUSE HEATING. GUARD RING VBIAS RF HIGH-Z SENSOR VIN -+ V+ RIN - LEAKAGE CURRENT LTC2066 VOUT + V- LEAKAGE CURRENT IS ABSORBED BY GROUND INSTEAD OF CAUSING A MEASUREMENT ERROR. 2066 F05 Figure 5. Example Layout of Inverting Amplifier with Leakage Guard Ring Rev A For more information www.analog.com 17 LTC2066/LTC2067 APPLICATIONS INFORMATION Board leakage can be minimized by encircling the input connections with a guard ring operated at a potential very close to that of the inputs. The ring must be tied to a low impedance node. For inverting configurations, the guard ring should be tied to the potential of the positive input (+IN). For noninverting configurations, the guard ring should be tied to the potential of the negative input (-IN). In order for this technique to be effective, the guard ring must not be covered by solder mask. Ringing both sides of the printed circuit board may be required. See Figure 5 for an example of proper layout. Shutdown Mode The LTC2066 in the SC70 package and the LTC2067 in the DFN package feature a shutdown mode for low-power applications. In the OFF state, each amplifier draws less than 170nA of supply current and the outputs present a high impedance to external circuitry. Shutdown operation is accomplished by tying SHDN below VL. If the shutdown feature is not required, it is recommended that SHDN be tied to V+. A current source pulls the SHDN pin high to keep the amplifier in the ON state when the pin is floated, however this may not be reliable at elevated temperatures due to board leakage (see SHDN Circuit Block Diagram, page 14). For operation in noisy environments, a capacitor between SHDN and V+ is recommended to prevent noise from changing the shutdown state. When there is a danger of SHDN being pulled beyond the supply rails, resistance in series with the SHDN pin is recommended to limit the resulting current. rent available to take the system up to nominal voltages. In other cases, this transient power-up current will lead to added power loss in duty-cycled applications. A way to quantify the transient current loss is to integrate the supply current during power-up to examine the total charge loss. If there were no additional transient current, the integrated supply current would appear as a smooth, straight line with a slope equal to the DC supply current of the part. Any deviation from a straight line indicates additional transient current that is drawn from the supply. The LTC2066/LTC2067 have been designed to minimize this charge loss during power-up so that power can be conserved in duty-cycled applications. Figure 6 shows the integrated supply current (i.e. charge) of the LTC2066 during power-up. Likewise, Figure 7 shows the charge loss due to enabling and disabling the part via the SHDN pin. V- 5V/DIV VOUT 2V/DIV QV+ 10nC/DIV 500s/DIV 1V/s V- EDGE RATE V+ = 5V Figure 6. LTC2066 Charge Loss During Power-Up VSHDN 5V/DIV Start-Up Characteristics Micropower op amps are often not micropower during start-up, which can cause problems when used on low current supplies. Large transient currents can conduct during power-up until the internal bias nodes settle to their final values. A large amount of current can be drawn from the supplies during this transient, which can sustain for several milliseconds in the case of a micropower part. In the worst case, there may not be enough supply cur- 18 2066 F06 VOUT 2V/DIV QV+ 10nC/DIV 500s/DIV 2066 F07 Figure 7. LTC2066 Charge Loss Due to Enabling and Disabling via SHDN Pin Rev A For more information www.analog.com LTC2066/LTC2067 APPLICATIONS INFORMATION There are benefits when the SHDN pin is used to disable and enable the part in duty-cycled applications, rather than powering down the external supply voltage (V+). Powering up and powering down the external supply will tend to waste charge due to charging and discharging the external decoupling capacitors. For these power-cycled applications, a relay or MOS device can be located after the decoupling capacitors to alleviate this; however there are drawbacks to this approach. The LTC2066 draws an initial charge of approximately 3nC when powered up. This recurring charge loss is unavoidable in power-cycled applications. Additionally, if the supply ramp rate exceeds 0.4V/s, an internal transient ESD clamp will trigger, conducting additional current from V+ to V-. This will waste charge and can make insignificant any gain that may have been expected by power-cycling the supply. Figure 8 shows the charge loss at power-up. The shutdown pin can be used to overcome these limitations in duty-cycled applications. The typical charge loss transitioning into and out of shutdown is only 2.3nC. Since the supply is not transitioned, the external decoupling capacitors do not draw charge from the supply. CHARGE CONSUMED TO 0.1% SETTLED POINT (nC) 100 10 Gas Sensor This low power precision gas sensor circuit operates in an oxygen level range of 0% to 30%, with a nominal output of 1V in normal atmospheric oxygen concentrations (20.9%) when the gas sensor has been fully initialized. Total active power consumption is less than 10.1A on a single rail supply. Since this gas sensor produces 100A in a normal oxygen environment and requires a 100 load resistor, the resulting input signal is typically around 10mV. The LTC2066's rail-to-rail input means no additional DC level shifting is necessary, all the way down to very low oxygen concentrations. Due to the extremely low input offset voltage of the LTC2066, which is 1V typically and 5V maximum, it is possible to gain up the mV-scale input signal substantially without introducing significant error. In the configuration shown in Figure 9, with a noninverting gain of 101V/V, the worst-case input offset results in a maximum of 0.5mV offset on the 1V output, or 0.05% error. Although the 100k resistor in series with the gas sensor does not strictly have the same precision requirement as the 10M and 100k resistors that set the gain, it is important to use a similar resistor at both input terminals. This helps to minimize additional offset voltage at the inputs due to thermocouple effects and bias current, hence the similar 0.1% precision requirement. 10M 0.1% 1 0.1 1 SUPPLY EDGE RATE (V/s) 2 OXYGEN SENSOR CITY TECHNOLOGY 40XV 100k 0.1% 100k* 0.1% 100 0.1% 2066 F08 Figure 8. LTC2066 Power-Up Charge vs Supply Edge Rate www.citytech.com 1.8V - LTC2066 + VOUT = 1V IN AIR ISUPPLY = 7.5A (ENABLED) 90nA (SHUTDOWN) VSHDN 2066 F09 *RESISTOR CANCELS OUT PARASITIC SEEBECK EFFECT VOLTAGE Figure 9. Micropower Precision Oxygen Sensor Rev A For more information www.analog.com 19 LTC2066/LTC2067 APPLICATIONS INFORMATION RTD Sensor This low power platinum resistance temperature detector (RTD) sensor circuit draws only 43A total supply current on a minimum 2.6V rail, and is accurate to within 1C at room temperature, including all error intrinsic to the Vishay PTS Class F0.3 Variant RTD. It covers the temperature range from -40C to 85C in 10mV/C increments and produces an output of 1V at nominal room temperature of 25C. The LTC2066's extremely low typical offset of 1V and typical input bias current of 5pA allows for the use of a very low excitation current in the RTD. Thus, self-heating is negligible, improving accuracy. The LT5400-3, B-grade, is used to provide a 0.025% matched resistor network that is effectively a precision 131:1 voltage divider. This precision divider forms one half of a bridge circuit, with the 0.1% 110k and RTD in the other branch. Note that the 110k's precision requirement is to ensure matching with the RTD. The 11k R2 serves to provide a DC offset for the entire bridge so that IN 2.6V VSUPPLY 18V + - C1 0.1F LT6656-2.048 GND the output is 1V at room temperature. Since bridge imbalances can lead to error, it is recommended to minimize the length of the leads connecting the RTD to reduce additional lead resistance. The LT6656-2.048 reference helps create a known excitation current in the RTD at each temperature of operation, and also acts as a supply for the LTC2066, all while using less than 1A itself. The LT6656 can accept input voltages anywhere between 2.6V and 18V, allowing for flexibility in selection of supply voltage while maintaining a fixed output range. The LT6656 reference can easily source the 43A required to run the entire circuit, thanks to the LTC2066's 10A maximum supply current and ability to handle microvolt signals produced by the RTD under low excitation current. Care should be taken to minimize thermocouple effects by preventing significant thermal gradients between the two op amp inputs. It is also important to choose feedback and series resistors that are low-tempco to minimize error due to drift over the entire temperature range. OUT C2 10F VISHAY PTS SERIES 1k PtRTD, CLASS F0.3 PTS12061B1K00P100 www.vishay.com 110k 0.1% 2ppm/C VOUT SCALE 10mV/C 1V AT 25C ROOM TEMP ISUPPLY = 43A 100k RTD 1k 10k 10k R2 11k 100k + OUT LTC2066 - RFB 1.58M 2066 F10 LT5400-3 131:1 VOLTAGE DIVIDER Figure 10. RTD Sensor 20 Rev A For more information www.analog.com LTC2066/LTC2067 APPLICATIONS INFORMATION VIN 4.5V TO 90V RIN 49.9 0.1% ISENSE 100A to 250mA RSENSE 0.1 C1 3.3F REF LT1389-4.096 R1 49.9 0.1% - BSP322P M1 LTC2066 + D1 1N4148 LOAD C3 100nF BSP322P M2 R3 499k C4 22F RLOAD 5k 0.1% VOUT = 10 * ISENSE 1mV TO 2.5V C2* 10F 2066 F11 *C2 MUST WITHSTAND VOLTAGES UP TO VIN Figure 11. High Side Current Sense High Side Current Sense This micropower precision LTC2066 high side current sense circuit measures currents from 100A to 250mA over a 4.5V to 90V input voltage range. The output of this circuit is: R *R VOUT = LOAD SENSE ISENSE = 10 *ISENSE RIN The LTC2066's low typical input offset voltage of 1V and low input bias current of 5pA contribute output errors that are much smaller than the error due to precision limitations of the resistors used. Thus, output accuracy is mainly set by the accuracy of the resistors RSENSE, RIN, and RLOAD. R1 helps cancel out parasitic Seebeck effect voltages at -IN by balancing with an identical voltage at +IN. The LT1389-4.096 reference, along with the bootstrap circuit composed of M2, R3, and D1, establishes a very low power isolated 3V rail that protects the LTC2066 from reaching its absolute maximum voltage of 5.5V while allowing for much higher input voltages. Since the LTC2066's gain-bandwidth product is 100kHz, it is recommended to use this circuit to measure currents that do not change faster than 10kHz. Note that the output filter as drawn will limit the frequency to 1.5Hz, which optimizes for lowest noise. Rev A For more information www.analog.com 21 LTC2066/LTC2067 APPLICATIONS INFORMATION Parallel LTC2067 Amplifiers to Reduce Noise by 2 R2 909k R1 100k 1.5V - 1/2 LTC2067 + R3 100 -1.5V IN OUT 1.5V R4 100 + R5 100k 1/2 LTC2067 - -1.5V R6 909k 2066 F12 Precision, Micropower Carbon Monoxide Detector C2 100nF R3 35.7k 4CM CARBON MONOXIDE SENSOR CITY TECHNOLOGY 70nA/ppm CO TYP 2.5V - 2.5V R1 402k R2 100k 1/2 LTC2067 + C1 100nF 4CM COUNTER ELECTRODE (CE) SELF-BIASES BELOW WE POTENTIAL VWE - VCE = -0.3V TO -0.4V TYP CE 2.5V RE 4CM WE J1 MMBFJ270 RBURDEN 5 2.5V R6 402k R7 100k TYPICAL GAIN: 2.5mV/ppm CO C4 100nF R4 1M INPUT RANGE: 0ppm TO 500ppm CO R5 35.7k OUTPUT: 1.7V (TYP) 2.0V (MAX) AT 500ppm CO 2.5V - 1/2 LTC2067 R8 100k OUT C5 10F + C3 100nF 2066 F13 22 Rev A For more information www.analog.com LTC2066/LTC2067 PACKAGE DESCRIPTION SC6 Package 6-Lead Plastic SC70 (Reference LTC DWG # 05-08-1638 Rev B) 0.47 MAX 0.65 REF 1.80 - 2.20 (NOTE 4) 1.00 REF INDEX AREA (NOTE 6) 1.80 - 2.40 1.15 - 1.35 (NOTE 4) 2.8 BSC 1.8 REF PIN 1 RECOMMENDED SOLDER PAD LAYOUT PER IPC CALCULATOR 0.10 - 0.40 0.65 BSC 0.15 - 0.30 6 PLCS (NOTE 3) 0.80 - 1.00 1.00 MAX 0.00 - 0.10 REF GAUGE PLANE 0.15 BSC 0.26 - 0.46 0.10 - 0.18 (NOTE 3) SC6 SC70 1205 REV B NOTE: 1. DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLUSIVE OF PLATING 4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 5. MOLD FLASH SHALL NOT EXCEED 0.254mm 6. DETAILS OF THE PIN 1 IDENTIFIER ARE OPTIONAL, BUT MUST BE LOCATED WITHIN THE INDEX AREA 7. EIAJ PACKAGE REFERENCE IS EIAJ SC-70 8. JEDEC PACKAGE REFERENCE IS MO-203 VARIATION AB Rev A For more information www.analog.com 23 LTC2066/LTC2067 PACKAGE DESCRIPTION S5 Package 5-Lead Plastic TSOT-23 (Reference LTC DWG # 05-08-1635) 0.62 MAX 0.95 REF 2.90 BSC (NOTE 4) 1.22 REF 1.4 MIN 3.85 MAX 2.62 REF 2.80 BSC 1.50 - 1.75 (NOTE 4) PIN ONE RECOMMENDED SOLDER PAD LAYOUT PER IPC CALCULATOR 0.30 - 0.45 TYP 5 PLCS (NOTE 3) 0.95 BSC 0.80 - 0.90 0.20 BSC 0.30 - 0.50 REF 0.09 - 0.20 (NOTE 3) NOTE: 1. DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLUSIVE OF PLATING 4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 5. MOLD FLASH SHALL NOT EXCEED 0.254mm 6. JEDEC PACKAGE REFERENCE IS MO-193 24 0.01 - 0.10 1.00 MAX DATUM `A' 1.90 BSC S5 TSOT-23 0302 Rev A For more information www.analog.com LTC2066/LTC2067 PACKAGE DESCRIPTION MS8 Package 8-Lead Plastic MSOP (Reference LTC DWG # 05-08-1660 Rev G) 0.889 0.127 (.035 .005) 5.10 (.201) MIN 3.20 - 3.45 (.126 - .136) 3.00 0.102 (.118 .004) (NOTE 3) 0.65 (.0256) BSC 0.42 0.038 (.0165 .0015) TYP 8 7 6 5 0.52 (.0205) REF RECOMMENDED SOLDER PAD LAYOUT 0.254 (.010) 3.00 0.102 (.118 .004) (NOTE 4) 4.90 0.152 (.193 .006) DETAIL "A" 0 - 6 TYP GAUGE PLANE 0.53 0.152 (.021 .006) DETAIL "A" 1 2 3 4 1.10 (.043) MAX 0.86 (.034) REF 0.18 (.007) SEATING PLANE 0.22 - 0.38 (.009 - .015) TYP 0.65 (.0256) NOTE: BSC 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 0.1016 0.0508 (.004 .002) MSOP (MS8) 0213 REV G Rev A For more information www.analog.com 25 LTC2066/LTC2067 PACKAGE DESCRIPTION DD Package 10-Lead Plastic DFN (3mm x 3mm) (Reference LTC DWG # 05-08-1699 Rev C) 0.70 0.05 3.55 0.05 1.65 0.05 2.15 0.05 (2 SIDES) PACKAGE OUTLINE 0.25 0.05 0.50 BSC 2.38 0.05 (2 SIDES) RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS 3.00 0.10 (4 SIDES) R = 0.125 TYP 6 0.40 0.10 10 1.65 0.10 (2 SIDES) PIN 1 NOTCH R = 0.20 OR 0.35 x 45 CHAMFER PIN 1 TOP MARK (SEE NOTE 6) 0.200 REF 5 0.75 0.05 0.00 - 0.05 1 (DD) DFN REV C 0310 0.25 0.05 0.50 BSC 2.38 0.10 (2 SIDES) BOTTOM VIEW--EXPOSED PAD NOTE: 1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-2). CHECK THE LTC WEBSITE DATA SHEET FOR CURRENT STATUS OF VARIATION ASSIGNMENT 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 26 Rev A For more information www.analog.com LTC2066/LTC2067 REVISION HISTORY REV DATE DESCRIPTION A 07/18 Adding LTC2067 to data sheet PAGE NUMBER All Pages Rev A Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is For granted by information implication orwww.analog.com otherwise under any patent or patent rights of Analog Devices. more 27 LTC2066/LTC2067 TYPICAL APPLICATION Battery Powered Current Sense Amplifier Floats with Sense Resistor Voltage IN BAT >3.1V 12V LT6656-3 10F 2M 2M 14k ILOAD CURRENT TO BE MEASURED (BI-DIRECTIONAL) RSENSE 10m OUT 10F 2M 2M VREF + LTC2066 14k - VOUT = VREF/2 ILOAD x RSENSE x GAIN GAIN = 2M/14k 2M 2066 TA03 0.1% RESISTORS TO MAINTAIN OFFSET ACCURACY RELATED PARTS PART NUMBER DESCRIPTION LT1494/LT1495/ LT1496 1.5A Max, Over-The-Top Precision Rail-to-Rail 375V VOS, 1.5A IS, 2.2V to 36V VS, 2.7kHz, RRIO Input and Output Op Amps LT6003/LT6004/ LT6005 1.6V, 1A Precision Rail-to-Rail Input and Output Op Amps 500V VOS, 1A IS, 1.6V to 16V VS, 2kHz, RRIO LTC2063/LTC2064 2A, Low IB, Zero-Drift Operational Amplifiers 5V VOS, 2A IS, 1.7V to 5.25V VS, 20kHz, RRIO ADA4051-1/ ADA4051-2 Micropower, Single/Dual, Zero-Drift Operational 15V VOS, 17A IS, 1.8V to 5.5V VS, 115kHz, RRIO Amplifier LT6023 Micropower, Enhanced Slew Op Amp LTC2054/LTC2055 Micropower, Single/Dual, Zero-Drift Operational 5V VOS, 130A IS, 2.7V to 11V VS, 500kHz, RR Output Amplifier LTC2057/ LTC2057HV High Voltage-Low Noise Zero-Drift Operational Amplifier 4V VOS, 1.2mA IS, 4.75V to 60V VS, 1.5MHz, RR Output LTC2050/ LTC2050HV Zero-Drift Operational Amplifier 3V VOS, 1.5mA IS, 2.7V to 12V VS, 3MHz, RR Output LTC2051/LTC2052 Dual/Quad, Zero-Drift Operational Amplifier 3V VOS, 1.5mA IS, 2.7V to 12V VS, 3MHz, RR Output LTC2053 Precision, Rail-to-Rail, Zero-Drift, ResistorProgrammable Instrumentation Amplifier 10V VOS, 1.3mA IS, 2.7V to 12V VS, 200kHz, RRIO LT5400 Quad Matched Resistor Network 0.01% Matching, 8ppm/C Temp Drift , 0.2ppm/C Temp Matching AD7170 12-Bit Low Power - ADC 130A in Conversion Mode, 5A in Shutdown LTC5800 SmartMesh(R) Wireless Sensor Network IC Wireless Mesh Networks LT6656 850nA Precision Voltage Reference 850nA, 10ppm/C Temp Drift, 0.05% Accuracy, SOT-23 Package 28 COMMENTS 20V VOS, 20A IS, 3V to 30V VS, 40kHz Rev A D16885-0-7/18(A) For more information www.analog.com www.analog.com ANALOG DEVICES, INC. 2017-2018