14-Bit, 80/105/125/150 MSPS, 1.8 V
Dual Analog-to-Digital Converter
AD9640
Rev. B
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FEATURES
SNR = 71.8 dBc (72.8 dBFS) to 70 MHz @ 125 MSPS
SFDR = 85 dBc to 70 MHz @ 125 MSPS
Low power: 750 mW @ 125 MSPS
SNR = 71.6 dBc (72.6 dBFS) to 70 MHz @ 150 MSPS
SFDR = 84 dBc to 70 MHz @ 150 MSPS
Low power: 820 mW @ 150 MSPS
1.8 V analog supply operation
1.8 V to 3.3V CMOS output supply or 1.8 V LVDS
output supply
Integer 1 to 8 input clock divider
IF sampling frequencies to 450 MHz
Internal ADC voltage reference
Integrated ADC sample-and-hold inputs
Flexible analog input range: 1 V p-p to 2 V p-p
Differential analog inputs with 650 MHz bandwidth
ADC clock duty cycle stabilizer
95 dB channel isolation/crosstalk
Serial port control
User-configurable, built-in self-test (BIST) capability
Energy-saving power-down modes
Integrated receive features
Fast detect/threshold bits
Composite signal monitor
APPLICATIONS
Communications
Diversity radio systems
Multimode digital receivers
GSM, EDGE, WCDMA, LTE,
CDMA2000, WiMAX, TD-SCDMA
I/Q demodulation systems
Smart antenna systems
General-purpose software radios
Broadband data applications
FUNCTIONAL BLOCK DIAGRAM
06547-001
VIN+A
VIN–A
VREF
SENSE
VIN–B
VIN+B
D13A
D0A
CLK+
CLK–
DCOA
DCOB
D13B
D0B
AGND SYNC FD(0:3)B
ADC
ADC
SIG NAL M O NITO R
DATA
AVDD DVDD FD(0:3)A
DRGND
PROG RAM M I NG DATA
DRVDD
FD BITS/THRESHOLD
DETECT
REF
SELECT DUTY CYCLE
STABILIZER
MULTICHIP
SYNC FD BITS / THRESHO L D
DETECT SIG NAL MO NITO R
INTERFACE
DCO
GENERATION
DIVIDE
1TO 8
SIGNAL
MONITOR
SPI
CMOS
OUT PUT BUF F E R
CMOS
OUT P UT BUFFER
SHA
SHA
CSB
SCLK/
DFS
SDIO/
DCS
CML
RBIAS
SMI
SDO/
OEB
SMI
SCLK/
PDWN
SMI
SDFS
Figure 1.
PRODUCT HIGHLIGHTS
1. Integrated dual 14-bit, 80/105/125/150 MSPS ADC.
2. Fast overrange detect and signal monitor with serial output.
3. Signal monitor block with dedicated serial output mode.
4. Proprietary differential input that maintains excellent SNR
performance for input frequencies up to 450 MHz.
5. Operation from a single 1.8 V supply and a separate digital
output driver supply to accommodate 1.8 V to 3.3 V logic
families.
6. A standard serial port interface that supports various
product features and functions, such as data formatting
(offset binary, twos complement, or gray coding), enabling
the clock DCS, power-down, and voltage reference mode.
7. Pin compatibility with the AD9627, AD9627-11, and the
AD9600 for a simple migration from 14 bits to 12 bits, 11
bits, or 10 bits.
AD9640
Rev. B | Page 2 of 52
TABLE OF CONTENTS
Features .............................................................................................. 1
Applications ....................................................................................... 1
Functional Block Diagram .............................................................. 1
Product Highlights ........................................................................... 1
Revision History ............................................................................... 3
General Description ......................................................................... 4
Specifications ..................................................................................... 5
ADC DC Specifications—AD9640ABCPZ-80,
AD9640BCPZ-80, AD9640ABCPZ-105, and
AD9640BCPZ-105 ......................................................................... 5
ADC DC Specifications—AD9640ABCPZ-125,
AD9640BCPZ-125, AD9640ABCPZ-150, and
AD9640BCPZ-150 ......................................................................... 6
ADC AC Specifications—AD9640ABCPZ-80,
AD9640BCPZ-80, AD9640ABCPZ-105, and
AD9640BCPZ-105 ......................................................................... 7
ADC AC Specifications—AD9640ABCPZ-125,
AD9640BCPZ-125, AD9640ABCPZ-150, and
AD9640BCPZ 150 ......................................................................... 8
Digital Specifications ................................................................... 9
Switching Specifications—AD9640ABCPZ-80,
AD9640BCPZ-80, AD9640ABCPZ-105, and
AD9640BCPZ-105 ..................................................................... 10
Switching Specifications—AD9640ABCPZ-125,
AD9640BCPZ-125, AD9640ABCPZ-150, and
AD9640BCPZ-150 ..................................................................... 11
Timing Specifications ................................................................ 12
Absolute Maximum Ratings .......................................................... 14
Thermal Characteristics ............................................................ 14
ESD Caution ................................................................................ 14
Pin Configurations and Function Descriptions ......................... 15
Equivalent Circuits ......................................................................... 19
Typical Performance Characteristics ........................................... 20
Theory of Operation ...................................................................... 25
ADC Architecture ...................................................................... 25
Analog Input Considerations .................................................... 25
Voltage Reference ....................................................................... 27
Clock Input Considerations ...................................................... 28
Power Dissipation and Standby Mode .................................... 30
Digital Outputs ........................................................................... 31
Timing ......................................................................................... 31
ADC Overrange and Gain Control .............................................. 32
Fast Detect Overview ................................................................. 32
ADC Fast Magnitude ................................................................. 32
ADC Overrange (OR) ................................................................ 33
Gain Switching ............................................................................ 33
Signal Monitor ................................................................................ 35
Peak Detector Mode................................................................... 35
RMS/MS Magnitude Mode ......................................................... 35
Threshold Crossing Mode ......................................................... 36
Additional Control Bits ............................................................. 36
DC Correction ............................................................................ 36
Signal Monitor SPORT Output ................................................ 37
Built-In Self-Test (BIST) and Output Test .................................. 38
Built-In Self-Test (BIST) ............................................................ 38
Output Test Modes ..................................................................... 38
Channel/Chip Synchronization .................................................... 39
Serial Port Interface (SPI) .............................................................. 40
Configuration Using the SPI ..................................................... 40
Hardware Interface ..................................................................... 40
Configuration Without the SPI ................................................ 41
SPI Accessible Features .............................................................. 41
Memory Map .................................................................................. 42
Reading the Memory Map Table .............................................. 42
External Memory Map .............................................................. 43
Memory Map Register Description ......................................... 46
Applications Information .............................................................. 49
Design Guidelines ...................................................................... 49
Outline Dimensions ....................................................................... 50
Ordering Guide .......................................................................... 51
AD9640
Rev. B | Page 3 of 52
REVISION HISTORY
12/09—Rev. A to Rev. B
Added CP-64-6 Package .................................................... Universal
Changes to Ordering Guide ........................................................... 51
6/09—Rev. 0 to Rev. A
Changes to Applications Section and Product
Highlights Section ............................................................................. 1
Changes to General Description Section ....................................... 3
Changes to Specifications Section ................................................... 4
Changes to Figure 2 ......................................................................... 11
Changes to Figure 3 ......................................................................... 12
Changes to Pin Configurations and Functional
Descriptions Section ....................................................................... 12
Changes to Figure 11, Figure 12, Figure 14 ................................. 18
Change to Table 15 .......................................................................... 30
Changes to ADC Overrange and Gain Control Section ............ 31
Changes to Signal Monitor Section .............................................. 34
Changes to Table 25 ........................................................................ 42
Changes to Signal Monitor Period (Register 0x113 to
Register 0x115) Section .................................................................. 47
Added LVDS Operation Section ................................................... 48
Added Exposed Pad Notation to Outline Dimensions .............. 49
6/07—Revision 0: Initial Version
AD9640
Rev. B | Page 4 of 52
GENERAL DESCRIPTION
The AD9640 is a dual 14-bit, 80/105/125/150 MSPS analog-to-
digital converter (ADC). The AD9640 is designed to support
communications applications where low cost, small size, and
versatility are desired.
The dual ADC core features a multistage, differential pipelined
architecture with integrated output error correction logic. Each
ADC features wide bandwidth differential sample-and-hold
analog input amplifiers supporting a variety of user-selectable
input ranges. An integrated voltage reference eases design
considerations. A duty cycle stabilizer is provided to compen-
sate for variations in the ADC clock duty cycle, allowing the
converters to maintain excellent performance.
The AD9640 has several functions that simplify the automatic
gain control (AGC) function in the system receiver. The fast detect
feature allows fast overrange detection by outputting four bits of
input level information with very short latency.
In addition, the programmable threshold detector allows moni-
toring of the incoming signal power using the four fast detect
bits of the ADC with very low latency. If the input signal level
exceeds the programmable threshold, the fine upper threshold
indicator goes high. Because this threshold is set from the four
MSBs, the user can quickly turn down the system gain to avoid an
overrange condition.
The second AGC-related function is the signal monitor. This
block allows the user to monitor the composite magnitude of
the incoming signal, which aids in setting the gain to optimize
the dynamic range of the overall system.
The ADC output data can be routed directly to the two external
14-bit output ports. These outputs can be set from 1.8 V to 3.3 V
CMOS or 1.8 V LVDS.
Flexible power-down options allow significant power savings,
when desired.
Programming for setup and control is accomplished using a
3-bit SPI-compatible serial interface.
The AD9640 is available in a 64-lead LFCSP and is specified
over the industrial temperature range of −40°C to +85°C.
AD9640
Rev. B | Page 5 of 52
SPECIFICATIONS
ADC DC SPECIFICATIONS—AD9640ABCPZ-80, AD9640BCPZ-80, AD9640ABCPZ-105, AND AD9640BCPZ-105
AVDD = 1.8 V, DVDD = 1.8 V, DRVDD = 3.3 V, maximum sample rate, VIN = −1.0 dBFS differential input, 1.0 V internal reference,
DCS enabled, fast detect outputs disabled, and signal monitor disabled, unless otherwise noted.
Table 1.
Parameter Temperature
AD9640ABCPZ-
80/AD9640BCPZ-80
AD9640ABCPZ-
105/AD9640BCPZ-105
Unit
Min Typ Max Min Typ Max
RESOLUTION Full 14 14 Bits
ACCURACY
No Missing Codes Full Guaranteed Guaranteed
Offset Error Full ±0.3 ±0.6 ±0.3 ±0.6 % FSR
Gain Error Full ±0.2 ±3.0 ±0.2 ±3.0 % FSR
Differential Nonlinearity (DNL)1 Full ±0.9 ±0.9 LSB
25°C ±0.4 ±0.4 LSB
Integral Nonlinearity (INL)1 Full ±5.0 ±5.0 LSB
25°C ±2.0 ±2.0 LSB
MATCHING CHARACTERISTIC
Offset Error Full ±0.3 ±0.6 ±0.4 ±0.7 % FSR
Gain Error Full ±0.1 ±0.5 ±0.1 ±0.5 % FSR
TEMPERATURE DRIFT
Offset Error Full ±15 ±15 ppm/°C
Gain Error Full ±95 ±95 ppm/°C
INTERNAL VOLTAGE REFERENCE
Output Voltage Error (1 V Mode) Full ±2 ±15 ±2 ±15 mV
Load Regulation @ 1.0 mA Full 7 7 mV
INPUT REFERRED NOISE
VREF = 1.0 V 25°C 1.3 1.3 LSB rms
ANALOG INPUT
Input Span, VREF = 1.0 V Full 2 2 V p-p
Input Capacitance2 Full 8 8 pF
VREF INPUT RESISTANCE Full 6 6 kΩ
POWER SUPPLIES
Supply Voltage
AVDD, DVDD Full 1.7 1.8 1.9 1.7 1.8 1.9 V
DRVDD (CMOS Mode) Full 1.7 3.3 3.6 1.7 3.3 3.6 V
DRVDD (LVDS Mode) Full 1.7 1.8 1.9 1.7 1.8 1.9 V
Supply Current
IAVDD1, 3 Full 233
277 310
371 mA
IDVDD1, 3 Full 26 34 mA
IDRVDD1 (3.3 V CMOS) Full 27 35 mA
IDRVDD1 (1.8 V CMOS) Full 12 18 mA
IDRVDD1 (1.8 V LVDS) Full 54 55 mA
POWER CONSUMPTION
DC Input Full 452 492 603 657 mW
Sine Wave Input1 (DRVDD = 1.8 V) Full 487 645 mW
Sine Wave Input1 (DRVDD = 3.3 V) Full 550 730 mW
Standby Power4 Full 52 68 mW
Power-Down Power Full 2.5 6 2.5 6 mW
1 Measured with a low input frequency, full-scale sine wave, with approximately 5 pF loading on each output bit.
2 Input capacitance refers to the effective capacitance between one differential input pin and AGND. See Figure 8 for the equivalent analog input structure.
3 The maximum limit applies to the combination of IAVDD and IDVDD currents.
4 Standby power is measured with a dc input and with the CLK pins (CLK+, CLK−) inactive (set to AVDD or AGND).
AD9640
Rev. B | Page 6 of 52
ADC DC SPECIFICATIONS—AD9640ABCPZ-125, AD9640BCPZ-125, AD9640ABCPZ-150, AND AD9640BCPZ-150
AVDD = 1.8 V, DVDD = 1.8 V, DRVDD = 3.3 V, maximum sample rate, VIN = −1.0 dBFS differential input, 1.0 V internal reference,
DCS enabled, fast detect outputs disabled, and signal monitor disabled, unless otherwise noted.
Table 2.
Parameter Temperature
AD9640ABCPZ-125/
AD9640BCPZ-125
AD9640ABCPZ-150/
AD9640BCPZ-150
Unit
Min Typ Max Min Typ Max
RESOLUTION Full 14 14 Bits
ACCURACY
No Missing Codes Full Guaranteed Guaranteed
Offset Error Full ±0.3 ±0.6 ±0.3 ±0.6 % FSR
Gain Error Full ±0.2 ±3.0 ±0.2 ±3.0 % FSR
Differential Nonlinearity (DNL)1 Full ±0.9 −0.95/+1.5 LSB
25°C ±0.4 −0.4/+0.6 LSB
Integral Nonlinearity (INL)1 Full ±5.0 ±5.0 LSB
25°C ±2 ±2 LSB
MATCHING CHARACTERISTIC
Offset Error 25°C ±0.4 ±0.7 ±0.4 ±0.7 % FSR
Gain Error 25°C ±0.1 ±0.6 ±0.2 ±0.6 % FSR
TEMPERATURE DRIFT
Offset Error Full ±15 ±15 ppm/°C
Gain Error Full ±95 ±95 ppm/°C
INTERNAL VOLTAGE REFERENCE
Output Voltage Error (1 V Mode) Full ±2 ±15 ±3 ±15 mV
Load Regulation @ 1.0 mA Full 7 7 mV
INPUT REFERRED NOISE
VREF = 1.0 V 25°C 1.3 1.3 LSB rms
ANALOG INPUT
Input Span, VREF = 1.0 V Full 2 2 V p-p
Input Capacitance2 Full 8 8 pF
VREF INPUT RESISTANCE Full 6 6 kΩ
POWER SUPPLIES
Supply Voltage
AVDD, DVDD Full 1.7 1.8 1.9 1.7 1.8 1.9 V
DRVDD (CMOS Mode) Full 1.7 3.3 3.6 1.7 3.3 3.6 V
DRVDD (LVDS Mode) Full 1.7 1.8 1.9 1.7 1.8 1.9 V
Supply Current
IAVDD1, 3 Full 385
470 419 517 mA
IDVDD1, 3 Full 42 50 mA
IDRVDD1 (3.3 V CMOS) Full 44 53 mA
IDRVDD1 (1.8 V CMOS) Full 22 27 mA
IDRVDD1 (1.8 V LVDS) 56 57
POWER CONSUMPTION
DC Input Full 750 846 820 938 mW
Sine Wave Input1 (DRVDD = 1.8 V) Full 810 895 mW
Sine Wave Input1 (DRVDD = 3.3 V) Full 910 1000 mW
Standby Power4 Full 77 77 mW
Power-Down Power Full 2.5 6 2.5 6 mW
1 Measured with a low input frequency, full-scale sine wave, with approximately 5 pF loading on each output bit.
2 Input capacitance refers to the effective capacitance between one differential input pin and AGND. See Figure 8 for the equivalent analog input structure.
3 The maximum limit applies to the combination of IAVDD and IDVDD currents.
4 Standby power is measured with a dc input and with the CLK pins (CLK+, CLK−) inactive (set to AVDD or AGND).
AD9640
Rev. B | Page 7 of 52
ADC AC SPECIFICATIONS—AD9640ABCPZ-80, AD9640BCPZ-80, AD9640ABCPZ-105, AND AD9640BCPZ-105
AVDD = 1.8 V, DVDD = 1.8 V, DRVDD = 3.3 V, maximum sample rate, VIN = −1.0 dBFS differential input, 1.0 V internal reference,
DCS enabled, fast detect outputs disabled, and signal monitor disabled, unless otherwise noted.
Table 3.
Parameter1 Temperature
AD9640ABCPZ-80/
AD9640BCPZ-80
AD9640ABCPZ-105/
AD9640BCPZ-105
Unit
Min Typ Max Min Typ Max
SIGNAL-TO-NOISE RATIO (SNR)
fIN = 2.3 MHz 25°C 72.5 72.3 dB
fIN = 70 MHz 25°C 72.1 71.9 dB
Full 70.5 70.2 dB
fIN = 140 MHz 25°C 71.6 71.3 dB
fIN = 200 MHz 25°C 71.0 70.3 dB
SIGNAL-TO-NOISE AND DISTORTION (SINAD)
fIN = 2.3 MHz 25°C 72.2 72.0 dB
fIN = 70 MHz 25°C 71.6 71.6 dB
Full 69 69.5 dB
fIN = 140 MHz 25°C 71.1 70.9 dB
fIN = 200 MHz 25°C 70.4 70.0 dB
EFFECTIVE NUMBER OF BITS (ENOB)
fIN = 2.3 MHz 25°C 11.9 11.8 Bits
fIN = 70 MHz 25°C 11.8 11.8 Bits
fIN = 140 MHz 25°C 11.7 11.7 Bits
fIN = 200 MHz 25°C 11.6 11.5 Bits
WORST SECOND OR THIRD HARMONIC
fIN = 2.3 MHz 25°C −87 −87 dBc
fIN = 70 MHz 25°C −85 −85 dBc
Full −75 −74 dBc
fIN = 140 MHz 25°C −84 −84 dBc
fIN = 200 MHz 25°C −83 −83 dBc
SPURIOUS-FREE DYNAMIC RANGE (SFDR)
fIN = 2.3 MHz 25°C 87 87 dBc
fIN = 70 MHz 25°C 85 85 dBc
Full 75 74 dBc
fIN = 140 MHz 25°C 84 84 dBc
fIN = 200 MHz 25°C 83 83 dBc
WORST OTHER HARMONIC OR SPUR
fIN = 2.3 MHz 25°C −93 −93 dBc
fIN = 70 MHz 25°C −89 −89 dBc
Full −82 −81 dBc
fIN = 140 MHz 25°C −89 −89 dBc
fIN = 200 MHz 25°C −89 −89 dBc
TWO TONE SFDR
fIN = 29.1 MHz, 32.1 MHz (−7 dBFS) 25°C 85 85 dBc
fIN = 169.1 MHz, 172.1 MHz (−7 dBFS) 25°C 82 82 dBc
CROSSTALK2 Full −95 −95 dB
ANALOG INPUT BANDWIDTH 25°C 650 650 MHz
1 See Application Note AN-835, Understanding High Speed ADC Testing and Evaluation, for a complete set of definitions.
2 Crosstalk is measured at 100 MHz with −1 dBFS on one channel and no input on the alternate channel.
AD9640
Rev. B | Page 8 of 52
ADC AC SPECIFICATIONS—AD9640ABCPZ-125, AD9640BCPZ-125, AD9640ABCPZ-150, AND AD9640BCPZ 150
AVDD = 1.8 V, DVDD = 1.8 V, DRVDD = 3.3 V, maximum sample rate, VIN = −1.0 dBFS differential input, 1.0 V internal reference,
DCS enabled, fast detect outputs disabled, and signal monitor disabled, unless otherwise noted.
Table 4.
Parameter1 Temperature
AD9640ABCPZ-125
AD9640BCPZ-125
AD9640ABCPZ-150/
AD9640BCPZ-150
Unit
Min Typ Max Min Typ Max
SIGNAL-TO-NOISE RATIO (SNR)
fIN = 2.3 MHz 25°C 72.1 71.9 dB
fIN = 70 MHz 25°C 71.8 71.6 dB
Full 70.2 69.5 dB
fIN = 140 MHz 25°C 71.4 70.9 dB
fIN = 200 MHz 25°C 70.8 70.0 dB
SIGNAL-TO-NOISE AND DISTORTION (SINAD)
fIN = 2.3 MHz 25°C 71.8 71.6 dB
fIN = 70 MHz 25°C 71.4 71.0 dB
Full 69.5 67.5 dB
fIN = 140 MHz 25°C 71.0 70.5 dB
fIN = 200 MHz 25°C 70.3 69.9 dB
EFFECTIVE NUMBER OF BITS (ENOB)
fIN = 2.3 MHz 25°C 11.8 11.8 Bits
fIN = 70 MHz 25°C 11.7 11.8 Bits
fIN = 140 MHz 25°C 11.7 11.6 Bits
fIN = 200 MHz 25°C 11.6 11.5 Bits
WORST SECOND OR THIRD HARMONIC
fIN = 2.3 MHz 25°C −86.5 −86.5 dBc
fIN = 70 MHz 25°C −85 −84 dBc
Full −74 −73 dBc
fIN = 140 MHz 25°C −84 −83.5 dBc
fIN = 200 MHz 25°C −83 −77 dBc
SPURIOUS-FREE DYNAMIC RANGE (SFDR)
fIN = 2.3 MHz 25°C 86.5 86.5 dBc
fIN = 70 MHz 25°C 85 84 dBc
Full 74 73 dBc
fIN = 140 MHz 25°C 84 83.5 dBc
fIN = 200 MHz 25°C 83 77 dBc
WORST OTHER HARMONIC OR SPUR
fIN = 2.3 MHz 25°C −92 −92 dBc
fIN = 70 MHz 25°C −89 −90 dBc
Full −80 −80 dBc
fIN = 140 MHz 25°C −89 −90 dBc
fIN = 200 MHz 25°C −89 −90 dBc
TWO TONE SFDR
fIN = 29.1 MHz, 32.1 MHz (−7 dBFS) 25°C 85 85 dBc
fIN = 169.1 MHz, 172.1 MHz (−7 dBFS) 25°C 82 82 dBc
CROSSTALK2 Full −95 −95 dB
ANALOG INPUT BANDWIDTH 25°C 650 650 MHz
1 See the AN-835 Application Note, Understanding High Speed ADC Testing and Evaluation, for a complete set of definitions.
2 Crosstalk is measured at 100 MHz with −1 dBFS on one channel and no input on the alternate channel.
AD9640
Rev. B | Page 9 of 52
DIGITAL SPECIFICATIONS
AVDD = 1.8 V, DVDD = 1.8 V, DRVDD = 3.3 V, maximum sample rate, VIN = −1.0 dBFS differential input, 1.0 V internal reference, and
DCS enabled, unless otherwise noted.
Table 5.
Parameter Temperature Min Typ Max Unit
DIFFERENTIAL CLOCK INPUTS (CLK+, CLK−)
Logic Compliance CMOS/LVDS/LVPECL
Internal Common-Mode Bias Full 1.2 V
Differential Input Voltage Full 0.2 6 V p-p
Input Voltage Range Full AGND − 0.3 AVDD + 1.6 V
Input Common-Mode Range Full 1.1 AVDD V
High Level Input Voltage Full 1.2 3.6 V
Low Level Input Voltage Full 0 0.8 V
High Level Input Current Full −10 +10 μA
Low Level Input Current Full −10 +10 μA
Input Capacitance Full 4 pF
Input Resistance Full 8 10 12 kΩ
SYNC INPUT
Logic Compliance CMOS
Internal Bias Full 1.2 V
Input Voltage Range Full AGND − 0.3 AVDD + 1.6 V
High Level Input Voltage Full 1.2 3.6 V
Low Level Input Voltage Full 0 0.8 V
High Level Input Current Full −10 +10 μA
Low Level Input Current Full −10 +10 μA
Input Capacitance Full 4 pF
Input Resistance Full 8 10 12 kΩ
LOGIC INPUT (CSB)1
High Level Input Voltage Full 1.22 3.6 V
Low Level Input Voltage Full 0 0.6 V
High Level Input Current Full −10 +10 μA
Low Level Input Current Full 40 132 μA
Input Resistance Full 26 kΩ
Input Capacitance Full 2 pF
LOGIC INPUT (SCLK/DFS)2
High Level Input Voltage Full 1.22 3.6 V
Low Level Input Voltage Full 0 0.6 V
High Level Input Current (VIN = 3.3 V) Full −92 −135 μA
Low Level Input Current Full −10 +10 μA
Input Resistance Full 26 kΩ
Input Capacitance Full 2 pF
LOGIC INPUTS/OUTPUTS (SDIO/DCS, SMI SDFS)1
High Level Input Voltage Full 1.22 3.6 V
Low Level Input Voltage Full 0 0.6 V
High Level Input Current Full −10 +10 μA
Low Level Input Current Full 38 128 μA
Input Resistance Full 26 kΩ
Input Capacitance Full 5 pF
LOGIC INPUTS/OUTPUTS (SMI SDO/OEB, SMI SCLK/PDWN)2
High Level Input Voltage Full 1.22 3.6 V
Low Level Input Voltage Full 0 0.6 V
High Level Input Current (VIN = 3.3 V) Full −90 −134 μA
Low Level Input Current Full −10 +10 μA
Input Resistance Full 26 kΩ
Input Capacitance Full 5 pF
AD9640
Rev. B | Page 10 of 52
Parameter Temperature Min Typ Max Unit
DIGITAL OUTPUTS
CMOS Mode—DRVDD = 3.3 V
High Level Output Voltage (IOH = 50 μA) Full 3.29 V
High Level Output Voltage (IOH = 0.5 mA) Full 3.25 V
Low Level Output Voltage (IOL = 1.6 mA) Full 0.2 V
Low Level Output Voltage (IOL = 50 μA) Full 0.05 V
CMOS Mode—DRVDD = 1.8 V
High Level Output Voltage (IOH = 50 μA) Full 1.79 V
High Level Output Voltage (IOH = 0.5 mA) Full 1.75 V
Low Level Output Voltage (IOL = 1.6 mA) Full 0.2 V
Low Level Output Voltage (IOL = 50 μA) Full 0.05 V
LVDS Mode—DRVDD = 1.8 V
Differential Output Voltage (VOD), ANSI Mode Full 250 350 450 mV
Output Offset Voltage (VOS), ANSI Mode Full 1.15 1.25 1.35 V
Differential Output Voltage (VOD), Reduced Swing Mode Full 150 200 280 mV
Output Offset Voltage (VOS), Reduced Swing Mode Full 1.15 1.25 1.35 V
1 Pull up.
2 Pull down.
SWITCHING SPECIFICATIONS—AD9640ABCPZ-80, AD9640BCPZ-80, AD9640ABCPZ-105, AND
AD9640BCPZ-105
AVDD = 1.8 V, DVDD = 1.8 V, DRVDD = 3.3 V, maximum sample rate, VIN = −1.0 dBFS differential input, 1.0 V internal reference,
DCS enabled, unless otherwise noted.
Table 6.
Parameter Temp
AD9640ABCPZ-80
AD9640BCPZ-80
AD9640ABCPZ-105/
AD9640BCPZ-105
Unit
Min Typ Max Min Typ Max
CLOCK INPUT PARAMETERS
Input Clock Rate Full 625 625 MHz
Conversion Rate
DCS Enabled1 Full 20 80 20 105 MSPS
DCS Disabled1 Full 10 80 10 105 MSPS
CLK Period—Divide by 1 Mode (tCLK) Full 12.5 9.5 ns
CLK Pulse Width High
Divide by 1 Mode, DCS Enabled Full 3.75 6.25 8.75 2.85 4.75 6.65 ns
Divide by 1 Mode, DCS Disabled Full 5.63 6.25 6.88 4.28 4.75 5.23 ns
Divide by 2 Mode, DCS Enabled Full 1.6 1.6 ns
Divide by 3 Through 8, DCS Enabled Full 0.8 0.8 ns
DATA OUTPUT PARAMETERS (DATA, FD)
CMOS Mode—DRVDD = 3.3 V
Data Propagation Delay (tPD)2 Full 2.2 4.5 6.4 2.2 4.5 6.4 ns
DCO Propagation Delay (tDCO) Full 3.8 5.0 6.8 3.8 5.0 6.8 ns
Setup Time (tS) Full 6.25 5.25 ns
Hold Time (tH) Full 5.75 4.25 ns
CMOS Mode—DRVDD = 1.8 V
Data Propagation Delay (tPD)2 Full 2.4 5.2 6.9 2.4 5.2 6.9 ns
DCO Propagation Delay (tDCO) Full 4.0 5.6 7.3 4.0 5.6 7.3 ns
LVDS Mode—DRVDD = 1.8 V
Data Propagation Delay (tPD)2 Full 3.0 3.7 4.4 3.0 3.7 4.4 ns
DCO Propagation Delay (tDCO) Full 5.4 7.0 8.4 5.2 6.4 7.6 ns
AD9640
Rev. B | Page 11 of 52
Parameter Temp
AD9640ABCPZ-80
AD9640BCPZ-80
AD9640ABCPZ-105/
AD9640BCPZ-105
Unit
Min Typ Max Min Typ Max
CMOS Mode Pipeline Delay (Latency) Full 12 12 Cycles
LVDS Mode Pipeline Delay (Latency)
Channel A/Channel B
12/12.5 12/12.5 Cycles
Aperture Delay (tA) Full 1.0 1.0 ns
Aperture Uncertainty (Jitter, tJ) Full 0.1 0.1 ps rms
Wake-Up Time3 Full 350 350 μs
OUT-OF-RANGE RECOVERY TIME Full 2 2 Cycles
1 Conversion rate is the clock rate after the divider.
2 Output propagation delay is measured from CLK 50% transition to DATA 50% transition, with 5 pF load.
3 Wake-up time is dependent on the value of the decoupling capacitors.
SWITCHING SPECIFICATIONS—AD9640ABCPZ-125, AD9640BCPZ-125, AD9640ABCPZ-150, AND
AD9640BCPZ-150
AVDD = 1.8 V, DVDD = 1.8V, DRVDD = 3.3 V, maximum sample rate, VIN = −1.0 dBFS differential input, 1.0 V internal reference, DCS
enabled, unless otherwise noted.
Table 7.
Parameter Temperature
AD9640ABCPZ-125/
AD9640BCPZ-125
AD9640ABCPZ-150/
AD9640BCPZ-150
Unit
Min Typ Max Min Typ Max
CLOCK INPUT PARAMETERS
Input Clock Rate Full 625 625 MHz
Conversion Rate
DCS Enabled1 Full 20 125 20 150 MSPS
DCS Disabled1 Full 10 125 10 150 MSPS
CLK Period—Divide by 1 Mode (tCLK) Full 8 6.66 ns
CLK Pulse Width High
Divide by 1 Mode, DCS Enabled Full 2.4 4 5.6 2.0 3.33 4.66 ns
Divide by 1 Mode, DCS Disabled Full 3.6 4 4.4 3.0 3.33 3.66 ns
Divide by 2 Mode, DCS Enabled Full 1.6 1.6 ns
Divide by 3 Through 8, DCS Enabled Full 0.8 0.8 ns
DATA OUTPUT PARAMETERS (DATA, FD)
CMOS Mode—DRVDD = 3.3 V
Data Propagation Delay (tPD)2 Full 2.2 4.5 6.4 2.2 4.5 6.4 ns
DCO Propagation Delay (tDCO) Full 3.8 5.0 6.8 3.8 5.0 6.8 ns
Setup Time (tS) Full 4.5 3.83 ns
Hold Time (tH) Full 3.5 2.83 ns
CMOS Mode—DRVDD = 1.8 V
Data Propagation Delay (tPD)2 Full 2.4 5.2 6.9 2.4 5.2 6.9 ns
DCO Propagation Delay (tDCO) Full 4.0 5.6 7.3 4.0 5.6 7.3 ns
LVDS Mode—DRVDD = 1.8 V
Data Propagation Delay (tPD)2 Full 3.0 3.8 4.5 3.0 3.8 4.5 ns
DCO Propagation Delay (tDCO) Full 5.0 6.2 7.4 4.8 5.9 7.3 ns
CMOS Mode Pipeline Delay (Latency) Full 12 12 Cycles
LVDS Mode Pipeline Delay (Latency)
Channel A/Channel B
12/12.5 12/12.5 Cycles
Aperture Delay (tA) Full 1.0 1.0 ns
Aperture Uncertainty (Jitter, tJ) Full 0.1 0.1 ps rms
Wake-Up Time3 Full 350 350 μs
OUT-OF-RANGE RECOVERY TIME Full 3 3 Cycles
1 Conversion rate is the clock rate after the divider.
2 Output propagation delay is measured from CLK 50% transition to DATA 50% transition, with 5 pF load.
3 Wake-up time is dependent on the value of the decoupling capacitors.
AD9640
Rev. B | Page 12 of 52
TIMING SPECIFICATIONS
Table 8.
Parameter Conditions Min Typ Max Unit
SYNC TIMING REQUIREMENTS
tSSYNC SYNC to rising edge of CLK setup time 0.24 ns
tHSYNC SYNC to rising edge of CLK hold time 0.40 ns
SPI TIMING REQUIREMENTS
tDS Setup time between the data and the rising edge of SCLK 2 ns
tDH Hold time between the data and the rising edge of SCLK 2 ns
tCLK Period of the SCLK 40 ns
tS Setup time between CSB and SCLK 2 ns
tH Hold time between CSB and SCLK 2 ns
tHIGH SCLK pulse width high 10 ns
tLOW SCLK pulse width low 10 ns
tEN_SDIO Time required for the SDIO pin to switch from an input to an
output relative to the SCLK falling edge
10 ns
tDIS_SDIO Time required for the SDIO pin to switch from an output to
an input relative to the SCLK rising edge
10 ns
SPORT TIMING REQUIREMENTS
tCSSCLK Delay from rising edge of CLK+ to rising edge of SMI SCLK 3.2 4.5 6.2 ns
tSSCLKSDO Delay from rising edge of SMI SCLK to SMI SDO −0.4 0 +0.4 ns
tSSCLKSDFS Delay from rising edge of SMI SCLK to SMI SDFS −0.4 0 +0.4 ns
Timing Diagrams
CLK+
DCOA/DCOB
C
H A/ B DAT
A
N
N+ 1 N+2
N+ 3
N+ 4
N+ 5 N+ 6 N+ 7
N+ 8
N – 12 N – 11 N – 9 N – 8 N – 7 N – 6 N – 5 N – 4
N – 13
CLK–
t
CLK
t
PD
t
S
t
H
t
DCO
t
CLK
t
A
CH A/B FAST
DETECT N – 1 N + 2 N + 3 N + 4 N + 5 N + 6N – 3 N – 2
06547-021
N – 10
N + 1
N
Figure 2. CMOS Output Mode Data and Fast Detect Output Timing (Fast Detect Mode 0)
AD9640
Rev. B | Page 13 of 52
CLK+
DCO–
DCO+
C
H A/CH B DAT
A
N
N + 1 N + 2
N + 3
N + 4
N + 5 N + 6 N + 7
N + 8
N – 12 N – 11 N – 9 N – 8 N – 7 N – 6 N – 5 N – 4
N – 13
CLK–
t
CLK
t
PD
t
CLK
t
A
CH A/CH B FAST
DETECT
ABABABABABABABABA AB
N – 10
N – 6 N – 5 N – 3 N – 2 N – 1 N N + 1 N + 2N – 7
ABABABABABABABABA AB
N – 4
t
DCO
06547-089
Figure 3. LVDS Mode Data and Fast Detect Output Timing (Fast Detect Mode 1 Through Fast Detect Mode 5)
SYNC
CLK+
tHSYNC
tSSYNC
06547-072
Figure 4. SYNC Input Timing Requirements
CLK+
SMI SCLK
SMI SDFS
06547-082
DATA DATASMI SDO
CLK– t
CSSCLK
t
SSCLKSDFS
t
SSCLKSDO
Figure 5. Signal Monitor SPORT Output Timing (Divide by 2 Mode)
AD9640
Rev. B | Page 14 of 52
ABSOLUTE MAXIMUM RATINGS
THERMAL CHARACTERISTICS
Table 9.
Parameter Rating
ELECTRICAL
AVDD, DVDD to AGND −0.3 V to +2.0 V
DRVDD to DRGND −0.3 V to +3.9 V
AGND to DRGND −0.3 V to +0.3 V
AVDD to DRVDD −3.9 V to +2.0 V
VIN+A/VIN+B, VIN−A/VIN−B to AGND −0.3 V to AVDD + 0.2 V
CLK+, CLK− to AGND −0.3 V to +3.9 V
SYNC to AGND −0.3 V to +3.9 V
VREF to AGND −0.3 V to AVDD + 0.2 V
SENSE to AGND −0.3 V to AVDD + 0.2 V
CML to AGND −0.3 V to AVDD + 0.2 V
RBIAS to AGND −0.3 V to AVDD + 0.2 V
CSB to AGND −0.3 V to +3.9 V
SCLK/DFS to DRGND −0.3 V to +3.9 V
SDIO/DCS to DRGND −0.3 V to DRVDD + 0.3 V
SMI SDO/OEB −0.3 V to DRVDD + 0.3 V
SMI SCLK/PDWN −0.3 V to DRVDD + 0.3 V
SMI SDFS −0.3 V to DRVDD + 0.3 V
D0A/D0B through D13A/D13B to
DRGND
−0.3 V to DRVDD + 0.3 V
FD0A/FD0B through FD3A/FD3B to
DRGND
−0.3 V to DRVDD + 0.3 V
DCOA/DCOB to DRGND
−0.3 V to DRVDD + 0.3 V
ENVIRONMENTAL
Operating Temperature Range
(Ambient)
−40°C to +85°C
Maximum Junction Temperature
Under Bias
150°C
Storage Temperature Range
(Ambient)
−65°C to +150°C
The exposed paddle must be soldered to the ground plane for
the LFCSP package. Soldering the exposed paddle to the customer
board increases the reliability of the solder joints and maximizes
the thermal capability of the package.
Table 10. Thermal Resistance
Package
Type
Airflow
Velocity
(m/s) θJA1, 2 θJC1, 3 θJB1, 4 Unit
64-lead LFCSP
9 mm × 9 mm
0 18.8 0.6 6.0 °C/W
1.0 16.5 °C/W
2.0 15.8 °C/W
1 JEDEC 51-7, plus JEDEC 25-5 2S2P test board.
2 Per JEDEC JESD51-2 (still air) or JEDEC JESD51-6 (moving air).
3 Per MIL-Std 883, Method 1012.1.
4 Per JEDEC JESD51-8 (still air).
Typical θJA is specified for a 4-layer PCB with a solid ground
plane. As shown, airflow improves heat dissipation, which
reduces θJA. In addition, metal in direct contact with the
package leads from metal traces, through holes, ground, and
power planes, reduces the θJA.
ESD CAUTION
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
AD9640
Rev. B | Page 15 of 52
NOTES
1. NC = NO CONNE CT.
2. THE EX POSE D THERMAL PAD ON T HE BOTTO M OF THE PACKAGE PROVIDES THE
ANALO G G ROUND FO R THE PART. THIS E X P OSED PAD MUST BE CO NNECTED TO
GROUND FOR PROPER OPERATION.
PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
D5A
D6A
D7A
DRGND
DRVDD
D8A
D9A
DVDD
D10A
D11A
D12A
D13 A (MSB)
FD0A
FD1A
FD2A
FD3A
64
63
62
61
60
59
58
57
56
55
54
53
52
51
50
49
DRGND
D5B
D4B
D3B
D2B
D1B
D0B (L S B)
DVDD
FD3B
FD2B
FD1B
FD0B
SYNC
CSB
CLK–
CLK+
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
DRVDD
D6B
D7B
D8B
D9B
D10B
D11B
D12B
D13B (MSB)
DCOB
DCOA
D0A (LS B)
D1A
D2A
D3A
D4A
SCLK/DFS
SDIO/DCS
AVDD
AVDD
VIN+B
VIN–B
RBIAS
CML
SENSE
VREF
VIN–A
VIN+A
AVDD
SMI SDFS
SMI SCLK/PDWN
SMI SDO /OEB
48
47
46
45
44
43
42
41
40
39
38
37
36
35
34
33
06547-002
PIN 1
INDICATOR
AD9640
PARALL EL CMOS
TOP VIEW
(No t t o S cale)
EXPOSED P ADDLE, P IN 0
(BOTTOM OF P ACKAGE)
Figure 6. Pin Configuration, LFCSP Parallel CMOS (Top View)
Table 11. Pin Function Descriptions (Parallel CMOS Mode)
Pin No. Mnemonic Type Description
ADC Power Supplies
20, 64 DRGND Ground Digital Output Ground.
1, 21 DRVDD Supply Digital Output Driver Supply (1.8 V to 3.3 V).
24, 57 DVDD Supply Digital Power Supply (1.8 V Nominal).
36, 45, 46 AVDD Supply Analog Power Supply (1.8 V Nominal).
0 AGND,
Exposed Pad
Ground The exposed thermal pad on the bottom of the package provides the analog ground
for the part. This exposed pad must be connected to ground for proper operation.
ADC Analog
37 VIN+A Input Differential Analog Input Pin (+) for Channel A.
38 VIN−A Input Differential Analog Input Pin (−) for Channel A.
44 VIN+B Input Differential Analog Input Pin (+) for Channel B.
43 VIN−B Input Differential Analog Input Pin (−) for Channel B.
39 VREF Input/Output Voltage Reference Input/Output.
40 SENSE Input Voltage Reference Mode Select. See Table 14 for details.
42 RBIAS Input/Output External Reference Bias Resistor.
41 CML Output Common Mode Level Bias Output for Analog Inputs.
49 CLK+ Input ADC Clock Input—True.
50 CLK− Input ADC Clock Input—Complement.
AD9640
Rev. B | Page 16 of 52
Pin No. Mnemonic Type Description
ADC Fast Detect Outputs
29 FD0A Output Channel A Fast Detect Indicator. See Table 18 for details.
30 FD1A Output Channel A Fast Detect Indicator. See Table 18 for details.
31 FD2A Output Channel A Fast Detect Indicator. See Table 18 for details.
32 FD3A Output Channel A Fast Detect Indicator. See Table 18 for details.
53 FD0B Output Channel B Fast Detect Indicator. See Table 18 for details.
54 FD1B Output Channel B Fast Detect Indicator. See Table 18 for details.
55 FD2B Output Channel B Fast Detect Indicator. See Table 18 for details.
56 FD3B Output Channel B Fast Detect Indicator. See Table 18 for details.
Digital Inputs
52 SYNC Input Digital Synchronization Pin. Slave mode only.
Digital Outputs
12 D0A (LSB) Output Channel A CMOS Output Data.
13 D1A Output Channel A CMOS Output Data.
14 D2A Output Channel A CMOS Output Data.
15 D3A Output Channel A CMOS Output Data.
16 D4A Output Channel A CMOS Output Data.
17 D5A Output Channel A CMOS Output Data.
18 D6A Output Channel A CMOS Output Data.
19 D7A Output Channel A CMOS Output Data.
22 D8A Output Channel A CMOS Output Data.
23 D9A Output Channel A CMOS Output Data.
25 D10A Output Channel A CMOS Output Data.
26 D11A Output Channel A CMOS Output Data.
27 D12A Output Channel A CMOS Output Data.
28 D13A (MSB) Output Channel A CMOS Output Data.
58 D0B (LSB) Output Channel B CMOS Output Data.
59 D1B Output Channel B CMOS Output Data.
60 D2B Output Channel B CMOS Output Data.
61 D3B Output Channel B CMOS Output Data.
62 D4B Output Channel B CMOS Output Data.
63 D5B Output Channel B CMOS Output Data.
2 D6B Output Channel B CMOS Output Data.
3 D7B Output Channel B CMOS Output Data.
4 D8B Output Channel B CMOS Output Data.
5 D9B Output Channel B CMOS Output Data.
6 D10B Output Channel B CMOS Output Data.
7 D11B Output Channel B CMOS Output Data.
8 D12B Output Channel B CMOS Output Data.
9 D13B (MSB) Output Channel B CMOS Output Data.
11 DCOA Output Channel A Data Clock Output.
10 DCOB Output Channel B Data Clock Output.
SPI Control
48 SCLK/DFS Input SPI Serial Clock/Data Format Select Pin in External Pin Mode.
47 SDIO/DCS Input/Output SPI Serial Data I/O/Duty Cycle Stabilizer in External Pin Mode.
51 CSB Input SPI Chip Select (Active Low).
Serial Port
33 SMI SDO/OEB Input/Output Signal Monitor Serial Data Output/Output Enable Input (Active Low) in External Pin Mode.
35 SMI SDFS Output Signal Monitor Serial Data Frame Sync.
34 SMI SCLK/PDWN Input/Output Signal Monitor Serial Clock Output/Power-Down Input in External Pin Mode.
AD9640
Rev. B | Page 17 of 52
PIN 1
INDICATOR
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
D7+
D8–
D8+
DRGND
DRVDD
D9–
D9+
DVDD
D10–
D10+
D11–
D11+
D12–
D12+
(MS B)
+ (M SB)
64
63
62
61
60
59
58
57
56
55
54
53
52
51
50
49
DRGND
D0+ (LSB)
D0– (L S B )
FD3+
FD3–
FD2+
FD2–
DVDD
FD1+
FD1–
FD0+
FD0–
SYNC
CSB
CLK–
CLK+
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
DRVDD
D1–
D1+
D2–
D2+
D3–
D3+
D4–
D4+
DCO–
DCO+
D5–
D5+
D6–
D6+
D7–
SCLK/DFS
SDIO/DCS
AVDD
AVDD
VIN+B
VIN–B
RBIAS
CML
SENSE
VREF
VIN–A
VIN+A
AVDD
SMI S DF S
SMI SCLK/PDWN
SMI SDO/OEB
48
47
46
45
44
43
42
41
40
39
38
37
36
35
34
33
D13–
D13
AD9640
PARALLEL LVDS
TOP VIEW
(Not to Scale)
EXPOSED PADDLE, PIN 0
(BOTTO M O F PACKAG E)
06547-003
NOTES
1. NC = NO CONNE C T.
2. THE EXPOSED THERMAL PAD ON THE BOTTOM OF THE PACKAGE PROVIDES
THE ANALO G GROUND FO R THE PART. THIS E X P OSED PAD MUST BE
CONNECTED TO GROUND FOR PRO P E R OPERATI ON.
Figure 7. Pin Configuration, LFCSP LVDS (Top View)
Table 12. Pin Function Descriptions (Interleaved Parallel LVDS Mode)
Pin No. Mnemonic Type Function
ADC Power Supplies
20, 64 DRGND Ground Digital Output Ground.
1, 21 DRVDD Supply Digital Output Driver Supply (1.8 V to 3.3 V).
24, 57 DVDD Supply Digital Power Supply (1.8 V Nominal).
36, 45, 46 AVDD Supply Analog Power Supply (1.8 V Nominal).
0 AGND,
Exposed Pad
Ground The exposed thermal pad on the bottom of the package provides the analog ground for the
part. This exposed pad must be connected to ground for proper operation.
ADC Analog
37 VIN+A Input Differential Analog Input Pin (+) for Channel A.
38 VIN−A Input Differential Analog Input Pin (−) for Channel A.
44 VIN+B Input Differential Analog Input Pin (+) for Channel B.
43 VIN−B Input Differential Analog Input Pin (−) for Channel B.
39 VREF Input/Output Voltage Reference Input/Output.
40 SENSE Input Voltage Reference Mode Select. See Table 14 for details.
42 RBIAS Input/Output External Reference Bias Resistor.
41 CML Output Common-Mode Level Bias Output for Analog Inputs.
49 CLK+ Input ADC Clock Input—True.
50 CLK− Input ADC Clock Input—Complement.
ADC Fast Detect Outputs
54 FD0+ Output Channel A/Channel B LVDS Fast Detect Indicator 0—True. See Table 18 for details.
53 FD0− Output Channel A/Channel B LVDS Fast Detect Indicator 0—Complement. See Table 18 for details.
56 FD1+ Output Channel A/Channel B LVDS Fast Detect Indicator 1—True. See Table 18 for details.
55 FD1− Output Channel A/Channel B LVDS Fast Detect Indicator 1—Complement. See Table 18 for details.
59 FD2+ Output Channel A/Channel B LVDS Fast Detect Indicator 2—True. See Table 18 for details.
58 FD2− Output Channel A/Channel B LVDS Fast Detect Indicator 2—Complement. See Table 18 for details.
61 FD3+ Output Channel A/Channel B LVDS Fast Detect Indicator 3—True. See Table 18 for details.
60 FD3− Output Channel A/Channel B LVDS Fast Detect Indicator 3—Complement. See Table 18 for details.
AD9640
Rev. B | Page 18 of 52
Pin No. Mnemonic Type Function
Digital Inputs
52 SYNC Input Digital Synchronization Pin. Slave mode only.
Digital Outputs
63 D0+ (LSB) Output Channel A/Channel B LVDS Output Data 0—True.
62 D0− (LSB) Output Channel A/Channel B LVDS Output Data 0—Complement.
3 D1+ Output Channel A/Channel B LVDS Output Data 1—True.
2 D1− Output Channel A/Channel B LVDS Output Data 1—Complement.
5 D2+ Output Channel A/Channel B LVDS Output Data 2—True.
4 D2− Output Channel A/Channel B LVDS Output Data 2—Complement.
7 D3+ Output Channel A/Channel B LVDS Output Data 3—True.
6 D3− Output Channel A/Channel B LVDS Output Data 3—Complement.
9 D4+ Output Channel A/Channel B LVDS Output Data 4—True.
8 D4− Output Channel A/Channel B LVDS Output Data 4—Complement.
13 D5+ Output Channel A/Channel B LVDS Output Data 5—True.
12 D5− Output Channel A/Channel B LVDS Output Data 5—Complement.
15 D6+ Output Channel A/Channel B LVDS Output Data 6 —True.
14 D6− Output Channel A/Channel B LVDS Output Data 6—Complement.
17 D7+ Output Channel A/Channel B LVDS Output Data 7—True.
16 D7− Output Channel A/Channel B LVDS Output Data 7—Complement.
19 D8+ Output Channel A/Channel B LVDS Output Data 8—True.
18 D8− Output Channel A/Channel B LVDS Output Data 8—Complement.
23 D9+ Output Channel A/Channel B LVDS Output Data 9—True.
22 D9− Output Channel A/Channel B LVDS Output Data 9—Complement.
26 D10+ Output Channel A/Channel B LVDS Output Data 10—True.
25 D10− Output Channel A/Channel B LVDS Output Data 10—Complement.
28 D11+ Output Channel A/Channel B LVDS Output Data 11—True.
27 D11− Output Channel A/Channel B LVDS Output Data 11—Complement.
30 D12+ Output Channel A/Channel B LVDS Output Data 12—True.
29 D12− Output Channel A/Channel B LVDS Output Data 12—Complement.
32 D13+ (MSB) Output Channel A/Channel B LVDS Output Data 13—True.
31 D13− (MSB) Output Channel A/Channel B LVDS Output Data 13—Complement.
11 DCO+ Output Channel A/Channel B LVDS Data Clock Output—True.
10 DCO− Output Channel A/Channel B LVDS Data Clock Output—Complement.
SPI Control
48 SCLK/DFS Input SPI Serial Clock/Data Format Select Pin in External Pin Mode.
47 SDIO/DCS Input/Output SPI Serial Data I/O/Duty Cycle Stabilizer in External Pin Mode.
51 CSB Input SPI Chip Select (Active Low).
Signal Monitor Ports
33 SMI SDO/OEB Input/Output Signal Monitor Serial Data Output/Output Enable Input (Active Low) in External Pin Mode.
35 SMI SDFS Output Signal Monitor Serial Data Frame Sync.
34 SMI SCLK/PDWN Input/Output Signal Monitor Serial Clock Output/Power-Down Input in External Pin Mode.
AD9640
Rev. B | Page 19 of 52
EQUIVALENT CIRCUITS
V
IN
06547-004
Figure 8. Equivalent Analog Input Circuit
1.2V
10kΩ10kΩ
C
LK+ CLK–
AVDD
06547-005
Figure 9. Equivalent Clock Input Circuit
0
6547-081
DRVDD
DRGND
Figure 10. Digital Output
SDIO/DCS 1kΩ
26kΩ
06547-007
DRVDD
DVDD
DRVDD
DVDD
Figure 11. Equivalent SDIO/DCS or SMI SDFS Circuit
06547-011
DVDD
SCLK/DFS 1kΩ
26kΩ
Figure 12. Equivalent SCLK/DFS Input Circuit
SENSE 1kΩ
06547-009
Figure 13. Equivalent SENSE Circuit
CSB 1kΩ
26kΩ
DVDD
06547-010
DVDD
Figure 14. Equivalent CSB Input Circuit
06547-096
V
REF
AVDD
6kΩ
Figure 15. Equivalent VREF Circuit
AD9640
Rev. B | Page 20 of 52
TYPICAL PERFORMANCE CHARACTERISTICS
AVDD = 1.8 V; DVDD = 1.8 V; DRVDD = 3.3 V; sample rate = 150 MSPS, DCS enabled, 1 V internal reference;
2 V p-p differential input; VIN = −1.0 dBFS; and 64k sample; TA = 25°C, unless otherwise noted.
0
–120 0
06547-050
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 7060
150MSPS
2.3M Hz @ –1d BFS
SNR = 71.9d Bc ( 72.9d BFS)
ENOB = 11.8 BIT S
SFDR = 86dBc
SECO ND HARMONIC
THIRD HARMONIC
Figure 16. AD9640-150 Single-Tone FFT with fIN = 2.3 MHz
0
–120 0
06547-051
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 7060
150MSPS
30.3M Hz @ –1dBF S
SNR = 71.7d Bc ( 72.7d BFS)
ENOB = 11.8 BIT S
SFDR = 89.9d Bc
SECO ND HARMONIC
THIRD HARMONIC
Figure 17. AD9640-150 Single-Tone FFT with fIN = 30.3 MHz
0
–120 0
06547-052
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 7060
150MSPS
70MHz @ –1dBFS
SNR = 71.5dBc (72. 5dBFS)
ENOB = 11.7 BITS
SF DR = 84dBc
SECOND HARMONI C
THI RD HARM O NIC
Figure 18. AD9640-150 Single-Tone FFT with fIN = 70 MHz
0
–120 0
06547-053
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 7060
150MSPS
140.3M Hz @ –1 dBFS
SNR = 70.9dBc (71. 9dBFS)
ENOB = 11.6 BITS
SF DR = 85.1dBc
SECO ND HARMONIC
THI RD HARM O NIC
Figure 19. AD9640-150 Single-Tone FFT with fIN = 140.3 MHz
0
–120 0
06547-054
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 7060
150MSPS
200.3M Hz @ –1dBF S
SNR = 70dBc (71dBF S )
ENO B = 11.5 BI TS
SFDR = 80dBc
SECO ND HARMONIC
THI RD HARM O NIC
Figure 20. AD9640-150 Single-Tone FFT with fIN = 200.3 MHz
0
–120 0
06547-085
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 7060
150MSPS
337MHz @ – 1dBFS
SNR = 68d Bc ( 69dBF S )
ENOB = 11 BITS
SF DR = 72.4dB
SECO ND HARMONIC
THIRD HARMONIC
Figure 21. AD9640-150 Single-Tone FFT with fIN = 337 MHz
AD9640
Rev. B | Page 21 of 52
0
–120 0
06547-086
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 7060
150MSPS
440MHz @ –1dBF S
SNR = 65dBc (66dBF S )
ENO B = 10.4 BI TS
SFDR = 70.0dB
SECOND HARMONI C
THIRD HARMONIC
Figure 22. AD9640-150 Single-Tone FFT with fIN = 440 MHz
0
–120 0
06547-057
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 60
125 MSPS
2.3M Hz @ –1dBF S
SNR = 72.3d Bc ( 73.3dBFS)
ENO B = 11.8 BI TS
SFDR = 88 .4dBc
SECO ND HARMONI C
THI RD HARM O NIC
Figure 23. AD9640-125 Single-Tone FFT with fIN = 2.3 MHz
0
–120 0
06547-058
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 60
125 MSP S
30.3M Hz @ –1dBF S
SNR = 72.1d Bc ( 73.1d BFS)
ENOB = 11.8 BIT S
SFDR = 89.1d Bc
THIRD HARMONIC
SECO ND HARMONIC
Figure 24. AD9640-125 Single-Tone FFT with fIN = 30.3 MHz
0
–120 0
06547-093
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 60
125MSPS
70MHz @ –1dBFS
SNR = 71.8dBc (72. 8dBFS)
ENOB = 11.7 BITS
SF DR = 85dBc
SECOND HARMONI C THIRD HARM ONIC
Figure 25. AD9640-125 Single-Tone FFT with fIN = 70 MHz
0
–120 0
06547-059
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 60
125 MS PS
140MHz @ –1dBF S
SNR = 71.4d Bc (72. 4dBF S )
ENO B = 11.7 BI TS
SF DR = 87.1d Bc
SECO ND HARMONIC
THI RD HARM O NIC
Figure 26. AD9640-125 Single-Tone FFT with fIN = 140 MHz
0
–120 0
06547-060
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
10 20 30 40 50 60
125 MS P S
200MHz @ –1dBF S
SNR = 70.8dBc (71. 8dBFS)
ENOB = 11.6 BITS
SF DR = 80.5dBc
SECOND HARMONI C
THIRD HARMONIC
Figure 27. AD9640-125 Single-Tone FFT with fIN = 200 MHz
AD9640
Rev. B | Page 22 of 52
120
100
80
60
40
20
0
–90 –80 –70 –60 –50 –40 –30 –20 –10
06547-061
INPUT AMPLITUDE (dBFS )
SNR/S F DR ( dBc AND dBFS)
0
SFDR ( dBFS )
SNR (dBFS)
SFDR ( dBc) SNR (dBc)
85dB REFERENCE LINE
Figure 28. AD9640-150 Single-Tone SNR/SFDR vs. Input Amplitude (AIN)
with fIN = 2.3 MHz
120
100
80
60
40
20
0
–90 –80 –70 –60 –50 –40 –30 –20 –10
06547-062
INPUT AMPLITUDE (dBFS )
SNR/S F DR ( dBc AND dBFS)
0
SFDR ( dBFS )
SNR (dBFS)
SFDR ( dBc) SNR ( dBc)
85dB REFERENCE LINE
Figure 29. AD9640-150 Single-Tone SFDR vs. Input Amplitude with
fIN = 98.12 MHz
95
90
85
80
75
70
65
600
06547-087
INPUT F REQUENCY (M Hz)
SNR/S FDR (d B c)
45050 100 150 200 250 300 350 400
SFDR = +25° C
SFDR = –40°C
SFDR = +85°C
SNR = –40° C
SNR = + 25°C SNR = + 85°C
Figure 30. AD9640-150 Single-Tone SNR/SFDR vs.
Input Frequency (fIN) and Temperature with 2 V p-p Full Scale
95
90
85
80
75
70
65
600
06547-088
INPUT F REQUENCY (M Hz)
SNR/S FDR (d B c)
45050 100 150 200 250 300 350 400
SFDR = +25°C
SFDR = –40 °C
SFDR = + 85°C
SNR = –40° C
SNR = +25°C SNR = +85°C
Figure 31. AD9640-150 Single-Tone SNR/SFDR vs.
Input Frequency (fIN) and Temperature with 1 V p-p Full Scale
0.8
–1.0
–40
06547-098
TE MPE RAT URE ( ° C)
GAIN/OFFSET ERROR (%F SR)
0.6
0.4
0.2
0
–0.2
–0.4
–0.6
–0.8
–200 20406080
GAIN
OFFSET
Figure 32. AD9640 Gain and Offset vs. Temperature
0
–100
–80
–60
–40
–20
–120
–90 –78 –66 –54 –42 –30 –18
06547-063
INPUT AMPLIT UDE (dBFS)
SNR/S F DR ( dBc AND dBFS)
–6
SFDR (dBF S )
IMD3 (dBF S)
SFDR ( dBc)
IMD3 (dBc)
Figure 33. AD9640-150 Two-Tone SFDR/IMD3 vs. Input Amplitude (AIN)
with fIN1 = 29.1 MHz, fIN2 = 32.1 MHz, fS = 150 MSPS
AD9640
Rev. B | Page 23 of 52
0
–100
–80
–60
–40
–20
–120
–90 –78 –66 –54 –42 –30 –18
06547-064
INPUT AMPLITUDE (dBFS )
SNR/S F DR ( dBc AND dBFS)
–6
SFDR (dBF S )
SFDR ( dBc)
IMD3 (dBc)
IMD3 ( d BF S)
Figure 34. AD9640-150 Two-Tone SFDR/IMD3 vs. Input Amplitude (AIN)
with fIN1 = 169.1 MHz, fIN2 = 172.1 MHz, fS = 150 MSPS
0 61.44
0
–120
06547-102
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
15.36 30.72 46.08
Figure 35. AD9640-125, Two 64 k WCDMA Carriers
with fIN = 170 MHz, fS = 122.88 MSPS
010 20 30 40 50 7060
0
–120
06547-065
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
150 MSP S
29.1M Hz @–7dBFS
32.1M Hz @–7dBFS
SF DR = 86.1dBc (93d BFS)
Figure 36. AD9640-150 Two-Tone FFT with fIN1 = 29.1 MHz and fIN2 = 32.1 MHz
010 20 30 40 50 7060
0
–120
06547-066
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
–20
–40
–60
–80
–100
150 MSP S
169.1M Hz @–7dBF S
172.1M Hz @–7dBF S
SF DR = 83.8dBc (90.8d BFS)
Figure 37. AD9640-150 Two-Tone FFT with fIN1 = 169.1 MHz and
fIN2 = 172.1 MHz
0
–120 0
06547-100
FREQUENCY (MHz)
AMPL ITUDE ( dBFS )
62.5
–20
–40
–60
–80
–100
15.625 31.25 46.875
NPR = 64. 7dBc
NOT CH @ 18.5MHz
NOT CH WIDTH = 3M Hz
Figure 38. AD9640 Noise Power Ratio (NPR)
0 150
100
70
06547-067
CLO CK FREQ UE NCY ( M sps)
SNR/S FDR (d B c)
95
90
85
80
75
25 50 75 100 125
SNR—SIDE A
SNR—SIDE B
SFDR— SIDE A
SFDR—SIDE B
Figure 39. AD9640-125 Single-Tone SNR/SFDR vs. Clock Frequency (fS)
with fIN = 2.3 MHz
AD9640
Rev. B | Page 24 of 52
10
0N – 4
OUT P UT CODE
NUMBER O F HI T S (1M)
8
6
4
2
N – 3 N – 2 N – 1 N N + 1 N + 2 N + 3 N + 4
1.3 LSB rms
06547-079
Figure 40. AD9640 Grounded Input Histogram
0 16,384
2.0
–2.0
–1.5
–1.0
–0.5
06547-068
OUT P UT CODE
INL ERROR ( LSB)
8192
1.5
1.0
0.5
0
2048 4096 6144 10,240 12,288 14,336
Figure 41. AD9640 INL with fIN = 10.3 MHz
0 16,384
0.5
–0.5
–0.4.
–0.3
–0.2
–0.1
06547-069
OUT P UT CODE
DNL ERROR ( LS B )
8192
0.4
0.3
0.2
0.1
0
2048 4096 6144 10,240 12,288 14,336
Figure 42. AD9640 DNL with fIN = 10.3 MHz
100
6020 80
DUTY CYCLE ( %)
SNR/S F DR (d Bc)
SFDR DCS ON
SFDR DCS OF F
SNR DCS OFF
SNR DCS O N
95
90
85
80
75
70
65
40 60
06547-090
Figure 43. AD9640 SNR/SFDR vs. Duty Cycle with fIN = 10.3 MHz
90
70
0.5 1.3
INPUT COMMON-MODE VOLTAGE (V)
SNR/S F DR (d Bc)
85
80
75
0.6 0.7 0.8 0.9 1.0 1.1 1.2
SFDR
SNR
06547-091
Figure 44. AD9640 SNR/SFDR vs. Input Common Mode Voltage (VCM)
with fIN = 30 MHz
AD9640
Rev. B | Page 25 of 52
THEORY OF OPERATION
The AD9640 dual ADC design can be used for diversity reception
of signals, where the ADCs are operating identically on the same
carrier but from two separate antennae. The ADCs can also be
operated with independent analog inputs. The user can sample
any fS/2 frequency segment from dc to 200 MHz using appropriate
low-pass or band-pass filtering at the ADC inputs with little loss
in ADC performance. Operation to 450 MHz analog input is
permitted but occurs at the expense of increased ADC distortion.
In nondiversity applications, the AD9640 can be used as a base-
band receiver, where one ADC is used for I input data and the
other is used for Q input data.
Synchronizaton capability is provided to allow synchronized
timing between multiple channels or multiple devices.
Programming and control of the AD9640 are accomplished
using a 3-bit SPI-compatible serial interface.
ADC ARCHITECTURE
The AD9640 architecture consists of a dual front-end sample-
and-hold amplifier (SHA), followed by a pipelined, switched
capacitor ADC. The quantized outputs from each stage are
combined into a final 14-bit result in the digital correction
logic. The pipelined architecture permits the first stage to
operate on a new input sample, and the remaining stages
operate on preceding samples. Sampling occurs on the rising
edge of the clock.
Each stage of the pipeline, excluding the last, consists of a low
resolution flash ADC connected to a switched capacitor digital-
to-analog converter (DAC) and an interstage residue amplifier
(MDAC). The residue amplifier magnifies the difference between
the reconstructed DAC output and the flash input for the next
stage in the pipeline. One bit of redundancy is used in each stage
to facilitate digital correction of flash errors. The last stage
simply consists of a flash ADC.
The input stage of each channel contains a differential SHA that
can be ac- or dc-coupled in differential or single-ended modes.
The output staging block aligns the data, carries out error correc-
tion, and passes the data to the output buffers. The output buffers
are powered from a separate supply, allowing adjustment of the
output voltage swing. During power-down, the output buffers go
into a high impedance state.
ANALOG INPUT CONSIDERATIONS
The analog input to the AD9640 is a differential switched
capacitor SHA that has been designed for optimum performance
while processing a differential input signal.
The clock signal alternatively switches the SHA between sample
mode and hold mode (see Figure 45). When the SHA is switched
into sample mode, the signal source must be capable of charging
the sample capacitors and settling within ½ of a clock cycle.
A small resistor in series with each input can help reduce the
peak transient current required from the output stage of the
driving source. A shunt capacitor can be placed across the
inputs to provide dynamic charging currents. This passive
network creates a low-pass filter at the ADC input; therefore,
the precise values are dependent on the application.
In intermediate frequency (IF) undersampling applications,
any shunt capacitors should be reduced. In combination with
the driving source impedance, they limit the input bandwidth.
See the AN-742 Application Note, Frequency Domain Response
of Switched-Capacitor ADCs; the AN-827 Application Note, A
Resonant Approach to Interfacing Amplifiers to Switched-Capacitor
ADCs; and the Analog Dialogue article, “Transformer-Coupled
Front-End for Wideband A/D Converters” for more information
on this subject.
VIN+
VIN–
CPIN, PAR
CPIN, PAR
CS
CS
CH
CH
H
S
S
S
S
06547-024
Figure 45. Switched-Capacitor SHA Input
For best dynamic performance, the source impedances driving
VIN+ and VIN− should be matched.
An internal differential reference buffer creates positive and
negative reference voltages that define the input span of the ADC
core. The span of the ADC core is set by the buffer to 2 × VREF.
Input Common Mode
The analog inputs of the AD9640 are not internally dc biased.
In ac-coupled applications, the user must provide this bias
externally. Setting the device so that VCM = 0.55 × AVDD
is recommended for optimum performance, but the device
functions over a wider range with reasonable performance
(see Figure 44). An on-board common-mode voltage reference
is included in the design and is available from the CML pin.
Optimum performance is achieved when the common-mode
voltage of the analog input is set by the CML pin voltage
(typically 0.55 × AVDD). The CML pin must be decoupled to
ground by a 0.1 µF capacitor, as described in the Applications
Information section.
Differential Input Configurations
Optimum performance is achieved while driving the AD9640
in a differential input configuration. For baseband applications,
the AD8138 differential driver provides excellent performance
and a flexible interface to the ADC.
AD9640
Rev. B | Page 26 of 52
The output common-mode voltage of the AD8138 is easily set
with the CML pin of the AD9640 (see Figure 46), and the driver
can be configured in a Sallen-Key filter topology to provide
band limiting of the input signal.
AVDD
1V p-p 49.9Ω
523Ω
0.1µF
R
R
C
499Ω
499Ω
499Ω
AD8138
06547-025
AD9640
VIN+
VIN– CML
Figure 46. Differential Input Configuration Using the AD8138
For baseband applications where SNR is a key parameter,
differential transformer coupling is the recommended input
configuration. An example is shown in Figure 47. To bias the
analog input, the CML voltage can be connected to the center
tap of the transformer’s secondary winding.
2V p -p 49.9Ω
0.1µF
R
R
C
06547-026
AD9640
VIN+
VIN– CML
Figure 47. Differential Transformer-Coupled Configuration
The signal characteristics must be considered when selecting
a transformer. Most RF transformers saturate at frequencies
below a few MHz, and excessive signal power can also cause
core saturation, which leads to distortion.
At input frequencies in the second Nyquist zone and above, the
noise performance of most amplifiers is not adequate to achieve
the true SNR performance of the AD9640. For applications where
SNR is a key parameter, differential double balun coupling is the
recommended input configuration (see Figure 49 for an example).
An alternative to using a transformer coupled input at frequencies
in the second Nyquist zone is to use the AD8352 differential
driver. An example is shown in Figure 50. See the AD8352 data
sheet for more information.
In any configuration, the value of Shunt Capacitor C is dependent
on the input frequency and source impedance and may need to
be reduced or removed. Table 13 displays recommended values to
set the RC network. However, these values are dependent on the
input signal and should be used only as a starting guide.
Table 13. Example RC Network
Frequency Range (MHz)
R Series
(Ω Each) C Differential (pF)
0 to 70 33 15
70 to 200 33 5
200 to 300 15 5
>300 15 Open
Single-Ended Input Configuration
A single-ended input can provide adequate performance in cost
sensitive applications. In this configuration, SFDR and distortion
performance degrade due to the large input common-mode swing.
If the source impedances on each input are matched, there should
be little effect on SNR performance. Figure 48 details a typical
single-ended input configuration.
1V p-p
R
R
C
49.9Ω0.1µF
10µF
10µF 0.1µF
AVDD
1kΩ
1kΩ
1kΩ
1kΩ
AD9640
A
V
DD
06547-071
VIN+
VIN–
Figure 48. Single-Ended Input Configuration
AD9640
R
0.1µF
0.1µF
2V p - p VIN+
VIN– CML
C
R
0.1µF
S0.1µF
06547-028
25Ω
25Ω
SPAP
Figure 49. Differential Double Balun Input Configuration
AD9640
AD8352
0Ω
R
0Ω
C
D
R
D
R
G
0.1µF
0.1µF
0.1µF
VIN+
VIN– CML
C
0.1µF
16
1
2
3
4
5
11
R
0.1µF
0.1µF
10
14
0.1µF
8, 13
V
CC
200Ω
200Ω
06547-070
ANALO G I NPUT
ANALO G I NPUT
Figure 50. Differential Input Configuration Using the AD8352
AD9640
Rev. B | Page 27 of 52
VOLTAGE REFERENCE
A stable and accurate voltage reference is built into the AD9640.
The input range can be adjusted by varying the reference voltage
applied to the AD9640, using either the internal reference or an
externally applied reference voltage. The input span of the ADC
tracks reference voltage changes linearly. The various reference
modes are summarized in the next few sections. The Reference
Decoupling section describes the best practices PCB layout of
the reference.
Internal Reference Connection
A comparator within the AD9640 detects the potential at the
SENSE pin and configures the reference into four possible
modes, which are summarized in Table 14. If SENSE is grounded,
the reference amplifier switch is connected to the internal
resistor divider (see Figure 51), setting VREF to 1 V. Connecting
the SENSE pin to VREF switches the reference amplifier output
to the SENSE pin, completing the loop and providing a 0.5 V
reference output. If a resistor divider is connected external to
the chip, as shown in Figure 52, the switch again sets to the
SENSE pin. This puts the reference amplifier in a noninverting
mode with the VREF output defined as
⎟
⎠
⎞
⎜
⎝
⎛+×= R1
R2
VREF 15.0
The input range of the ADC always equals twice the voltage at
the reference pin for either an internal or an external reference.
VREF
SENSE
0.5V
AD9640
SELECT
LOGIC
0.1µF1.0µF
06547-030
VIN–A/VIN–B
VIN+A/VIN+B
ADC
CORE
Figure 51. Internal Reference Configuration
0.5V
AD9640
SELECT
LOGIC
06547-031
VIN–A/VIN–B
VIN+A/VIN+B
ADC
CORE
VREF
SENSE
0.1µF1.0µF R2
R1
Figure 52. Programmable Reference Configuration
If the internal reference of the AD9640 is used to drive multiple
converters to improve gain matching, the loading of the reference
by the other converters must be considered. Figure 53 shows
how the internal reference voltage is affected by loading.
0
–1.25 02
LO AD CURRENT (mA)
REFE RE NCE VOL TAGE E RRO R (%)
.0
–0.25
–0.50
–0.75
–1.00
0.5 1.0 1.5
VREF = 0.5V
VREF = 1V
06547-080
Figure 53. VREF Accuracy vs. Load
External Reference Operation
The use of an external reference may be necessary to enhance
the gain accuracy of the ADC or improve thermal drift charac-
teristics. Figure 54 shows the typical drift characteristics of the
internal reference in 1 V mode.
Table 14. Reference Configuration Summary
Selected Mode SENSE Voltage Resulting VREF (V) Resulting Differential Span (V p-p)
External Reference AVDD N/A 2 × External Reference
Internal Fixed Reference VREF 0.5 1.0
Programmable Reference 0.2 V to VREF ⎟
⎠
⎞
⎜
⎝
⎛+× R1
R2
15.0 (see Figure 52) 2 × VREF
Internal Fixed Reference AGND to 0.2 V 1.0 2.0
AD9640
Rev. B | Page 28 of 52
2.5
–2.5
–40
06547-099
TE MPE RAT URE ( ° C)
REFE RE NCE VOL TAGE E RRO R (mV)
2.0
1.5
1.0
0
–0.5
–1.0
–1.5
–2.0
–200 20406080
Figure 54. Typical VREF Drift
When the SENSE pin is tied to AVDD, the internal reference is
disabled, allowing the use of an external reference. An internal
reference buffer loads the external reference with an equivalent
6 kΩ load (see Figure 15). The internal buffer generates the
positive and negative full-scale references for the ADC core.
Therefore, the external reference must be limited to a maximum
of 1 V.
CLOCK INPUT CONSIDERATIONS
For optimum performance, the AD9640 sample clock inputs
CLK+, and CLK− should be clocked with a differential signal.
The signal is typically ac-coupled into the CLK+ and CLK− pins
via a transformer or capacitors. These pins are biased internally
(see Figure 55) and require no external bias.
0
6547-034
1.2V
A
V
DD
2pF 2pF
CLK–CLK+
Figure 55. Equivalent Clock Input Circuit
Clock Input Options
The AD9640 has a very flexible clock input structure. Clock input
can be a CMOS, LVDS, LVPECL, or sine wave signal. Regardless of
the type of signal being used, the jitter of the clock source is of the
most concern, as described in the Jitter Considerations section.
Figure 56 and Figure 57 show two preferred methods for clocking
the AD9640 (at clock rates to 625 MHz). A low jitter clock source
is converted from a single-ended signal to a differential signal
using either an RF balun or an RF transformer. The RF balun
configuration is recommended for clock frequencies between
125 MHz and 625 MHz, and the RF transformer is recommended
for clock frequencies from 10 MHz to 200MHz. The back-to-back
Schottky diodes across the transformer/balun secondary limit
clock excursions into the AD9640 to approximately 0.8 V p-p
differential.
This helps prevent the large voltage swings of the clock from
feeding through to other portions of the AD9640, while preserving
the fast rise and fall times of the signal that are critical to a low
jitter performance.
0.1µF
0.1µF
0.1µF0.1µF
SCHOTTKY
DIODES:
HSMS2822
CLOC
K
INPUT 50Ω100Ω
CLK–
CLK+
ADC
AD9640
MINI-CIRCUITS
ADT1–1WT , 1:1Z
XFMR
06547-035
Figure 56. Transformer Coupled Differential Clock (Up to 200 MHz)
0.1µF
0.1µF1nF
CLOCK
INPUT
1nF
50Ω
CLK–
CLK+
ADC
AD9640
0
6547-101
SCHOTTKY
DIODES:
HSMS2822
Figure 57. Balun Coupled Differential Clock (Up to 625 MHz)
If a low jitter clock source is not available, another option is to
ac couple a differential PECL signal to the sample clock input
pins, as shown in Figure 58. The AD9510/AD9511/AD9512/
AD9513/AD9514/AD9515/AD9516 clock drivers offer excellent
jitter performance.
100Ω
0.1µF
0.1µF
0.1µF
0.1µF
240Ω240Ω
PECL DRIVER
50kΩ50kΩ
CLK–
CLK+
ADC
AD9640
CLOCK
INPUT
CLOCK
INPUT
06547-036
AD951x
Figure 58. Differential PECL Sample Clock (Up to 625 MHz)
A third option is to ac-couple a differential LVDS signal to the
sample clock input pins, as shown in Figure 59. The AD9510/
AD9511/AD9512/AD9513/AD9514/AD9515/AD9516 clock
drivers offer excellent jitter performance.
100Ω
0.1µF
0.1µF
0.1µF
0.1µF
50kΩ50kΩ
CLK–
CLK+
ADC
AD9640
CLOCK
INPUT
CLOCK
INPUT
06547-037
AD951x
LV DS DRIVE R
Figure 59. Differential LVDS Sample Clock (Up to 625 MHz)
In some applications, it may be acceptable to drive the sample
clock inputs with a single-ended CMOS signal. In such applica-
tions, CLK+ should be directly driven from a CMOS gate, and
the CLK− pin should be bypassed to ground with a 0.1 F
capacitor in parallel with a 39 k resistor (see Figure 60).
AD9640
Rev. B | Page 29 of 52
CLK+ can be directly driven from a CMOS gate. Although the
CLK+ input circuit supply is AVDD (1.8 V), this input is designed
to withstand input voltages up to 3.6 V, making the selection of
the drive logic voltage very flexible.
OPTIONAL
100Ω0.1µF
0.1µF
0.1µF
39kΩ
50Ω
1
1
50Ω RESISTOR IS OPTIONAL
CLK–
CLK+
ADC
AD9640
V
CC
1kΩ
1kΩ
CLOCK
INPUT
06547-038
AD951x
CMOS DRIVER
Figure 60. Single-Ended 1.8 V CMOS Sample Clock (Up to 150 MSPS)
150Ω RESI S TOR IS OPT IONAL
OPTIONAL
100Ω0.1µF
0.1µF
0.1µF
VCC
50Ω1
CLK–
CLK+
ADC
AD9640
1kΩ
1kΩ
CLOCK
INPUT
06547-039
AD951x
CMOS DRIVER
Figure 61. Single-Ended 3.3 V CMOS Sample Clock (Up to 150 MSPS)
Input Clock Divider
The AD9640 contains an input clock divider with the ability to
divide the input clock by integer values between 1 and 8. If a
divide ratio other than 1 is selected, the duty cycle stabilizer is
automatically enabled.
The AD9640 clock divider can be synchronized using the external
SYNC input. Bit 1 and Bit 2 of Register 0x100 allow the clock
divider to be resynchronized on every SYNC signal or only on
the first SYNC signal after the register is written. A valid SYNC
causes the clock divider to reset to its initial state. This synchro-
nization feature allows multiple parts to have their clock dividers
aligned to guarantee simultaneous input sampling.
Clock Duty Cycle
Typical high speed ADCs use both clock edges to generate
a variety of internal timing signals and, as a result, may be
sensitive to clock duty cycle. Commonly, a ±5% tolerance is
required on the clock duty cycle to maintain dynamic
performance characteristics.
The AD9640 contains a duty cycle stabilizer (DCS) that retimes
the nonsampling (falling) edge, providing an internal clock
signal with a nominal 50% duty cycle. This allows the user to
provide a wide range of clock input duty cycles without affecting
the performance of the AD9640. Noise and distortion performance
are nearly flat for a wide range of duty cycles with the DCS on,
as shown in Figure 43.
Jitter in the rising edge of the input is still of paramount concern
and is not easily reduced by the internal stabilization circuit.
The duty cycle control loop does not function for clock rates
less than 20 MHz nominally. The loop has a time constant
associated with it that needs to be considered where the clock
rate can change dynamically. This requires a wait time of 1.5 µs
to 5 µs after a dynamic clock frequency increase or decrease before
the DCS loop is relocked to the input signal. During the time
period the loop is not locked, the DCS loop is bypassed, and
internal device timing is dependent on the duty cycle of the input
clock signal. In such applications, it may be appropriate to disable
the duty cycle stabilizer. In all other applications, enabling the DCS
circuit is recommended to maximize ac performance.
Jitter Considerations
High speed, high resolution ADCs are sensitive to the quality
of the clock input. The degradation in SNR from the low
frequency SNR (SNRLF) at a given input frequency (fINPUT) due
to jitter (tJRMS) can be calculated by
SNRHF = −10 log[(2π × fINPUT × tJRMS)2 + 10 ]
)10/( LF
SNR−
In the equation, the rms aperture jitter represents the clock input
jitter specification. IF undersampling applications are particularly
sensitive to jitter, as illustrated in Figure 62.
75
70
65
60
55
50
45
40 1 10 100 1000
SNR (d Bc)
INPUT FREQUENCY (MHz)
06547-041
3.00ps
0.05ps
MEASURED
PERFORMANCE 0.20ps
0.5ps
1.0ps
1.50ps
2.00ps
2.50ps
Figure 62. SNR vs. Input Frequency and Jitter
The clock input should be treated as an analog signal in cases
where aperture jitter may affect the dynamic range of the AD9640.
Power supplies for clock drivers should be separated from the
ADC output driver supplies to avoid modulating the clock
signal with digital noise. Low jitter, crystal-controlled oscillators
make the best clock sources. If the clock is generated from
another type of source (by gating, dividing, or other methods),
it should be retimed by the original clock at the last step.
See the AN-501 Application Note and AN-756 Application
Note for more information about jitter performance as it
relates to ADCs.
AD9640
Rev. B | Page 30 of 52
POWER DISSIPATION AND STANDBY MODE
As shown in Figure 63, the power dissipated by the AD9640
is proportional to its sample rate. In CMOS output mode,
the digital power dissipation is determined primarily by the
strength of the digital drivers and the load on each output bit.
The maximum DRVDD current (IDRVDD) can be calculated as
IDRVDD = VDRVDD × CLOAD × fCLK × N
where N is the number of output bits (30 in the case of the AD9640
with the FD bits disabled). This maximum current occurs when
every output bit switches on every clock cycle, that is, a full-
scale square wave at the Nyquist frequency of fCLK/2. In practice,
the DRVDD current is established by the average number of
output bits switching, which is determined by the sample rate
and the characteristics of the analog input signal.
Reducing the capacitive load presented to the output drivers can
minimize digital power consumption. The data in Figure 63 was
taken with the same operating conditions as the Typical
Performance Characteristics, with a 5 pF load on each output
driver.
0 150125
1.25
0.75
1.0
0
06547-076
ENCODE FREQ UE NCY ( MHz)
TOTAL POWER (W)
SUPPLY CURRENT ( A)
0.5
0.25
0.5
0.4
0.3
0.2
0.1
0
25 50 75 100
I
AVDD
TOTAL POWER
I
DRVDD
I
DVDD
Figure 63. AD9640-150 Power and Current vs. Clock Frequency
0 125
1.25
0.75
1.0
0
06547-075
ENCODE FREQ UE NCY ( MHz)
TOTAL POWER (W)
SUPPLY CURRENT ( A)
0.5
0.25
0.5
0.4
0.3
0.2
0.1
0
25 50 75 100
I
AVDD
TOTAL POWER
I
DVDD
I
DRVDD
Figure 64. AD9640-125 Power and Current vs. Clock Frequency
0
1
0
ENCODE FREQ UE NCY ( MHz)
TOTAL POWER (W)
0.75
0.25
0.5
25 50 75 100
06547-074
SUPPLY CURRENT (A)
0.4
0.3
0.2
0.1
0
I
AVDD
TOTAL POWER
I
DRVDD
I
DVDD
Figure 65. AD9640-105 Power and Current vs. Clock Frequency
08
0.75
0
06547-073
ENCODE FREQ UE NCY (MHz)
TOTAL POWER (W)
SUPPLY CURRENT ( A)
0
0.5
0.25
0.3
0.2
0.1
0
20 40 60
IAVDD
TOTAL POWER
IDRVDD
IDVDD
Figure 66. AD9640-80 Power and Current vs. Clock Frequency
By asserting PDWN (either through the SPI port or by asserting
the PDWN pin high), the AD9640 is placed in power-down
mode. In this state, the ADC typically dissipates 2.5 mW.
During power-down, the output drivers are placed in a high
impedance state. Asserting the PDWN pin low returns the
AD9640 to its normal operational mode. Note that PDWN is
referenced to the digital supplies (DRVDD) and should not
exceed that supply voltage.
Low power dissipation in power-down mode is achieved by
shutting down the reference, reference buffer, biasing networks,
and clock. Internal capacitors are discharged when entering power-
down mode and then must be recharged when returning to normal
operation. As a result, wake-up time is related to the time spent
in power-down mode, and shorter power-down cycles result in
proportionally shorter wake-up times.
When using the SPI port interface, the user can place the ADC
in power-down mode or standby mode. Standby mode allows
the user to keep the internal reference circuitry powered when
faster wake-up times are required. See the Memory Map Register
Description section for more details.
AD9640
Rev. B | Page 31 of 52
DIGITAL OUTPUTS
The AD9640 output drivers can be configured to interface with
1.8 V to 3.3 V CMOS logic families by matching DRVDD to the
digital supply of the interfaced logic. The AD9640 can also be
configured for LVDS outputs using a DRVDD supply voltage
of 1.8 V.
In CMOS output mode, the output drivers are sized to provide
sufficient output current to drive a wide variety of logic families.
However, large drive currents tend to cause current glitches on
the supplies that may affect converter performance.
Applications requiring the ADC to drive large capacitive loads
or large fan-outs may require external buffers or latches.
The output data format can be selected for either offset binary
or twos complement by setting the SCLK/DFS pin when operating
in the external pin mode (see Table 15).
As detailed in the AN-877 Application Note, Interfacing to High
Speed ADCs via SPI, the data format can be selected for offset
binary, twos complement, or gray code when using the SPI control.
Table 15. SCLK/DFS Mode Selection (External Pin Mode)
Voltage at Pin SCLK/DFS SDIO/DCS
AGND Offset binary (default) DCS disabled
AVDD Twos complement DCS enabled (default)
Digital Output Enable Function (OEB)
The AD9640 has a flexible three-state ability for the digital output
pins. The three-state mode is enabled using the SMI SDO/OEB
pin or through the SPI interface. If the SMI SDO/OEB pin is low,
the output data drivers are enabled. If the SMI SDO/OEB pin is
high, the output data drivers are placed in a high impedance state.
This OEB function is not intended for rapid access to the data
bus. Note that OEB is referenced to the digital supplies (DRVDD)
and should not exceed that supply voltage.
When using the SPI interface, the data and fast detect outputs
of each channel can be independently three-stated by using the
output enable bar bit in Register 0x14.
TIMING
The AD9640 provides latched data with a pipeline delay of
twelve clock cycles. Data outputs are available one propagation
delay (tPD) after the rising edge of the clock signal.
The length of the output data lines and loads placed on them
should be minimized to reduce transients within the AD9640.
These transients can degrade converter dynamic performance.
The lowest typical conversion rate of the AD9640 is 10 MSPS.
At clock rates below 10 MSPS, dynamic performance can degrade.
Data Clock Output (DCO)
The AD9640 provides two data clock output (DCO) signals
intended for capturing the data in an external register. The data
outputs are valid on the rising edge of DCO, unless the DCO clock
polarity has been changed via the SPI. See Figure 2 and Figure 3
for a graphical timing description.
Table 16. Output Data Format
Input (V) Condition (V) Offset Binary Output Mode Twos Complement Mode OVR
VIN+ − VIN− < −VREF − 0.5 LSB 00 0000 0000 0000 10 0000 0000 0000 1
VIN+ − VIN− = −VREF 00 0000 0000 0000 10 0000 0000 0000 0
VIN+ − VIN− = 0 10 0000 0000 0000 00 0000 0000 0000 0
VIN+ − VIN− = +VREF − 1.0 LSB 11 1111 1111 1111 01 1111 1111 1111 0
VIN+ − VIN− > +VREF − 0.5 LSB 11 1111 1111 1111 01 1111 1111 1111 1
AD9640
Rev. B | Page 32 of 52
ADC OVERRANGE AND GAIN CONTROL
In receiver applications, it is desirable to have a mechanism to
reliably determine when the converter is about to be clipped.
The standard overflow indicator provides after-the-fact infor-
mation on the state of the analog input that is of limited usefulness.
Therefore, it is helpful to have a programmable threshold below
full scale that allows time to reduce the gain before the clip
actually occurs. In addition, because input signals can have
significant slew rates, latency of this function is of major concern.
Highly pipelined converters can have significant latency. A good
compromise is to use the output bits from the first stage of the
ADC for this function. Latency for these output bits is very low,
and overall resolution is not highly significant. Peak input signals
are typically between full scale and 6 dB to 10 dB below full
scale. A 3-bit or 4-bit output provides adequate range and
resolution for this function.
Using the SPI port, the user can provide a threshold above which
an overrange output is active. As long as the signal is below that
threshold, the output should remain low. The fast detect outputs
can also be programmed via the SPI port so that one of the pins
functions as a traditional overrange pin for customers who
currently use this feature. In this mode, all 14 bits of the converter
are examined in the traditional manner, and the output is high for
the condition normally defined as overflow. In either mode, the
magnitude of the data is considered in the calculation of the
condition (but the sign of the data is not considered). The threshold
detection responds identically to positive and negative signals
outside the desired range (magnitude).
FAST DETECT OVERVIEW
The AD9640 contains circuitry to facilitate fast overrange detec-
tion, allowing very flexible external gain control implementations.
Each ADC has four fast detect (FD) output pins that are used
to output information about the current state of the ADC input
level. The function of these pins is programmable via the fast detect
mode select bits and the fast detect enable bit in Register 0x104,
allowing range information to be output from several points in
the internal datapath. These output pins can also be set up to
indicate the presence of overrange or underrange conditions,
according to programmable threshold levels. Table 17 shows the
six configurations available for the fast detect pins.
Table 17. Fast Detect Mode Select Bits Settings
Fast Detect
Mode Select Bits
(Register 0x104[3:1])
Information Presented on
Fast Detect (FD) Pins of Each ADC1, 2
FD3 FD2 FD1 FD0
000 ADC fast magnitude
(see Table 18)
001 ADC fast magnitude
(see Table 19)
OR
010 ADC fast magnitude
(see Table 20)
OR F_LT
011 ADC fast magnitude
(see Table 20)
C_UT F_LT
100 OR C_UT F_UT F_LT
101 OR F_UT IG DG
1 The fast detect pins are FD0A/FD0B to FD3A/FD3B for the CMOS mode
configuration and FD0+/FD0− to FD3+/FD3− for the LVDS mode configuration.
2 See the ADC Overrange (OR) and Gain Switching sections for more
information about OR, C_UT, F_UT, F_LT, IG, and DG.
ADC FAST MAGNITUDE
When the fast detect output pins are configured to output the ADC
fast magnitude (that is, when the fast detect mode select bits are
set to 0b000), the information presented is the ADC level from
an early converter stage with a latency of only two clock cycles
(when in CMOS output mode). Using the fast detect output pins
in this configuration provides the earliest possible level indication
information. Because this information is provided early in the
datapath, there is significant uncertainty in the level indicated.
The nominal levels, along with the uncertainty indicated by the
ADC fast magnitude, are shown in Table 18.
Table 18. ADC Fast Magnitude Nominal Levels with Fast Detect
Mode Select Bits = 000
ADC Fast
Magnitude on
FD[3:0] Pins
Nominal Input
Magnitude
Below FS (dB)
Nominal Input
Magnitude
Uncertainty (dB)
0000 <−24 Minimum to −18.07
0001 −24 to −14.5 −30.14 to −12.04
0010 −14.5 to −10 −18.07 to −8.52
0011 −10 to −7 −12.04 to −6.02
0100 −7 to −5 −8.52 to −4.08
0101 −5 to −3.25 −6.02 to −2.5
0110 −3.25 to −1.8 −4.08 to −1.16
0111 −1.8 to −0.56 −2.5 to FS
1000 −0.56 to 0 −1.16 to 0
AD9640
Rev. B | Page 33 of 52
When the fast detect mode select bits are set to 0b001, 0b010, or
0b011, a subset of the fast detect output pins is available. In these
modes, the fast detect output pins have a latency of six clock cycles.
Table 19 shows the corresponding ADC input levels when the
fast detect mode select bits are set to 0b001 (that is, when ADC fast
magnitude is presented on the FD[3:1] pins).
Table 19. ADC Fast Magnitude Nominal Levels with
Fast Detect Mode Select Bits = 001
ADC Fast Magnitude
on FD[3:1] Pins
Nominal Input
Magnitude
Below FS (dB)
Nominal Input
Magnitude
Uncertainty (dB)
000 <−24 Minimum to −18.07
001 −24 to −14.5 −30.14 to −12.04
010 −14.5 to −10 −18.07 to −8.52
011 −10 to −7 −12.04 to −6.02
100 −7 to −5 −8.52 to −4.08
101 −5 to −3.25 −6.02 to −2.5
110 −3.25 to −1.8 −4.08 to −1.16
111 −1.8 to 0 −2.5 to 0
When the fast detect mode select bits are set to 0b010 or 0b011
(that is, when ADC fast magnitude is presented on the FD[3:2]
pins), the LSB is not provided. The input ranges for this mode
are shown in Table 20.
Table 20. ADC Fast Magnitude Nominal Levels with
Fast Detect Mode Select Bits = 010 or 011
ADC Fast
Magnitude on
FD[2:1] Pins
Nominal Input
Magnitude
Below FS (dB)
Nominal Input
Magnitude
Uncertainty (dB)
00 <−14.5 Minimum to −12.04
01 −14.5 to −7 −18.07 to −6.02
10 −7 to −3.25 −8.52 to −2.5
11 −3.25 to 0 −4.08 to 0
ADC OVERRANGE (OR)
The ADC overrange indicator is asserted when an overrange is
detected on the input of the ADC. The overrange condition is
determined at the output of the ADC pipeline and, therefore, is
subject to a latency of 12 ADC clock cycles. An overrange at the
input is indicated by this bit 12 clock cycles after it occurs.
GAIN SWITCHING
The AD9640 includes circuitry that is useful in applications either
where large dynamic ranges exist or where gain ranging converters
are employed. This circuitry allows digital thresholds to be set
such that an upper threshold and a lower threshold can be
programmed. Fast detect mode select bit = 010 through fast
detect mode select bit = 101 support various combinations of the
gain switching options.
One such use is to detect when an ADC is about to reach full
scale with a particular input condition. The result is to provide
an indicator that can be used to quickly insert an attenuator that
prevents ADC overdrive.
Coarse Upper Threshold (C_UT)
The coarse upper threshold indicator is asserted if the ADC fast
magnitude input level is greater than the level programmed in
the coarse upper threshold register (Address 0x105[2:0]). The
coarse upper threshold output is output two clock cycles after the
level is exceeded at the input and, therefore, provides a fast indi-
cation of the input signal level. The coarse upper threshold levels
are listed in Table 21. This indicator remains asserted for a
minimum of two ADC clock cycles or until the signal drops
below the threshold level.
Table 21. Coarse Upper Threshold Levels
Coarse Upper Threshold
Register 0x105[2:0]
C_UT Is Active When Signal
Magnitude Below FS
Is Greater Than (dB)
000 <−24
001 −24
010 −14.5
011 −10
100 −7
101 −5
110 −3.25
111 −1.8
Fine Upper Threshold (F_UT)
The fine upper threshold indicator is asserted if the input
magnitude exceeds the value programmed in the fine upper
threshold register located in Register 0x106 and Register 0x107.
The 13-bit threshold register is compared with the signal magni-
tude at the output of the ADC. This comparison is subject to the
ADC clock latency but is accurate in terms of the converter
resolution. The fine upper threshold magnitude is defined by
the following equation:
dBFS = 20 log(Threshold Magnitude/213)
Fine Lower Threshold (F_LT)
The fine lower threshold indicator is asserted if the input
magnitude is less than the value programmed in the fine lower
threshold register located at Register 0x108 and Register 0x109.
The fine lower threshold register is a 13-bit register that is
compared with the signal magnitude at the output of the ADC.
This comparison is subject to ADC clock latency but is accurate
in terms of the converter resolution. The fine lower threshold
magnitude is defined by the following equation:
dBFS = 20 log(Threshold Magnitude/213)
The operation of the fine upper threshold indicators and fine
lower threshold indicators is shown in Figure 67.
Increment Gain (IG) and Decrement Gain (DG)
The increment gain and decrement gain indicators are intended
to be used together to provide information to enable external
gain control. The decrement gain indicator works in conjunction
with the coarse upper threshold bits, asserting when the input
magnitude is greater than the 3-bit value in the coarse upper
threshold register (Address 0x105). The increment gain indicator,
AD9640
Rev. B | Page 34 of 52
dBFS = 20 log(Threshold Magnitude/213) similarly, corresponds to the fine lower threshold bits, except
that it is asserted only if the input magnitude is less than the
value programmed in the fine lower threshold register after the
dwell time elapses. The dwell time is set by the 16-bit dwell time
value located at Address 0x10A and Address 0x10B and is set in
units of ADC input clock cycles ranging from 1 to 65,535. The
fine lower threshold register is a 13-bit register that is compared
with the magnitude at the output of the ADC. This comparison
is subject to the ADC clock latency but allows a finer, more
accurate comparison. The fine upper threshold magnitude is
defined by the following equation:
The decrement gain output works from the ADC fast detect
output pins, providing a fast indication of potential overrange
conditions. The increment gain uses the comparison at the
output of the ADC, requiring the input magnitude to remain
below an accurate, programmable level for a predefined period
before signaling external circuitry to increase the gain.
The operation of the increment gain output and the decrement
gain output is shown in Figure 67.
0
6547-097
F_UT
F_LT
FINE UPP E R THRESHO LD
FI NE LO WER T HRESHOL D
Figure 67. Threshold Settings for F_UT and F_LT
AD9640
Rev. B | Page 35 of 52
SIGNAL MONITOR
The signal monitor block provides additional information
about the signal being digitized by the ADC. The signal monitor
computes the rms input magnitude, the peak magnitude,
and/or the number of samples by which the magnitude exceeds
a particular threshold. Together, these functions can be used to
gain insight into the signal characteristics and to estimate the
peak/average ratio or even the shape of the complementary cumu-
lative distribution function (CCDF) curve of the input signal. This
information can be used to drive an AGC loop to optimize the
range of the ADC in the presence of real-world signals.
The signal monitor result values can be obtained from the part by
reading back internal registers at Address 0x116 to Address 0x11B,
using the SPI port or the signal monitor SPORT output. The output
contents of the SPI-accessible signal monitor registers are set via
the two signal monitor mode bits of the signal monitor control
register. Both ADC channels must be configured for the same
signal monitor mode (Address 0x112). Separate SPI-accessible,
20-bit signal monitor result (SMR) registers are provided for each
ADC channel. Any combination of the signal monitor functions
can also be output to the user via the serial SPORT interface.
These outputs are enabled using the peak detector output enable
bit, the rms/ms magnitude output enable bit, and the threshold
crossing output enable bit in the signal monitor SPORT control
register.
For each signal monitor measurement, a programmable signal
monitor period register (SMPR) controls the duration of the
measurement. This period of time is programmed as the number
of input clock cycles in a 24-bit signal monitor period register
located at Address 0x113, Address 0x114, and Address 0x115.
This register can be programmed with a period from 128 samples
to 16.78 (224) million samples.
Because the dc offset of the ADC can be significantly larger
than the signal of interest (affecting the results from the signal
monitor), a dc correction circuit is included as part of the signal
monitor block to null the dc offset before measuring the power.
PEAK DETECTOR MODE
The magnitude of the input port signal is monitored over a
programmable time period (determined by the SMPR) to give
the peak value detected. This function is enabled by programming
a Logic 1 in the signal monitor mode bits of the signal monitor
control register or by setting the peak detector output enable bit
in the signal monitor SPORT control register. The 24-bit SMPR
must be programmed before activating this mode.
After enabling this mode, the value in the SMPR is loaded into
a monitor period timer, and the countdown is started. The magni-
tude of the input signal is compared with the value in the internal
peak level holding register (not accessible to the user), and the
greater of the two is updated as the current peak level. The initial
value of the peak level holding register is set to the current ADC
input signal magnitude. This comparison continues until the
monitor period timer reaches a count of 1.
When the monitor period timer reaches a count of 1, the 13-bit
peak level value is transferred to the signal monitor holding register
(not accessible to the user), which can be read through the SPI port
or output through the SPORT serial interface. The monitor period
timer is reloaded with the value in the SMPR, and the countdown is
restarted. In addition, the magnitude of the first input sample is
updated in the peak level holding register, and the comparison and
update procedure, as explained previously, continues.
Figure 68 is a block diagram of the peak detector logic. The SMR
register contains the absolute magnitude of the peak detected by
the peak detector logic.
SIG NAL MONITOR
HOLDING
REGISTER (SMR)
MAGNITUDE
STORAGE
REGISTER
COMPARE
A>B
TO
MEMORY
MAP/SPORT
FROM
MEMORY
MAP
FROM
INPUT
PORTS
LOAD
CLEAR
LOAD LOAD
IS COUNT = 1?
DOWN
COUNTER
SIGNAL M ONITOR
PERIOD REGISTER
06547-044
Figure 68. ADC Input Peak Detector Block Diagram
RMS/MS MAGNITUDE MODE
In this mode, the root-mean-square (rms) or mean-square (ms)
magnitude of the input port signal is integrated (by adding an
accumulator) over a programmable period of time (determined by
the SMPR) to give the rms or ms magnitude of the input signal.
This mode is set by programming Logic 0 in the signal monitor
mode bits of the signal monitor control register or by setting the
rms/ms magnitude output enable bit in the signal monitor SPORT
control register. The 24-bit SMPR, representing the period over
which integration is performed, must be programmed before acti-
vating this mode.
After enabling the rms/ms magnitude mode, the value in the SMPR
is loaded into a monitor period timer, and the countdown is started
immediately. Each input sample is converted to floating-point
format and squared. It is then converted to 11-bit, fixed-point
format and added to the contents of the 24-bit accumulator.
The integration continues until the monitor period timer reaches
a count of 1.
When the monitor period timer reaches a count of 1, the square
root of the value in the accumulator is taken and transferred,
after some formatting, to the signal monitor holding register, which
can be read through the SPI port or output through the SPORT
serial port. The monitor period timer is reloaded with the value
in the SMPR, and the countdown is restarted. In addition, the
first input sample signal power is updated in the accumulator,
and the accumulation continues with the subsequent input
samples.
AD9640
Rev. B | Page 36 of 52
Figure 69 illustrates the rms magnitude monitoring logic.
SIG NAL M O NI T O R
HOLDING
REGISTER (SMR)
ACCUMULATOR
TO
MEMORY
MAP/SPORT
FROM
MEMORY
MAP
FROM
INPUT
PORTS
LOAD
CLEAR LOAD
IS COUNT = 1?
DOWN
COUNTER
SIGNAL MONITO R
PERI OD REG IST E R
06547-092
Figure 69. ADC Input RMS Magnitude Monitoring Block Diagram
For rms magnitude mode, the value in the signal monitor result
(SMR) register is a 20-bit fixed-point number. The following
equation can be used to determine the rms magnitude in dBFS
from the MAG value in the register. Note that if the signal monitor
period (SMP) is a power of 2, the second term in the equation
becomes 0.
RMS Magnitude = 20 log
[]
⎥
⎦
⎤
⎢
⎣
⎡
−
⎟
⎠
⎞
⎜
⎝
⎛
)(log
20 2
2
log10
2SMPceil
SMPMAG
For ms magnitude mode, the value in the SMR is a 20-bit fixed-
point number. The following equation can be used to determine
the ms magnitude in dBFS from the MAG value in the register.
Note that if the SMP is a power of 2, the second term in the
equation becomes 0.
MS Magnitude = 10 log
[]
⎥
⎦
⎤
⎢
⎣
⎡
−
⎟
⎠
⎞
⎜
⎝
⎛
)(log
20 2
2
log10
2SMPceil
SMPMAG
THRESHOLD CROSSING MODE
In the threshold crossing mode of operation, the magnitude of
the input port signal is monitored over a programmable time
period (given by the SMPR) to count the number of times it
crosses a certain programmable threshold value. This mode is set
by programming Logic 1x (where x is a don’t care bit) in the
signal monitor mode bits of the signal monitor control register
or by setting the threshold crossing output enable bit in the
signal monitor SPORT control register. Before activating this
mode, the user needs to program the 24-bit SMPR and the
13-bit upper threshold register for each individual input port.
The same upper threshold register is used for both signal moni-
toring and gain control (see the ADC Overrange and Gain
Control section).
After entering this mode, the value in the SMPR is loaded into
a monitor period timer, and the countdown is started. The magni-
tude of the input signal is compared with the upper threshold
register (programmed previously) on each input clock cycle.
If the input signal has a magnitude greater than the upper
threshold register, the internal count register is incremented by 1.
The initial value of the internal count register is set to 0. This
comparison and incrementing of the internal count register
continues until the monitor period timer reaches a count of 1.
When the monitor period timer reaches a count of 1, the value
in the internal count register is transferred to the signal monitor
holding register, which can be read through the SPI port or output
through the SPORT serial port.
The monitor period timer is reloaded with the value in the SMPR
register, and the countdown is restarted. The internal count
register is also cleared to a value of 0. Figure 70 illustrates the
threshold crossing logic. The value in the SMR register is the
number of samples that have a magnitude greater than the
threshold register.
SIGNAL MO NIT OR
HOLDING
REGIS TER (SMR)
COMPARE
A>B
UPPER
THRESHOLD
REGISTER
COMPARE
A>B
TO
MEMORY
MAP/SPORT
FROM
MEMORY
MAP
FROM
MEMORY
MAP
FROM
INPUT
PORTS
LOAD
CLEAR LOAD
IS COUNT = 1?
DOWN
COUNTER
SIGNAL MONITOR
PERIO D RE GISTE R
B
A
06547-046
Figure 70. ADC Input Threshold Crossing Block Diagram
ADDITIONAL CONTROL BITS
For additional flexibility in the signal monitoring process, two
control bits are provided in the signal monitor control register.
They are the signal monitor enable bit and the complex power
calculation mode enable bit.
Signal Monitor Enable Bit
The signal monitor enable bit, Bit 0 of Register 0x112, enables
operation of the signal monitor block. If the signal monitor
function is not needed in a particular application, this bit should
be cleared (default) to conserve power.
Complex Power Calculation Mode Enable Bit
When this bit is set, the part assumes that Channel A is digitizing
the I data and Channel B is digitizing the Q data for a complex
input signal (or vice versa). In this mode, the power reported is
equal to the following:
22 QI +
This result is presented in the Signal Monitor DC Value Channel A
register if the signal monitor mode bits are set to 00. The Signal
Monitor DC Value Channel B register continues to compute the
Channel B value.
DC CORRECTION
Because the dc offset of the ADC may be significantly larger
than the signal being measured, a dc correction circuit is included
to null the dc offset before measuring the power. The dc correction
circuit can also be switched into the main signal path, but this
may not be appropriate if the ADC is digitizing a time-varying
signal with significant dc content, such as GSM.
AD9640
Rev. B | Page 37 of 52
DC Correction Bandwidth SIGNAL MONITOR SPORT OUTPUT
The dc correction circuit is a high-pass filter with a programmable
bandwidth (ranging between 0.15 Hz and 1.2 kHz at 125 MSPS).
The bandwidth is controlled by writing Bits[5:2] of the signal
monitor dc correction control register, located at Address 0x10C.
The SPORT is a serial interface with three output pins:
SMI SCLK (SPORT clock), SMI SDFS (SPORT frame sync), and
SMI SDO (SPORT data output). The SPORT is the master and
drives all three SPORT output pins on the chip.
The following equation can be used to compute the bandwidth
value for the dc correction circuit: SMI SCLK
The data output and frame sync are driven on the positive edge of
the SMI SCLK. The SMI SCLK has three possible baud rates: 1/2,
1/4, or 1/8 the ADC clock rate, based on the SPORT controls. The
SMI SCLK can also be gated off when not sending any data, based
on the SPORT SMI SCLK sleep bit. Using this bit to disable the SMI
SCLK when it is not needed can reduce any coupling errors back
into the signal path, if these prove to be a problem in the system.
Doing so, however, has the disadvantage of spreading the frequency
content of the clock. If desired, the SMI SCLK can be left running
to ease frequency planning.
π×
×= −−
2
2__ 14 CLK
kf
BWCorrDC
where:
k is the 4 bit value programmed in Register 0x10C, Bits[5:2]
(values between 0 and 13 are valid for k; programming 14 or
15 provides the same result as programming 13).
fCLK is the ADC sample rate in hertz (Hz).
DC Correction Readback
The current dc correction value can be read back in Register 0x10D
and Register 0x10E for Channel A and in Register 0x10F and
Register 0x110 for Channel B. The dc correction value is a 14-bit
value that can span the entire input range of the ADC.
SMI SDFS
The SMI SDFS is the serial data frame sync, and it defines the
start of a frame. One SPORT frame includes data from both
datapaths. The data from Datapath A is sent just after the frame
sync, followed by data from Datapath B.
DC Correction Freeze
Setting Bit 6 of Register 0x10C freezes the dc correction at its
current state and continues to use the last updated value as the
dc correction value. Clearing this bit restarts dc correction and
adds the currently calculated value to the data.
SMI SDO
The SMI SDO is the serial data output of the block. The data
is sent MSB first on the next positive edge after the SMI SDFS.
Each data output block includes one or more rms/ms magnitude,
peak level, and threshold crossing values from each datapath in
the stated order. If enabled, the data is sent, rms first, followed by
peak and threshold, as shown in Figure 71.
DC Correction Enable Bits
Setting Bit 0 of Register 0x10C enables dc correction for use in
the signal monitor calculations. The calculated dc correction
value can be added to the output data signal path by setting Bit 1
of Register 0x10C.
20 CYCL E S 16 CYCL ES16 CYCL ES 20 CYCLES 16 CYCLES 16 CY CLES
SMI SDFS
MSB MSB
RMS /M S CH A
PK CH A PK CH B
THR CH B
RMS /M S CH B
RMS/ M S CH A
LSB LSB
THR CH A
SMI SDO
S
MI SCLK
GAT E D, BASED ON CONT ROL
06547-094
Figure 71. Signal Monitor SPORT Output Timing (RMS/MS, Peak, and Threshold Enabled)
20 CYCLES 16 CYCLE S 20 CYCL ES 16 CY CLES
SMI S CL K
SMI SDFS
SMI SDO MSB MSBRMS /M S CH A RMS/ M S CH ALSB THR CH A RMS/MS CH B L SB THR CH B
GA T E D , BA S ED O N CONTROL
06547-095
Figure 72. Signal Monitor SPORT Output Timing (RMS/MS and Threshold Enabled)
AD9640
Rev. B | Page 38 of 52
BUILT-IN SELF-TEST (BIST) AND OUTPUT TEST
The AD9640 includes built-in test features to enable verification
of the integrity of each channel as well as to facilitate board level
debugging. A built-in self-test (BIST) feature is included that
verifies the integrity of the digital data path of the AD9640.
Various output test options are also provided to place predictable
values on the outputs of the AD9640.
BUILT-IN SELF-TEST (BIST)
The BIST is a thorough test of the digital portion of the selected
AD9640 signal path. When enabled, the test runs from an internal
PN source through the digital data path starting at the ADC
block output. The BIST sequence runs for 512 cycles and stops.
The BIST signature value for Channel A or Channel B is placed
in Register 0x024 and Register 0x025. If one channel is chosen,
its BIST signature is written to the two registers. If both channels
are chosen, the results from the A channel are placed in the
BIST signature register.
The outputs are not disconnected during this test, so the PN
sequence can be observed as it runs. The PN sequence can be
continued from its last value or started from the beginning,
based on the value programmed in Register 0x00E, Bit 2. The
BIST signature result varies based on the channel configuration.
OUTPUT TEST MODES
The output test options are shown in Table 25. When an output
test mode is enabled, the analog section of the ADC is discon-
nected from the digital backend blocks and the test pattern is run
through the output formatting block. Some of the test patterns are
subject to output formatting and some are not. The seed value for
the PN sequence tests can be forced if the PN reset bits are used
to hold the generator in reset mode by setting Bit 4 or Bit 5 of
Register 0x0D. These tests can be performed with or without
an analog signal (if present, the analog signal is ignored), but
they do require an encode clock. For more information, see the
AN-877 Application Note, Interfacing to High Speed ADCs via SPI.
AD9640
Rev. B | Page 39 of 52
CHANNEL/CHIP SYNCHRONIZATION
The AD9640 has a SYNC input that allows the user flexible
synchronization options for synchronizing the internal blocks.
The clock divider sync feature is useful to guarantee synchronized
sample clocks across multiple ADCs. The signal monitor block
can also be synchronized using the SYNC input allowing properties
of the input signal to be measured during a specific time period.
The input clock divider can be enabled to synchronize on a single
occurrence of the sync signal or on every occurrence. The signal
monitor block is synchronized on every SYNC input signal.
The SYNC input is internally synchronized to the sample clock;
however, to ensure there is no timing uncertainty between multiple
parts, the SYNC input signal should be externally synchronized to
the input clock signal, meeting the setup and hold times shown
in Table 8. The SYNC input should be driven using a single-
ended CMOS-type signal.
AD9640
Rev. B | Page 40 of 52
SERIAL PORT INTERFACE (SPI)
The AD9640 serial port interface (SPI) allows the user to
configure the converter for specific functions or operations
through a structured register space provided inside the ADC.
This gives the user added flexibility and customization
depending on the application. Addresses are accessed via the
serial port and can be written to or read from via the port.
Memory is organized into bytes that can be further divided into
fields, which are documented in the Memory Map section. For
detailed operational information, see the AN-877 Application
Note, Interfacing to High Speed ADCs via SPI.
CONFIGURATION USING THE SPI
There are three pins that define the SPI of this ADC. They are
the SCLK/DFS pin, the SDIO/DCS pin, and the CSB pin (see
Table 22). The SCLK/DFS (a serial clock) is used to synchronize
the read and write data presented from and to the ADC. The
SDIO/DCS (serial data input/output) is a dual-purpose pin that
allows data to be sent and read from the internal ADC memory
map registers. The CSB (chip select bar) is an active-low control
that enables or disables the read and write cycles.
Table 22. Serial Port Interface Pins
Pin Function
SCLK Serial Clock. The serial shift clock input. SCLK is used to
synchronize serial interface reads and writes.
SDIO Serial Data Input/Output. A dual-purpose pin. The typical
role for this pin is an input and output depending on the
instruction being sent and the relative position in the
timing frame.
CSB Chip Select Bar. An active-low control that gates the read
and write cycles.
The falling edge of the CSB, in conjunction with the rising edge
of the SCLK, determines the start of the framing. An example of
the serial timing and its definitions can be found in Figure 73
and Tabl e 8.
Other modes involving the CSB are available. The CSB can be
held low indefinitely, which permanently enables the device;
this is called streaming. The CSB may stall high between bytes
to allow for additional external timing. When CSB is tied high,
SPI functions are placed in high impedance mode. This mode
turns on any SPI pin secondary functions.
During an instruction phase, a 16-bit instruction is transmitted.
Data follows the instruction phase, and its length is determined
by the W0 and W1 bits. All data is composed of 8-bit words.
The first bit of the first byte in a multibyte serial data transfer frame
indicates whether a read command or a write command is
issued. This allows the serial data input/output (SDIO) pin to
change direction from an input to an output.
In addition to word length, the instruction phase determines if
the serial frame is a read or write operation, allowing the serial
port to be used to both program the chip as well as read the
contents of the on-chip memory. If the instruction is a readback
operation, performing a readback causes the serial data input/
output (SDIO) pin to change direction from an input to an output
at the appropriate point in the serial frame.
Data can be sent in MSB first mode or LSB first mode. MSB
first is the default on power-up and can be changed via the
configuration register. For more information about this and
other features, see the AN-877 Application Note, Interfacing to
High Speed ADCs via SPI.
HARDWARE INTERFACE
The pins described in Table 22 comprise the physical interface
between the user’s programming device and the serial port of
the AD9640. The SCLK pin and the CSB pin function as inputs
when using the SPI interface. The SDIO pin is bidirectional,
functioning as an input during write phases and as an output
during readback.
The SPI interface is flexible enough to be controlled by either
FPGAs or microcontrollers. One method for SPI configuration
is described in detail in the AN-812 Application Note,
Microcontroller-Based Serial Port Interface Boot Circuit.
The SPI port should not be active during periods when the full
dynamic performance of the converter is required. Because the
SCLK signal, the CSB signal, and the SDIO signal are typically
asynchronous to the ADC clock, noise from these signals can
degrade converter performance. If the on-board SPI bus is utilized
for other devices, it may be necessary to provide buffers between
this bus and the AD9640 to keep these signals from transitioning
at the converter inputs during critical sampling periods.
Some pins serve a dual function when the SPI interface is not
being used. When the pins are strapped to AVDD or ground
during device power-on, they are associated with a specific
function. The Digital Outputs section describes the strappable
functions supported on the AD9640.
AD9640
Rev. B | Page 41 of 52
CONFIGURATION WITHOUT THE SPI
In applications that do not interface to the SPI control registers,
the SDIO/DCS pin, the SCLK/DFS pin, the SMI SDO/OEB pin,
and the SMI SCLK/PDWN pin serve as standalone, CMOS-
compatible control pins. When the device is powered up, it is
assumed that the user intends to use the pins as static control
lines for the duty cycle stabilizer, output data format, output
enable, and power-down feature control. In this mode, the CSB
chip select should be connected to AVDD, which disables the
serial port interface.
Table 23. Mode Selection
Pin
External
Voltage Configuration
SDIO/DCS AVDD (default) Duty cycle stabilizer enabled.
AGND Duty cycle stabilizer disabled.
SCLK/DFS AVDD Twos complement enabled.
AGND (default) Offset binary enabled.
SMI SDO/OEB AVDD Outputs in high impedance.
AGND (default) Outputs enabled.
SMI SCLK/PDWN AVDD Chip in power-down or
standby.
AGND (default) Normal operation.
SPI ACCESSIBLE FEATURES
A brief description of general features accessible via the SPI
follows. These features are described in detail in the AN-877
Application Note, Interfacing to High Speed ADCs via SPI. The
AD9640 part-specific features are described in detail following
Table 25, the external memory map register table.
Table 24. Features Accessible Using the SPI
Feature Name Description
Modes Allows user to set either power-down mode or
standby mode.
Clock Allows user to access the DCS via the SPI.
Offset Allows user to digitally adjust the converter
offset.
Test I/O Allows user to set test modes to have known
data on output bits.
Output Mode Allows user to set up outputs.
Output Phase Allows user to set the output clock polarity.
Output Delay Allows user to vary the DCO delay.
VREF Allows user to set the reference voltage.
DON’ T CARE
DON’T CAREDON’T CARE
DON’T CARE
SDIO
SCLK
CSB
t
S
t
DH
t
CLK
t
DS
t
H
R/W W1 W0 A12 A11 A10 A9 A8 A7 D5 D4 D3 D2 D1 D0
06547-049
t
LOW
t
HIGH
Figure 73. Serial Port Interface Timing Diagram
AD9640
Rev. B | Page 42 of 52
MEMORY MAP
READING THE MEMORY MAP TABLE
Each row in the memory map table has eight bit locations. The
memory map is roughly divided into four sections: chip configura-
tion and ID register map (Address 0x00 to Address 0x02); ADC
setup, control, and test (Address 0x08 to Address 0x25); the
channel index and transfer register map (Address 0x05 to
Address 0xFF); and digital feature control (Address 0x100 to
Address 0x11B).
Starting from the right hand column, the memory map register
in Table 25 documents the default hex value for each hex address
shown. The column with the heading Bit 7 (MSB) is the start
of the default hex value given. For example, Address 0x18, VREF
select, has a hex default value of 0xC0. This means Bit 7 = 1,
Bit 6 = 1, and the remaining bits are 0s. This setting is the default
reference selection setting. The default value uses a 2.0 V peak-
to-peak reference. For more information on this function and
others, see the AN-877 Application Note, Interfacing to High Speed
ADCs via SPI. This document details the functions controlled by
Register 0x00 to Register 0xFF. The remaining registers, from
Register 0x100 to Register 0x11B, are documented in the Memory
Map Register Description section.
Open Locations
All address and bit locations that are not included in Table 25
are currently not supported for this device. Unused bits of a
valid address location should be written with 0s. Writing to these
locations is required only when part of an address location is
open (for example, Address 0x18). If the entire address location
is open (for example, Address 0x13), this address location should
not be written.
Default Values
Coming out of reset, critical registers are loaded with default
values. The default values for the registers are given in the
memory map register table, Table 25.
Logic Levels
An explanation of logic level terminology follows:
• “Bit is set” is synonymous with “Bit is set to Logic 1” or
“Writing Logic 1 for the bit.”
• “Clear a bit” is synonymous with “Bit is set to Logic 0” or
“Writing Logic 0 for the bit.”
Transfer Register Map
Address 0x08 to Address 0x18 are shadowed. Writes to these
addresses do not affect part operation until a transfer command
is issued by writing 0x01 to Address 0xFF, setting the transfer bit.
This allows these registers to be updated internally and simulta-
neously when the transfer bit is set. The internal update takes
place when the transfer bit is set, and the bit autoclears.
Channel-Specific Registers
Some channel setup functions, such as the signal monitor
thresholds, can be programmed differently for each channel.
In these cases, channel address locations are internally duplicated
for each channel. These registers are designated in the parameter
name column of Table 2 5 as local registers. These local registers
can be accessed by setting the appropriate Channel A or Channel B
bits in Register 0x05. If both bits are set, the subsequent write
affects the registers of both channels. In a read cycle, only
Channel A or Channel B should be set to read one of the two
registers. If both bits are set during an SPI read cycle, the part
returns the value for Channel A. Registers designated as global
in the parameter name column of Table 25 affect the entire part
or the channel features where independent settings are not
allowed between the channels. The settings in Register 0x05
do not affect the global registers.
AD9640
Rev. B | Page 43 of 52
EXTERNAL MEMORY MAP
Table 25. Memory Map Registers
Addr
(Hex)
Register
Name
Bit 7
(MSB) Bit 6 Bit 5 Bit 4 Bit 3 Bit 2 Bit 1
Bit 0
(LSB)
Default
Value
(Hex)
Default
Notes/
Comments
Chip Configuration Registers
0x00 SPI Port
Configuration
(Global)
0 LSB first Soft reset 1 1 Soft reset LSB first 0 0x18 The nibbles
are mirrored
so that
LSB-first mode
or MSB-first
mode registers
correctly,
regardless of
shift mode
0x01 Chip ID
(Global)
8-bit Chip ID[7:0]
(AD9640 = 0x11)
(default)
0x11
Read
only
Read only
0x02 Chip Grade
(Global)
Open Open Speed grade ID
00 = 150 MSPS
01 = 125 MSPS
10 = 105 MSPS
11 = 80 MSPS
Open Open Open Open Read
only
Speed grade
ID used to
differentiate
devices
Channel Index and Transfer Registers
0x05 Channel Index Open Open Open Open Open Open
Data
Channel B
(default)
Data
Channel A
(default)
0x03 Bits are set
to determine
which device
on the chip
receives the
next write
command;
applies to local
registers
0xFF Device Update Open Open Open Open Open Open Open Transfer 0x00
Synchronously
transfers data
from the
master shift
register to the
slave
ADC Functions
0x08 Power Modes Open Open External
power-
down pin
function
(global)
0 = pdwn
1 = stndby
Open Open Open Internal power-down
mode (local)
00 = normal operation
01 = full power-down
10 = standby
11 = normal operation
0x00 Determines
various generic
modes of chip
operation
0x09 Global Clock
(Global)
Open Open Open Open Open Open Open Duty cycle
stabilizer
(default)
0x01
0x0B Clock Divide
(Global)
Open Open Open Open Open Clock divide ratio
000 = divide by 1
001 = divide by 2
010 = divide by 3
011 = divide by 4
100 = divide by 5
101 = divide by 6
110 = divide by 7
111 = divide by 8
0x00 Clock divide
values other
than 000
automatically
cause the duty
cycle stabilizer
to become
active
0x0D Test Mode
(Local)
Open Open Reset PN
long gen
Reset
PNshort
gen
Open Output test mode
000 = off (default)
001 = midscale short
010 = positive FS
011 = negative FS
100 = alternating checker board
101 = PN long sequence
110 = PN short sequence
111 = one/zero word toggle
0x00 When set,
the test data
is placed on
the output
pins in place of
normal data
AD9640
Rev. B | Page 44 of 52
Addr
(Hex)
Register
Name
Bit 7
(MSB) Bit 6 Bit 5 Bit 4 Bit 3 Bit 2 Bit 1
Bit 0
(LSB)
Default
Value
(Hex)
Default
Notes/
Comments
0x0E BIST Enable
(Local)
Open Open Open Open Open
Reset BIST
sequence
Open BIST enable 0x00
0x10 Offset Adjust
(Local)
Open Open Offset adjust in LSBs from +31 to −32
(twos complement format)
0x00
0x14 Output Mode Drive
strength
0 V to 3.3 V
CMOS or
ANSI
LVDS:
1 V to 1.8 V
CMOS or
reduced:
LVDS
(global)
Output type
0 = CMOS
1 = LVDS
(global)
Open Output
enable bar
(local)
Open Output
invert
(local)
00 = offset binary
01 = twos complement
01 = gray code
11 = offset binary
(local)
0x00 Configures the
outputs and
the format of
the data
0x16 Clock Phase
Control
(Global)
Invert DCO
clock
Open Open Open Open Input clock divider phase adjust
000 = no delay
001 = 1 input clock cycle
010 = 2 input clock cycles
011 = 3 input clock cycles
100 = 4 input clock cycles
101 = 5 input clock cycles
110 = 6 input clock cycles
0x00 Allows
selection of
clock delays
into the input
clock divider
0x17 DCO Output
Delay (Global)
Open Open Open DCO clock delay
(delay = 2500 ps × register value/31)
00000 = 0 ps
00001 = 81 ps
00010 = 161 ps
…
11110 = 2419 ps
11111 = 2500 ps
0x00
0x18 VREF Select
(Global)
Reference voltage selection
00 = 1.25 V p-p
01 = 1.5 V p-p
10 = 1.75 V p-p
11 = 2.0 V p-p (default)
Open Open Open Open Open Open 0xC0
0x24 BIST Signature
LSB (Local)
BIST signature[7:0] 0x00 Read only
0x25 BIST Signature
MSB (Local)
BIST signature[15:8] 0x00 Read only
Digital Feature Control
0x100 Sync Control
(Global)
SM sync
enable
Open Open Open Open
Clock
divider next
sync only
Clock
divider
sync
enable
Master
sync
enable
0x00
0x104 Fast Detect
Control (Local)
Open Open Open Open Fast Detect Mode Select[2:0] Fast detect
enable
0x00
0x106 Fine Upper
Threshold
Register 0
(Local)
Fine Upper Threshold[7:0] 0x00
0x107 Fine Upper
Threshold
Register 1
(Local)
Open Open Open Fine Upper Threshold[12:8] 0x00
0x108 Fine Lower
Threshold
Register 0
(Local)
Fine Lower Threshold[7:0] 0x00
0x109 Fine Lower
Threshold
Register 1
(Local)
Open Open Open Fine Lower Threshold[12:8] 0x00
AD9640
Rev. B | Page 45 of 52
Addr
(Hex)
Register
Name
Bit 7
(MSB) Bit 6 Bit 5 Bit 4 Bit 3 Bit 2 Bit 1
Bit 0
(LSB)
Default
Value
(Hex)
Default
Notes/
Comments
0x10C Signal Monitor
DC Correction
Control
(Global)
Open DC
correction
freeze
DC Correction Bandwidth[3:0] DC
correction
for signal
path
enable
DC
correction
for SM
enable
0x00
0x10D Signal Monitor
DC Value
Channel A
Register 0
(Global)
DC Value Channel A[7:0] Read only
0x10E Signal Monitor
DC Value
Channel A
Register 1
(Global)
Open Open DC Value Channel A[13:8] Read only
0x10F Signal Monitor
DC Value
Channel B
Register 0
(Global)
DC Value Channel B[7:0] Read only
0x110 Signal Monitor
DC Value
Channel B
Register 1
(Global)
Open Open DC Value Channel B[13:8] Read only
0x111 Signal Monitor
SPORT Control
(Global)
Open RMS/MS
magnitude
output
enable
Peak
power
output
enable
Threshold
crossing
output
enable
SPORT SMI
CLK divide
00 = undefined
01 = divide by 2
10 = divide by 4
11 = divide by 8
SPORT
SMI SCLK
sleep
Signal
monitor
SPORT
output
enable
0x04
0x112 Signal Monitor
Control
(Global)
Complex
power
calculation
mode
enable
Open Open Open
MS
mode
0 =
rms
1 = ms
Signal monitor mode
00 = RMS/MS Magnitude
01 = peak power
1x = threshold count
Signal
monitor
enable
0x00
0x113 Signal Monitor
Period
Register 0
(Global)
Signal Monitor Period[7:0] 0x40 In ADC clock
cycles
0x114 Signal Monitor
Period
Register 1
(Global)
Signal Monitor Period[15:8] 0x00 In ADC clock
cycles
0x115 Signal Monitor
Period
Register 2
(Global)
Signal Monitor Period[23:16] 0x00 In ADC clock
cycles
0x116 Signal Monitor
Result
Channel A
Register 0
(Global)
Signal Monitor Result Channel A[7:0] Read only
0x117 Signal Monitor
Result
Channel A
Register 1
(Global)
Signal Monitor Result Channel A[15:8] Read only
0x118 Signal Monitor
Result
Channel A
Register 2
(Global)
Open Open Open Open Signal Monitor Value Channel A[19:16] Read only
0x119 Signal Monitor
Result
Channel B
Register 0
(Global)
Signal Monitor Result Channel B[7:0] Read only
AD9640
Rev. B | Page 46 of 52
Addr
(Hex)
Register
Name
Bit 7
(MSB) Bit 6 Bit 5 Bit 4 Bit 3 Bit 2 Bit 1
Bit 0
(LSB)
Default
Value
(Hex)
Default
Notes/
Comments
0x11A Signal Monitor
Result
Channel B
Register 1
(Global)
Signal Monitor Result Channel B[15:8] Read only
0x11B Signal Monitor
Result
Channel B
Register 2
(Global)
Open Open Open Open Signal Monitor Result Channel B[19:16] Read only
MEMORY MAP REGISTER DESCRIPTION
For additional information about functions controlled in
Register 0x00 to Register 0xFF, see the AN-877 Application Note,
Interfacing to High Speed ADCs via SPI.
Sync Control (Register 0x100)
Bit 7—Signal Monitor Sync Enable
Bit 7 enables the sync pulse from the external SYNC input to
the signal monitor block. The sync signal is passed when Bit 7
is high and Bit 0 is high. This is continuous sync mode.
Bits[6:3]—Reserved
Bit 2—Clock Divider Next Sync Only
If the sync enable bit (Address 0x100[0]) is high and the clock
divider sync enable (Address 0x100[1]) is high, Bit 2 allows the
clock divider to sync to the first sync pulse it receives and ignore
the rest. Address 0x100[1] resets after it syncs.
Bit 1—Clock Divider Sync Enable
Bit 1 gates the sync pulse to the clock divider. The sync signal is
passed when Bit 1 is high and Bit 0 is high. This is continuous
sync mode.
Bit 0—Master Sync Enable
Bit 0 must be high to enable any of the sync functions.
Fast Detect Control (Register 0x104)
Bits[7:4]—Reserved
Bits[3:1]—Fast Detect Mode Select
These bits set the mode of the fast detect output bits according
to Table 17.
Bit 0—Fast Detect Enable
Bit 0 is used to enable the fast detect bits. When the fast detect
outputs are disabled, the outputs go into a high impedance state.
In LVDS mode, when the outputs are interleaved, the outputs go
high-Z only if both channels are turned off (power-down/standby/
output disabled). If only one channel is turned off (power-down/
standby/output disabled), the fast detect outputs repeat the data
of the active channel.
Fine Upper Threshold (Register 0x106 and Register 0x107)
Register 0x106, Bits[7:0]—Fine Upper Threshold[7:0]
Register 0x107, Bits[7:5]—Reserved
Register 0x107, Bits[4:0]—Fine Upper Threshold[12:8]
These registers provide the fine upper limit threshold. This 13-bit
value is compared to the 13-bit magnitude from the ADC block
and, if the ADC magnitude exceeds this threshold value, the
F_UT flag is set.
Fine Lower Threshold (Register 0x108 and Register 0x109)
Register 0x108, Bits[7:0]—Fine Lower Threshold[7:0]
Register 0x109, Bits[7:5]—Reserved
Register 0x109, Bits[4:0]—Fine Lower Threshold[12:8]
These registers provide a fine lower limit threshold. This 13-bit
value is compared to the 13-bit magnitude from the ADC block
and, if the ADC magnitude is less than this threshold value, the
F_LT flag is set.
Signal Monitor DC Correction Control (Register 0x10C)
Bit 7—Reserved
Bit 6—DC Correction Freeze
When Bit 6 is set high, the dc correction is no longer updated
to the signal monitoring block. It holds the last dc value it
calculated.
Bits[5:2]—DC Correction Bandwidth
These bits set the averaging time of the signal monitor dc correc-
tion function. It is a 4-bit word that sets the bandwidth of the
correction block (see Table 26).
AD9640
Rev. B | Page 47 of 52
Table 26. DC Correction Bandwidth
DC Correction Control Register 0x10C[5:2] Bandwidth (Hz)
0000 1218.56
0001 609.28
0010 304.64
0011 152.32
0100 76.16
0101 38.08
0110 19.04
0111 9.52
1000 4.76
1001 2.38
1010 1.19
1011 0.60
1100 0.30
1101 0.15
1110 0.15
1111 0.15
Bit 1—DC Correction for Signal Path Enable
Setting Bit 1 high causes the output of the dc measurement
block to be summed with the data in the signal path to remove
the dc offset from the signal path.
Bit 0—DC Correction for SM Enable
Bit 0 enables the dc correction function in the signal monitoring
block. The dc correction is an averaging function that can be
used by the signal monitor to remove dc offset in the signal.
Removing this dc from the measurement allows a more accurate
reading.
Signal Monitor DC Value Channel A (Register 0x10D and
Register 0x10E)
Register 0x10D, Bits[7:0]—Channel A DC Value[7:0]
Register 0x10E, Bits[7:0]—Channel A DC Value[13:8]
These read-only registers hold the latest dc offset value computed
by the signal monitor for Channel A.
Signal Monitor DC Value Channel B (Register 0x10F and
Register 0x110)
Register 0x10F Bits[7:0]—Channel B DC Value[7:0]
Register 0x110 Bits[7:0]—Channel B DC Value[13:8]
These read-only registers hold the latest dc offset value computed
by the signal monitor for Channel B.
Signal Monitor SPORT Control (Register 0x111)
Bit 7—Reserved
Bit 6—RMS/MS Magnitude Output Enable
These bits enable the 20-bit rms or ms magnitude measurement
as output on the SPORT.
Bit 5—Peak Power Output Enable
Bit 5 enables the 13-bit peak measurement as output on
the SPORT.
Bit 4—Threshold Crossing Output Enable
Bit 4 enables the 13-bit threshold measurement as output on
the SPORT.
Bits[3:2]—SPORT SMI SCLK Divide
The values of these bits set the SPORT SMI SCLK divide ratio
from the input clock. A value of 0x01 sets divide by 2 (default),
a value of 0x10 sets divide by 4, and a value of 0x11 sets divide by 8.
Bit 1— SPORT SMI SCLK Sleep
Setting Bit 1 high causes the SMI SCLK to remain low when the
signal monitor block has no data to transfer.
Bit 0—Signal Monitor SPORT Output Enable
When set, Bit 0 enables the SPORT output of the signal monitor
to begin shifting out the result data from the signal monitor block.
Signal Monitor Control (Register 0x112)
Bit 7—Complex Power Calculation Mode Enable
This mode assumes I data is present on one channel and Q data
is present on the opposite channel. The result reported is the
complex power, measured as
22 QI +
Bits[6:4]—Reserved
Bit 3—Signal Monitor RMS/MS Select
Setting Bit 3 low selects rms power measurement mode. Setting
Bit 3 high selects ms power measurement mode.
Bits[2:1]—Signal Monitor Mode
Bit 2 and Bit 1 set the mode of the signal monitor for data output
to Register 0x116 to Register 0x11B. Setting Bit 2 and Bit 1 to
0x00 selects rms/ms power output; setting these bits to 0x01
selects peak power output; and setting 0x10 or 0x11 selects
threshold crossing output.
Bit 0—Signal Monitor Enable
Setting Bit 0 high enables the signal monitor block.
Signal Monitor Period (Register 0x113 to Register 0x115)
Register 0x113, Bits[7:0]—Signal Monitor Period[7:0]
Register 0x114, Bits[7:0]—Signal Monitor Period[15:8]
Register 0x115, Bits[7:0]—Signal Monitor Period[23:16]
This 24-bit value sets the number of clock cycles over which the
signal monitor performs its operation. Although this register
defaults to 64 (0x40), the minimum value for this register is 128
(0x80) cycles – writing values less than 128 can cause inaccurate
results.
AD9640
Rev. B | Page 48 of 52
Signal Monitor Result Channel A (Register 0x116 to
Register 0x118)
Register 0x116, Bits[7:0]—Signal Monitor Result
Channel A[7:0]
Register 0x117, Bits[7:0]—Signal Monitor Result
Channel A[15:8]
Register 0x118, Bits[7:4]—Reserved
Register 0x118, Bits[3:0]—Signal Monitor Result
Channel A[19:16]
This 20-bit value contains the result calculated by the signal
monitoring block for Channel A. The content is dependent on the
settings in Register 0x112[2:1].
Signal Monitor Result Channel B (Register 0x119 to
Register 0x11B)
Register 0x119, Bits[7:0]— Signal Monitor Result
Channel B[7:0]
Register 0x11A, Bits[7:0]—Signal Monitor Result
Channel B[15:8]
Register 0x11B, Bits[7:4]—Reserved
Register 0x11B, Bits[3:0]—Signal Monitor Result
Channel B[19:16]
This 20-bit value contains the result calculated by the signal
monitoring block for Channel B. The content is dependent on
the settings in Register 0x112[2:1].
AD9640
Rev. B | Page 49 of 52
APPLICATIONS INFORMATION
DESIGN GUIDELINES
Before starting design and layout of the AD9640 as a system,
it is recommended that the designer become familiar with these
guidelines, which discuss the special circuit connections and
layout requirements needed for certain pins.
Power and Ground Recommendations
When connecting power to the AD9640, it is recommended
that two separate 1.8 V supplies be used: one supply should be
used for analog (AVDD) and digital (DVDD), and a separate
supply should be used for the digital outputs (DRVDD). The
AVDD and DVDD supplies, while derived from the same
source, should be isolated with a ferrite bead or filter choke
and separate decoupling capacitors. The user can employ
several different decoupling capacitors to cover both high
and low frequencies. These should be located close to the
point of entry at the PC board level and close to the part’s
pins with minimal trace length.
A single PCB ground plane should be sufficient when using the
AD9640. With proper decoupling and smart partitioning of the
PCB analog, digital, and clock sections, optimum performance
is easily achieved.
LVDS Operation
The AD9640 defaults to CMOS output mode on power-up.
If LVDS operation is desired, this mode must be programmed
using the SPI configuration registers after power-up. When the
AD9640 powers up in CMOS mode with LVDS termination
resistors (100 Ω) on the outputs, the DRVDD current may be
higher than the typical value until the part is placed in LVDS
mode. This additional DRVDD current does not cause damage
to the AD9640, but it should be taken into account when consid-
ering the maximum DRVDD current for the part.
To avoid this additional DRVDD current, the AD9640 outputs
can be disabled at power-up by taking the OEB pin high. After
the part is placed into LVDS mode via the SPI port, the OEB
pin can be taken low to enable the outputs.
Exposed Paddle Thermal Heat Slug Recommendations
It is mandatory that the exposed paddle on the underside of the
ADC be connected to analog ground (AGND) to achieve the
best electrical and thermal performance. A continuous, exposed
(no solder mask), copper plane on the PCB should mate to the
AD9640 exposed paddle, Pin 0.
The copper plane should have several vias to achieve the lowest
possible resistive thermal path for heat dissipation to flow
through the bottom of the PCB. These vias should be filled or
plugged with nonconductive epoxy.
To maximize the coverage and adhesion between the ADC and
PCB, a silkscreen should be overlaid to partition the continuous
plane on the PCB into several uniform sections. This provides
several tie points between the two during the reflow process.
Using one continuous plane with no partitions guarantees only
one tie point between the ADC and PCB. See the evaluation
board for a PCB layout example. For detailed information about
packaging and PCB layout of chip scale packages, see the AN-772
Application Note, A Design and Manufacturing Guide for the
Lead Frame Chip Scale Package (LFCSP).
CML
The CML pin should be decoupled to ground with a 0.1 F
capacitor, as shown in Figure 47.
RBIAS
The AD9640 requires that a 10 kΩ resistor be placed between
the RBIAS pin and ground. This resistor sets the master current
reference of the ADC core and should have at least a 1% tolerance.
Reference Decoupling
The VREF pin should be externally decoupled to ground with a
low ESR 1.0 F capacitor in parallel with a 0.1 F ceramic, low
ESR capacitor.
SPI Port
The SPI port should not be active during periods when the full
dynamic performance of the converter is required. Because the
SCLK, CSB, and SDIO signals are typically asynchronous to the
ADC clock, noise from these signals can degrade converter
performance. If the on-board SPI bus is used for other devices,
it may be necessary to provide buffers between this bus and the
AD9640 to keep these signals from transitioning at the converter
inputs during critical sampling periods.
AD9640
Rev. B | Page 50 of 52
OUTLINE DIMENSIONS
COMP LI ANT TO JE DEC S TANDARDS MO-220- V M M D- 4
080108-C
0.25 M IN
TOP VIEW 8.75
BSC SQ
9.00
BSC SQ
1
64
16
17
49
48
32
33
0.50
0.40
0.30
0.50
BSC
0.20 RE F
12° MAX 0.80 M AX
0.65 TYP
1.00
0.85
0.80
7.50
REF
0.05 MA X
0.02 NO M
0.60 M A X
0.60
MAX
EXPOSED PAD
(BO T TOM VIEW )
SEATING
PLANE
PIN 1
INDICATOR
7.25
7.10 S Q
6.95
PIN 1
INDICATOR
0.30
0.23
0.18
FOR PRO PER CONNECTI ON OF
THE EX P O SE D PAD, REF E R TO
THE PIN CONFI GURATION AND
FUNCT ION DESCRIP TIONS
SECT ION OF THI S DATA SHEE T.
Figure 74. 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
9 mm × 9 mm Body, Very Thin Quad
(CP-64-3)
Dimensions shown in millimeters
COMPLIANT TO JEDEC STANDARDS MO-220-VMMD-4
041509-A
0.25 MIN
TOP VIEW 8.75
BSC SQ
9.00
BSC SQ
1
64
16
17
49
48
32
33
0.50
0.40
0.30
0.50
BSC
0.20 REF
12° MAX 0.80 MAX
0.65 TYP
1.00
0.85
0.80
7.50
REF
0.05 MAX
0.02 NOM
0.60 MAX
0.60
MAX
EXPOSED PAD
(BOTTOM VIEW)
SEATING
PLANE
PIN 1
INDICATOR
7.65
7.50 SQ
7.35
PIN 1
INDICATOR
0.30
0.23
0.18
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
SECTION OF THIS DATA SHEET.
Figure 75. 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
9 mm × 9 mm Body, Very Thin Quad
(CP-64-6)
Dimensions shown in millimeters
AD9640
Rev. B | Page 51 of 52
ORDERING GUIDE
Model Temperature Range Package Description Package Option
AD9640ABCPZ-1501, 2 −40°C to +85°C 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ] CP-64-6
AD9640ABCPZ-1251, 2 −40°C to +85°C 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ] CP-64-6
AD9640ABCPZ-1051, 2 −40°C to +85°C 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ] CP-64-6
AD9640ABCPZ-801, 2 −40°C to +85°C 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ] CP-64-6
AD9640ABCPZRL7-801, 2 −40°C to +85°C 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ] CP-64-6
AD9640BCPZ-1501 −40°C to +85°C 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ] CP-64-3
AD9640BCPZ-1251 −40°C to +85°C 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ] CP-64-3
AD9640BCPZ-1051 −40°C to +85°C 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ] CP-64-3
AD9640BCPZ-801 −40°C to +85°C 64-Lead Lead Frame Chip Scale Package [LFCSP_VQ] CP-64-3
AD9640-150EBZ1 Evaluation Board
AD9640-125EBZ1 Evaluation Board
AD9640-105EBZ1 Evaluation Board
AD9640-80EBZ1 Evaluation Board
1 Z = RoHS Compliant Part.
2 Recommended for use in new designs; reference PCN 09_0156.
AD9640
Rev. B | Page 52 of 52
NOTES
©2007–2009 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D06547-0-12/09(B)
Mouser Electronics
Authorized Distributor
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AD9640ABCPZ-105 AD9640ABCPZRL7-105 AD9640ABCPZ-150 AD9640ABCPZRL7-125 AD9640ABCPZRL7-80
