QT240-ISS - Atmel - Product.Network

lQQT240

4 K

OUCH

™ S

ENSOR

APPLICATIONS

Instrument panels

Gaming machines

Access systems

Pointing devices

Appliance controls

Security systems

PC Peripherals

Backlighted buttons

The QT240 charge-transfer (“QT’”) QTouch IC is a self-contained digital sensor IC capable of detecting near-proximity or touch

on 4 electrodes. It allows electrodes to project independent sense fields through any dielectric like glass, plastic, stone,

ceramic, and wood. It can also turn metal-bearing objects into intrinsic sensors, making them responsive to proximity or touch.

This capability coupled with its continuous self-calibration feature can lead to entirely new product concepts, adding high value

to product designs.

Each of the channels operates independently of the others, and each can be tuned for a unique sensitivity level by simply

changing its sample capacitor value. Two speeds are supported, one of which consumes only 90µA of typical current at 4V.

Unique among capacitance sensors, the device incorporates spread spectrum modulation for unsurpassed EMC compliance.

The devices are designed specifically for human interfaces, like control panels, appliances, gaming devices, lighting controls,

or anywhere a mechanical switch or button may be found; they may also be used for some material sensing and control

applications.

These devices feature a SYNC pin which allows for synchronization with additional similar parts and/or to an external source to

suppress interference. This pin doubles as a drive pin for spread-spectrum modulation. Option pins are provided which allow

different timing and feature settings.

The RISC core of these devices use signal processing techniques pioneered by Quantum which are designed to survive

numerous real-world challenges, such as ‘stuck sensor’ conditions, component ageing, moisture films, and signal drift.

By using the charge transfer principle, these devices deliver a level of performance clearly superior to older technologies yet

are highly cost-effective.

QT240 1.07/0804

Four independent QT touch circuits

Individual outputs per channel - active high

Projects prox fields through any dielectric

Sensitivity easily adjusted on a per-channel basis

100% autocal for life - no adjustments required

3.9V ~ 5.5V single supply operation

10s, 60s, infinite auto-recal timeout (strap options)

Sync pin for line sync to suppress noise

Spread spectrum operation

Pin options for auto recalibration timings

Extremely low cost per key

20-SSOP package

Lead-free version available

YesQT240-ISS-G-40

C to +85

NoQT240-ISS-40

C to +85

Lead-FreeSSOP-20T

AVAILABLE OPTIONS

1 - OVERVIEW

QT240 devices are burst mode digital charge-transfer (QT)

sensor ICs designed specifically for touch controls; they

include all hardware and signal processing functions

necessary to provide stable sensing under a wide variety of

conditions. Only a single low cost capacitor per channel is

required for operation.

Figures 1-1 and 1-2 show basic circuits for these devices.

See Table 1-1 for device pin listings.

The devices employ bursts of charge-transfer cycles to

acquire signals. Burst mode permits low power operation,

dramatically reduces RF emissions, lowers susceptibility to

RF fields, and yet permits excellent speed. Internally, signals

are digitally processed to reject impulse noise using a

'consensus' filter that requires six consecutive confirmations

of detection.

The QT switches and charge measurement hardware

functions are all internal to the device. A single-slope

switched capacitor ADC includes the QT charge and transfer

switches in a configuration that provides direct ADC

conversion; an external Cs capacitor accumulates the charge

from sense-plate Cx, which is then measured.

Larger values of Cx cause the charge transferred into Cs to

rise more rapidly, reducing available resolution; as a

minimum resolution is required for proper operation, this can

result in dramatically reduced gain. Larger values of Cs

reduce the rise of differential voltage across it, increasing

available resolution by permitting longer QT bursts. The

value of Cs can thus be increased to allow larger values of

Cx to be tolerated. The IC is responsive to both Cx and Cs,

and changes in either can result in substantial changes in

sensor gain.

Unused channels: If a channel is not used, a dummy sense

capacitor (nominal value: 1nF) of any type plus a 2.2K series

resistor must be connected between unused SNS pin pairs

ensure correct operation.

1.1 OPERATING MODES

The QT240 features spread-spectrum acquisition

capability, external synchronization of acquire

bursts, and fast and slow acquisition modes. These

modes are enabled via high-value resistors

connected to the SNS pins to ground or Vdd. These

resistors are required in every circuit.

There are two basic modes as shown in Figures 1-1

and 1-2.

Low-power Sync mode: In this mode the device

operates with about a 100ms response time and

very low current (about 90µA average at 4.0V). This

mode allows the device to be synchronized to an

external clock source, which can be used to either

suppress external interference (such as from

50/60Hz wiring) or to decrease response time

(which will also increase power consumption).

Spread-spectrum operation is not directly supported

in this mode. Sync usage is optional; the Sync pin

should simply be grounded if unused.

Fast, Spread-Spectrum mode: In this mode the

device operates with ~40ms response times but

higher current drain (~1.5mA @ 4.0V). This mode

also supports spread-spectrum operation via a few

optional passive parts (if desired). Sync operation is not

supported in this mode.

1.2 ELECTRODE DRIVE; WIRING

The QT240 has four completely independent sensing

channels. The conversion process treats Cs on each channel

as a floating transfer capacitor; as a direct result, sense

electrodes can be connected to either SNS pin and the

sensitivity and basic function will be the same; however

electrodes should be connected to SNSnK lines to reduce

EMI susceptibility.

The PCB traces, wiring, and any components associated

with or in contact with either SNS pin will become touch

sensitive and should be treated with caution to limit the touch

area to the desired location.

2 QT240 1.07/0804

IGURE

1-1 L

OWER

, S

YNCHRONIZED

IRCUIT

VDD

KEY 2

KEY 3

10nF

CS1

KEY 1

VDD

62K

10nF

CS3

10nF

CS4

2.2K

RS3

KEY 4

VDD

22K

RSNS1

2.2K

RS1

22K

RSNS4

2.2K

RS4

OPT1

OUT1

SYNC

OUT4

OUT2

OUT3

10nF

CS2

RS2

2.2K

VDD

10 second

timeout shown

SPEED

OPT

22K

RSNS2

OPT2

22K

RSNS3

QT240-ISS

Sense pin (to Cs3, electrode); OPT1SNS3K20

Sense pin (to Rs3 + Cs3)SNS319

Sense pin (to Cs4, electrode); OPT2SNS4K18

Sense pin (to Rs4 + Cs4)SNS417

Ground or no connectVSS16

Oscillator bias inOSC15

Power: +4.0 to +5V locally regulatedVDD14

Reset pin, active low. Can usually tie to Vdd./RES13

Output, key 4OUT412

Unbonded internallyn.c.11

Unbonded internallyn.c.10

Sync in and/or spread spectrum driveSYNC/SS9

GroundVSS8

Output, key 3OUT37

Output, key 2OUT26

Output, key 1OUT15

Sense pin (to Cs1, electrode); speed optionSNS1K4

Sense pin (to Rs1 + Cs1)SNS13

Sense pin (to Cs2, electrode)SNS2K2

Sense pin (to Rs2 + Cs2)SNS21

DescriptionNamePin

ABLE

1-1 P

ISTING

- QT240-ISS

Multiple touch electrodes connected to any SNSnK can be

used, for example to create control surfaces on both sides of

an object.

It is important to limit the amount of stray capacitance on the

SNS terminals, for example by minimizing trace lengths and

widths to allow for higher gain without requiring higher values

of Cs. Under heavy delta-Cx loading of one key, cross

coupling to another key’s trace can cause the other key to

trigger. Therefore, electrode traces from adjacent keys

should not be run close to each other over long runs in order

to minimize cross-coupling if large values of delta-Cx are

expected, for example when an electrode is directly touched.

This is not a problem when the electrodes are working

through a plastic panel with normal touch sensitivity.

1.3 SENSITIVITY

Sensitivity can be altered to suit various applications and

situations on a channel-by-channel basis. The easiest and

most direct way to impact sensitivity is to alter the value of

each Cs; more Cs yields higher sensitivity. Each channel has

its own Cs value and can therefore be independently

adjusted.

1.3.1 A

LTERNATIVE

AYS

NCREASE

ENSITIVITY

Sensitivity can also be increased by using bigger

electrode areas, reducing panel thickness, or using

a panel material with a higher dielectric constant.

1.3.2 D

ECREASING

ENSITIVITY

In some cases the circuit may be too sensitive.

Gain can be lowered further by a number of

strategies: a) making the electrode smaller, b)

making the electrode into a sparse mesh using a

high space-to-conductor ratio, or c) by decreasing

the Cs capacitors.

1.3.3 K

ALANCE

A number of factors can cause sensitivity

imbalances. Notably, SNS wiring to electrodes can

have differing stray amounts of capacitance to

ground. Increasing load capacitance will cause a

decrease in gain. Key size differences, and

proximity to other metal surfaces can also impact

gain.

The four keys may thus require ‘balancing’ to

achieve similar sensitivity levels. This can be best

accomplished by trimming the values of the four

Cs capacitors to achieve equilibrium. The four Rs

resistors have no effect on sensitivity and should

not be altered. Load capacitances can also be

added to overly sensitive channels to ground, to reduce their

gains. These should be on the order of a few picofarads.

2 - QT240 SPECIFICS

2.1 SIGNAL PROCESSING

These devices process all signals using 16 bit math, using a

number of algorithms pioneered by Quantum. These

algorithms are specifically designed to provide for high

survivability in the face of adverse environmental changes.

2.1.1 D

RIFT

OMPENSATION

Signal drift can occur because of changes in Cx, Cs, and

Vdd over time. If a low grade Cs capacitor is chosen, the

signal can drift greatly with temperature. If keys are subject

to extremes of temperature or humidity, the signal can also

drift. It is crucial that drift be compensated, else false

detections, non-detections, and sensitivity shifts will follow.

Drift compensation (Figure 2-1) is a method that makes the

reference level track the raw signal at a slow rate, only while

no detection is in effect. The rate of reference adjustment

must be performed slowly else legitimate detections

can also be ignored. The IC drift compensates each

channel independently using a slew-rate limited

change to the reference level; the threshold and

hysteresis values are slaved to this reference.

Once an object is sensed, the drift compensation

mechanism ceases since the signal is legitimately

high, and therefore should not cause the reference

level to change.

The signal drift compensation is 'asymmetric'; the

reference level drift-compensates in one direction

faster than it does in the other. Specifically, it

compensates faster for decreasing signals than for

increasing signals. Increasing signals should not be

3 QT240 1.07/0804

IGURE

1-2 F

AST

, S

PREAD

-S

PECTRUM

IRCUIT

VDD

KEY 2

KEY 3

OUT4

OUT1

OUT2

OUT3

10nF

CS1

RS1

2.2K

KEY 1

22nF

VDD

10nF

CS3

10nF

CS4

RS3

2.2K

KEY 4

VDD

22K

RSNS1

360K

22K

RSNS4

RS4

2.2K

OPT1

10nF

CS2

RS2

2.2K

180K

VDD

62K R4

10 second

timeout shown

22K

RSNS2

SPEED

OPT

OPT2

22K

RSNS3

QT240_ISS

Figure 2-1 Drift Compensation

Threshold

Signal Hysteresis

Reference

Output

compensated for quickly, since an approaching finger could

be compensated for partially or entirely before even

approaching the sense electrode. However, an obstruction

over the sense pad, for which the sensor has already made

full allowance for, could suddenly be removed leaving the

sensor with an artificially elevated reference level and thus

become insensitive to touch. In this latter case, the sensor

will compensate for the object's removal very quickly, usually

in only a few seconds.

With large values of Cs and small values of Cx, drift

compensation will appear to operate more slowly than with

the converse.

Drift Compensation in Slow Mode: Drift compensation

rates in Slow mode are preserved if there is no Sync signal,

and the rates are derived from the ~90ms Sleep interval.

However if there is a Sync signal, then drift compensation

rates are derived from an assumption that the Sync

periodicity is ~18ms (which is corresponds to 55.5Hz). Thus,

drift compensation timings in Sync mode are correct for an

~18ms Sync period but different (slower or faster) for other

Sync periods. For example a Sync period of 36ms would

halve the expected drift compensation rates.

2.1.2 T

HRESHOLD

EVEL

The internal threshold level is fixed at 12 counts for all four

channels. The hysteresis is fixed at 2 counts (17%).

2.1.3 M

-D

URATION

If a sufficiently large object contacts a key for a prolonged

duration, the signal will trigger a detection output preventing

further normal operation. To cure such ‘stuck key’ conditions,

the sensor includes a timer on each channel to monitor

detection duration. If a detection exceeds the maximum timer

setting, the timer causes the sensor to perform a full

recalibration (if not set for infinite). This is known as the Max

On-Duration feature.

After the Max On-Duration interval, the sensor channel will

once again function normally, even if partially or fully

obstructed, to the best of its ability given electrode

conditions. There are three timeout durations available via

strap option: 10s, 60s, and infinite (Table 2-2).

Max On-Duration works independently per channel; a

timeout on one channel has no effect on another channel.

Note also that the timings in Table 2-2 are dependent on the

oscillator frequency in fast mode. Doubling the

recommended frequency will halve the timeouts. This is not

true in Slow mode.

Infinite timeout is useful in applications where a prolonged

detection can occur and where the output must reflect the

detection no matter how long. In infinite timeout mode, the

designer should take care to be sure that drift in Cs, Cx, and

Vdd do not cause the device to ‘stick on’ inadvertently even

when the target object is removed from the sense field.

Timeouts are approximate and can vary substantially over

Vdd and temperature, and should not be relied upon for

critical functions. Timeouts are also dependent on operating

frequency in Fast mode.

Max On-Duration in Slow Mode: When Sync mode is used

in Slow mode, the Max On-Duration timings are derived from

the Sync period. The device assumes the Sync periodicity is

18ms (midway between 50Hz and 60Hz sync timings). Thus,

Max On-Duration timings in Sync mode are correct for an

18ms Sync period but different (shorter or longer) for other

Sync periods. For example a Sync period of 36ms would

double all expected Max On-Duration timings.

2.1.4 D

ETECTION

NTEGRATOR

It is desirable to suppress false detections due to electrical

noise or from quick brushes with an object. To this end,

these devices incorporate a per-key ‘Detection Integrator’

counter that increments with each signal detection exceeding

the signal threshold (Figure 2-1) until a limit count is

reached, after which an Out pin becomes active. If a ‘no

detect’ is sensed even once prior to the limit, this counter is

reset to zero and no detect output is generated. The required

limit count is 6.

The Detection Integrator can also be viewed as a

'consensus' vote requiring a detection in successive samples

to trigger an active output.

In slow mode, the detect integrator forces the device to

operate faster to confirm a detection. The six successive

acquisitions required to affirm a detection are done without

benefit of a low power sleep mode between bursts.

2.1.5 F

ORCED

ENSOR

ECALIBRATION

Pin 13 is a Reset pin, active-low, which in cases where

power is clean can be simply tied to Vdd. On power-up, the

device will automatically recalibrate all channels of sensing.

Pin 13 can also be controlled by logic or a microcontroller to

force the chip to recalibrate, by toggling it low for 10µs or

more, then raising it high again.

2.1.6 F

AST

OSITIVE

ECALIBRATION

If the sensed capacitance becomes lower by 5 counts than

the reference level for 2 seconds, the sensor will consider

this to be an error condition and will force a recalibration on

the affected channel.

2.2 OPTIONS

These devices are designed for maximum flexibility and can

accommodate most popular sensing requirements via option

pins.

The option pins are read on power-up and about once every

10 seconds while the device is not detecting touch on any

channel. Options are set using high value resistors

connected to certain SNS pins, to either Vdd or Vss. These

options are read 25 times over 250µs to ensure that they are

not influenced by noise pulses. All 25 samples must agree.

However, large values of Cx on the SNS wires can load

down the pins to the point where the 1M pullup resistors

cannot pull high fast enough, and the pins are read

erroneously as a result. Cx should be below 50pF to prevent

errors; this value can be read with a conventional

capacitance meter with the QT240 removed.

The option setting resistors are mandatory and cannot be

deleted. The must be strapped to either Vdd or Vss.

Speed option (Strap S1): This jumper selects whether the

device acts in a slower, low power mode with a response

time of approximately 100ms, or in a fast mode with a

response time of 40ms typical. Fast mode consumes

substantially more power than the slow mode, but also

enables the use of spread-spectrum detection. Only slow

mode supports the use of external Sync (Section 2.3).

4 QT240 1.07/0804

Response time can also be modified by changing the

oscillator frequency (Section 3.3).

Recalibration / toggle select (S2, S3): See Table 2-2.

There are 3 recalibration timing options (‘Max On-Duration’;

see Section 2.1.3) and one toggle mode option. The

recalibration options control how long it takes for a

continuous detection to trigger a recalibration on a key.

When such an event occurs, only the ‘stuck’ key is

recalibrated. S2 / S3 should be connected as shown in Table

2-2 to achieve the desired Max On-Duration of either 10s,

60s, or infinite.

Toggle option: One option is toggle mode, which allows all

four keys to behave with flip-flop action. In this mode, each

key’s corresponding OUT pin will toggle High / Low with

successive touches on the key. The underlying Max

On-Duration is 10s in this mode. If a timeout occurs in

Toggle mode, the toggle state is not affected. Toggle state

flips only when the corresponding Out pin goes High.

This is useful for controlling power loads, for example in

kitchen appliances, power tools, light switches, etc. or

wherever a ‘touch-on / touch-off’ effect is required.

2.3 SYNCHRONIZATION

Sync capability is only present in Slow mode (Section 2.2). If

SYNC is not desired, SYNC/SS should be connected to Vss.

Adjacent capacitive sensors that operate independently can

cross-interfere with each other in ways that will create

sensitivity shifts and spurious detections. Since Quantum’s

QT devices operate in burst mode, the opportunity exists to

solve this problem by time-sequencing sensing channels so

that physically adjacent keys do not sense at the same time.

Within the QT240 the four channels operate synchronously,

so it is not possible for these channels to cross interfere.

However 2 or more adjacent chips will cross-interfere if they

are not synchronized to each other. The same is true of the

effects of unsynchronized external noise sources.

External noise sources can also be heavily suppressed by

synchronizing the QT240 to the noise source period. External

noise creates an ‘aliasing’ or ‘beat’ frequency effect between

the sampling rate of the QT part and the external noise

frequency. This shows up as a random noise component on

the internal signals, which in turn can lead to false activation.

Mains frequency is one common source of interference. A

simple AC zero-crossing detector feeding the SYNC pin is

enough to suppress this kind of periodic noise. Multiple

devices tied to SYNC can be synchronized to the mains

frequency in this fashion.

If two physically adjacent devices are to be synchronized to

each other, they should be connected via the SYNC pin to a

clock source that is slower than the burst rate of either

device. For example, a 50Hz clock can synchronize two

QT240’s running with burst spacings of up to 10ms each.

The two QT240’s should be synchronized on opposite

phases of the clock source, ie the clock source should feed

one part and its inverted phase, the other part.

A sync pulse on SYNC/SS in slow mode acts to break the

QT240 out of its sleep state between bursts, and to do

another burst. The device will then go back to sleep again

and await a new SYNC pulse. If a Sync pulse does not arrive

within about 90ms, it will wake again and run normally.

External sync pulses can be used to accelerate response

time (at the expense of power) in Slow mode. Sync pulses

running at 25Hz for example will improve response time by a

factor of 2. Sync cannot be used to slow down the device.

Sync Mode Effects on Timings: In the absence of a Sync

signal, the Max On-Duration timings and drift compensation

rates in Slow mode are nominally correct. It should be

understood that the Max On-Duration timings and drift

compensation rates are slaved to the burst interval in Slow

mode, and that changing the burst interval will have direct

effects on these parameters.

Since the most common use of Sync is to synchronize the

device to Mains frequency (50 or 60Hz) the device makes an

assumption that the presence of a Sync signal is at 55Hz,

and the timings are made to be correct at this frequency.

Should the Sync pulses vary from this frequency, the Max

On-Duration timings and drift compensation rates will vary

proportionately. Thus, if the Sync pulses are 25Hz, the

10-second Max On-Duration timing will become 10*55/25 =

22 seconds nominal. Only at Sync=55Hz with the 10s

timeout be 10s (the same as if there were no Sync signal, or

the device was in Fast mode).

3 - CIRCUIT GUIDELINES

3.1 CS SAMPLE CAPACITOR

Charge sampler caps Cs can be virtually any plastic film or

low to medium-K ceramic capacitor. The ‘normal’ Cs range is

4.7nF to 47nF depending on the sensitivity required; larger

values of Cs require higher stability to ensure reliable

sensing. Acceptable capacitor types for most uses include

plastic film (especially PPS film and polypropylene film) and

X7R ceramic. Lower grades than X7R are not advised;

higher-K ceramics have nonlinear dielectrics which induce

instabilities.

3.2 POWER SUPPLY, PCB LAYOUT

The power supply can range from 3.9 to 5.5 volts. If this

fluctuates slowly with temperature, the device will track and

compensate for these changes automatically with only minor

changes in sensitivity. If the supply voltage drifts or shift

quickly, the drift compensation mechanism will not be able to

keep up, causing sensitivity anomalies or false detections.

5 QT240 1.07/0804

VddSlow / Sync

VssFast / Spread Spectrum

ABLE

2-1 S1 S

PEED

/ S

YNC

PTIONS

- SNS1K P

Timings assume 100 kHz operation

infiniteVssVss

DC Out

10sVddVdd

Toggle

60sVssVdd

DC Out

10sVddVss

DC Out

Max On-Duration

SNS4K pin 18

SNS3K pin 20

ABLE

2-2 OPT O

PTIONS

The QT240 will track slow changes in Vdd, but can be

seriously affected by rapid voltage steps.

If the supply is shared with another electronic system, care

should be taken to assure that the supply is free of digital

spikes, sags, and surges which can cause adverse effects.

The supply is best locally regulated using almost any

3-terminal LDO device from 4.0V to 5V.

For proper operation a 0.1µF or greater bypass capacitor

must be used between Vdd and Vss; the bypass cap should

be placed very close to the device Vss and Vdd pins.

The PCB should if possible include a copper pour under and

around the IC, but not extensively under the SNS lines.

3.3 OSCILLATOR; SPREAD SPECTRUM

The oscillator is an internal type using an external current

bias source. Normal operation occurs at ~100 kHz +/-20%

with R=62K at Vdd = 4.0V.

In Fast mode the oscillator can be spread-spectrum

modulated with a simple external RC network to avoid

dwelling on any one frequency. The circuit works by current

modulating the oscillator bias to provide a chirp modulation

within each burst. This helps dramatically with both RF

emissions and susceptibility. The circuit for this is shown in

Figure 1-2. The SYNC/SS pin outputs a rectangular pulse

with a period of one burst. At the end of the burst, SYNC/SS

clamps to ground. This forms a sawtooth modulation

waveform to create the frequency chirp modulation (Figure

3-1).

The detection integrator (DI) filters out false detections

caused by interference on up to any 6 of these acquisitions.

The DI is a consensus filter that throws out a pending

detection if even one of the 6 samples does not confirm a

detection. As a result of this feature, it is extremely difficult

for an external signal to interfere with the device.

The typical modulation band of this circuit is +/-7% around

the center frequency.

The oscillator frequency can be measured by observing the

acquisition pulses on any sense channel with an

oscilloscope. The first two positive pulses in each burst will

be exactly 10µs from rising edge to rising edge

(100kHz) if the oscillator is set correctly (no

spread spectrum). Some subsequent pulse

pairs will have wider spacings; this is normal.

If desired the response time of the device in

Fast mode can be modified by altering the

oscillator frequency. The device can be set to

any center frequency from 20kHz to 150kHz by

simply altering the value of the bias resistor.

Lower values of R will speed up the device.

Higher resistor values will slow down the device

and reduce power consumption.

Slow mode relies on an internal RC timer which

cannot be adjusted via the bias resistor. During

intervals between bursts in Slow mode, the

100kHz oscillator is disabled.

Spread Spectrum in Slow Mode: The QT240

does not support spread spectrum in Slow

mode directly via the SYNC/SS pin. However,

the designer can still implement spread

spectrum by modulating the oscillator through a resistor to

OSC with a triangle or sawtooth wave.

The modulation signal should be exactly synchronous with

each burst, so that the resulting acquired signal is modulated

in the same way. If this rule is not followed, the signals will

contain modulation noise and false detections may occur.

3.4 UNUSED CHANNELS

Unused SNS pins should not be left open. They should have

a small value non-critical dummy Cs capacitor plus a 2.2K

series-R connected to their SNS pins to allow the internal

circuit to continue to function properly. A nominal value of

1nF (1,000pF) X7R ceramic will suffice.

Unused channels should not have sense traces or

electrodes connected to them except for the required option

resistors, which must always be installed and connected to

Vdd or Vss.

3.5 ESD PROTECTION

Normally, only a series resistor is required for ESD

suppression. A 22K Rsns resistor in series with the sense

trace is sufficient in most cases. The dielectric panel (glass

or plastic) usually provides a high degree of isolation to

prevent ESD discharge from reaching the circuit. Rsns

should be placed close to the chip.

If the Cx load is high, Rsns can prevent total charge and

transfer and as a result gain can deteriorate. If a reduction in

Rsns increases gain noticeably, the lower value should be

used. Conversely, increasing the Rsns can result in added

ESD and EMC benefits provided that the increase does not

decrease sensitivity.

3.6 CROSSTALK PRECAUTIONS

Adjacent sense traces might require intervening ground

traces in order to reduce capacitive cross bleed if high

sensitivity is required or high values of delta-Cx are

anticipated (for example, from direct human touch to an

electrode connection). In normal touch applications behind

plastic panels this is almost never a problem regardless of

how the electrodes are wired.

6 QT240 1.07/0804

Figure 3-1 Spread-Spectrum Waveforms

Higher values of Rsns will make crosstalk problems worse;

try to keep Rsns to 22K or less if possible.

In general try to keep the QT240 close to the electrodes and

reduce the adjacency of the sense wiring to ground planes

and other signal traces; this will reduce the Cx load, reduce

interference effects, and increase signal gain.

The one and only valid reason to run ground near SNS

traces is to provide crosstalk isolation between traces, and

then only on an as-needed basis.

7 QT240 1.07/0804

4.1 ABSOLUTE MAXIMUM SPECIFICATIONS

Operating temp................................................................................ as designated by suffix

Storage temp....................................................................................... -55

C to +105

VDD.................................................................................................... -0.3 to +5.5V

Max continuous pin current, any control or drive pin..............................................................±20mA

Short circuit duration to ground, any pin......................................................................... infinite

Short circuit duration to VDD, any pin............................................................................ infinite

Voltage forced onto any pin...................................................................-0.3V to (Vdd + 0.3) Volts

4.2 RECOMMENDED OPERATING CONDITIONS

VDD....................................................................................................+3.9 to +5.0V

Operating temperature range, 4.0V - 5.5V................................................................... -40 - +85C

Operating frequency, 4.0V - 5.5V............................................................................. 100 kHz

Short-term supply ripple+noise..................................................................................±5mV

Long-term supply stability.................................................................................... ±100mV

Cs (reference capacitors) value......................................................................... 4.7nF to 47nF

Cx (SNS load capacitance) maximum value.......................................................................50pF

4.3 AC SPECIFICATIONS

Vdd = 4.0, Ta = recommended, Cx = 10pF, Cs = 10nF, Rosc = 62K ohms

Fast mode onlybursts6Spread spectrum drive intervalT

% of Fosc; fast mode only;

Circuit of Figure 1-2

%+/-7Spread spectrum freq deviationF

SSD

Either speed modekHz12010080Acquisition center frequencyF

OSC

Fast mode

Slow mode

110

Response time to outputT

Either speed modecounts250Burst length, each channelN

Either speed modems4Burst duration, all channelsT

Either speed modeµs8Clamp durationT

Either speed modeµs2Pulse durationT

Fast mode

Slow mode

180

280

Recalibration time from cold

start or hard reset

Notes

UnitsMaxTypMinDescription

Parameter

4.4 DC SPECIFICATIONS

Vdd = 4.0V, Cx = 10pF, Cs = 10nF, Fosc = 100kHz, Ta = recommended range, unless otherwise noted

bits9Acquisition resolutionA

OPT1, OPT2, OPT3µA±1Input leakage currentI

OUTn, 1mA sourceVVdd-0.7High output voltageV

OUTn, 4mA sinkV0.6Low output voltageV

SYNC, RSTV2High input logic levelV

SYNC, RSTV0.7Low input logic levelV

Req’d for startup, w/o reset circuitV/s100Supply turn-on slopeV

DDS

Fast mode

Slow mode, no Sync

µA

1.5

Supply currentI

Notes

UnitsMaxTypMinDescription

Parameter

8 QT240 1.07/0804

4.5 SIGNAL PROCESSING

Vdd = 4.0V, Cx = 10pF, Cs = 10nF, Fosc = 100kHz, Ta = recommended range, unless otherwise noted

Option pin selected;

Nominal timings; dependent on Fosc, Sync

secs10, 60, infinitePost-detection recalibration timer duration

Nominal timing dependent on Fosc, Syncsecs2Fast negative recalibration timer duration

Nominal timing dependent on Fosc, Syncms/level250Negative drift compensation rate

Nominal timing dependent on Fosc, Syncms/level1,000Positive drift compensation rate

samples6Consensus filter length (Detection integrator)

counts5Fast negative threshold differential

From thresholdcounts2Hysteresis

From signal referencecounts12Threshold differential (positive)

Notes

UnitsValueDescription

5 - PACKAGE OUTLINE

Base level

Seating level

8º0º8º0º

0.200.108.04.0H

0.860.6634.026.0G

0.250.1010.04.0F

-0.635--25.0-E

1.851.6573.065.0D

7.496.88295.0271.0C’

0.380.2315.09.0C

5.594.98220.0196.0B

8.207.39323.0291.0A

MaxTypMinMaxTypMin

Metric (mm)Inches (mils)

SYMBOL

209 mil 20-pin SSOP Dimensions

6 - ORDERING INFORMATION

YesQT240-IGSSOP-20-40 - 85CQT240-ISS-G

NoQT240-ISSOP-20-40 - 85CQT240-ISS

LEAD-FREEMARKINGPACKAGETEMP RANGEPART

9 QT240 1.07/0804

Patented and patents pending

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Tel: 412-391-7367 Fax: 412-291-1015

The specifications set out in this document are subject to change without notice. All products sold and services supplied by QRG are subject

to our Terms and Conditions of sale and supply of services which are available online at www.qprox.com and are supplied with every order

acknowledgement. QProx, QTouch, QMatrix, QLevel, QView, QWheel, and QSlide are trademarks of QRG. QRG products are not suitable

for medical (including life-saving equipment), safety or mission critical applications or other similar purposes. Except as expressly set out in

QRG's Terms and Conditions, no licenses to patents or other intellectual property of QRG (express or implied) are granted by QRG in

connection with the sale of QRG products or provision of QRG services. QRG will not be liable for customer product design and customers

are entirely responsible for their products and applications which incorporate QRG's products.