CS5480 Three Channel Energy Measurement IC Features Description Description * The CS5480 is a high-accuracy, three-channel, energy measurement analog front end. * * * * * * * * * * * * * * * * * Superior Analog Performance with Ultra-low Noise Level & High SNR Energy Measurement Accuracy of 0.1% over 4000:1 Dynamic Range Current RMS Measurement Accuracy of 0.1% over 1000:1 Dynamic Range 3 Independent 24-bit, 4th-order, Delta-Sigma Modulators for Voltage and Current Measurements 3 Configurable Digital Outputs for Energy Pulses, Zero-crossing, or Energy Direction Supports Shunt Resistor, CT, & Rogowski Coil Current Sensors On-chip Measurements & Calculations: - Active, Reactive, and Apparent Power - RMS Voltage and Current - Power Factor and Line Frequency - Instantaneous Voltage, Current, and Power Overcurrent, Voltage Sag, and Voltage Swell Detection Ultra-fast On-chip Digital Calibration Internal Register Protection via Checksum and Write Protection UART/SPITM Serial Interface On-chip Temperature Sensor On-chip Voltage Reference (25 ppm / C Typ.) Single 3.3V Power Supply Ultra-fine Phase Compensation Low Power Consumption: <13 mW Power Supply Configurations GNDA = GNDD = 0 V, VDDA = +3.3 V 4mm x 4mm, 24-pin QFN Package ORDERING INFORMATION See Page 68. VDDA The CS5480 incorporates independent, 4th order, Delta-Sigma analog-to-digital converters for every channel, reference circuitry, and the proven EXL signal processing core to provide active, reactive, and apparent energy measurement. In addition, RMS and power factor calculations are available. Calculations are output via configurable energy pulse, or direct UART/SPITM serial access to on-chip registers. Instantaneous current, voltage, and power measurements are also available over the serial port. Multiple serial options are offered to allow customer flexibility. The SPI provides higher speed, and the 2-wire UART minimizes the cost of isolation where required. Three configurable digital outputs provide energy pulses, zerocrossing, energy direction, and interrupt functions. Interrupts can be generated for a variety of conditions including voltage sag or swell, overcurrent, and more. On-chip register integrity is assured via checksum and write protection. The CS5480 is designed to interface to a variety of voltage and current sensors including shunt resistors, current transformers, and Rogowski coils. On-chip functionality makes digital calibration simple and ultra-fast, minimizing the time required at the end of the customer production line. Performance across temperature is ensured with an on-chip voltage reference with very low drift. A single 3.3V power supply is required, and power consumption is very low at <13mW. To minimize space requirements, the CS5480 is offered in a low-cost, 4mm x 4mm 24-pin QFN package. VDDD RESET CS5480 IIN1+ IIN1- PGA 4th Order Modulator Digital Filter HPF Option SSEL IIN2+ IIN2- PGA 4th Order Modulator Digital Filter UART/SPI Serial Interface HPF Option CS RX / SDI TX / SDO SCLK VIN+ VIN- VREF+ VREF- 10x Voltage Reference 4th Order Modulator Cirrus Logic, Inc. http://www.cirrus.com HPF Option Calculation Energy To Pulse Conversion Temperature Sensor System Clock GNDA Digital Filter XOUT Copyright Cirrus Logic, Inc. 2012 (All Rights Reserved) DO3 MODE Clock Generator XIN DO1 DO2 GNDD JAN'12 DS893F1 CS5480 TABLE OF CONTENTS 1. Overview . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .5 2. Pin Description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .6 2.1 Analog Pins . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 2.1.1 Voltage Input . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 2.1.2 Current1 and Current2 Inputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 2.1.3 Voltage Reference . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 2.1.4 Crystal Oscillator . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 2.2 Digital Pins . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 2.2.1 Reset Input . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 2.2.2 Digital Outputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 2.2.3 UART/SPITM Serial Interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7 2.2.3.1 SPI . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .8 2.2.3.2 UART . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .8 2.2.4 MODE Pin . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .8 3. Characteristics and Specifications . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .9 4. Signal Flow Description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17 4.1 Analog-to-Digital Converters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17 4.2 Decimation Filters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17 4.3 IIR Filters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17 4.4 Phase Compensation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 4.5 DC Offset and Gain Correction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 4.6 High-pass and Phase Matching Filters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 4.7 Digital Integrators . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 4.8 Low-rate Calculations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 4.8.1 RMS Current and Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19 4.8.2 Active Power . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .19 4.8.3 Reactive Power . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19 4.8.4 Apparent Power . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19 4.8.5 Peak Voltage and Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19 4.8.6 Power Factor . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .19 4.9 Average Active Power Offset . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .19 4.10 Average Reactive Power Offset . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19 5. Functional Description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 5.1 Power-on Reset . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 5.2 Power Saving Modes . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 5.3 Zero-crossing Detection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 5.4 Line Frequency Measurement . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 5.5 Meter Configuration Modes . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 21 5.6 Tamper Detection and Correction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .22 5.6.1 Anti-tampering on Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 5.6.1.1 Automatic Channel Selection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 5.6.1.2 Manual Channel Selection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23 5.6.2 Anti-tampering on Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .23 5.7 Energy Pulse Generation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23 5.7.1 Pulse Rate . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 24 5.7.2 Pulse Width . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 24 2 DS893F1 CS5480 5.8 Voltage Sag, Voltage Swell, and Overcurrent Detection . . . . . . . . . . . . . . . . . . . . . 24 5.9 Phase Sequence Detection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25 5.10 Temperature Measurement . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 26 5.11 Anti-Creep . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 26 5.12 Register Protection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 26 5.12.1 Write Protection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 26 5.12.2 Register Checksum . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 26 6. Host Commands and Registers . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27 6.1 Host Commands . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27 6.1.1 Memory Access Commands . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27 6.1.1.1 Page Select . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27 6.1.1.2 Register Read . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27 6.1.1.3 Register Write . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27 6.1.2 Instructions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27 6.1.3 Checksum . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 28 6.1.4 Serial Time Out . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 28 6.2 Hardware Registers Summary (Page 0) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 29 6.3 Software Registers Summary (Page 16) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 31 6.4 Software Registers Summary (Page 17) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 33 6.5 Software Registers Summary (Page 18) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 34 6.6 Register Descriptions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 35 7. System Calibration . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 62 7.1 Calibration in General . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 62 7.1.1 Offset Calibration . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 62 7.1.1.1 DC Offset Calibration . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 62 7.1.1.2 Current Channel AC Offset Calibration . . . . . . . . . . . . . . . . . . . . . . . 62 7.1.2 Gain Calibration . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 63 7.1.3 Calibration Order . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 63 7.2 Phase Compensation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 63 7.3 Temperature Sensor Calibration . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 64 7.3.1 Temperature Offset and Gain Calibration . . . . . . . . . . . . . . . . . . . . . . . . . . . 64 8. Basic Application Circuits . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 65 9. Package Dimensions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 67 10. Ordering Information . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 68 11. Environmental, Manufacturing, and Handling Information . . . . . . . . . . . . . . . . . . . . . 68 12. Revision History . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 68 DS893F1 3 CS5480 LIST OF FIGURES Figure 1. Oscillator Connections................................................................................................... 7 Figure 2. Multi-device UART Connections.................................................................................... 8 Figure 3. UART Serial Frame Format ........................................................................................... 8 Figure 4. Active Energy Load Performance.................................................................................. 9 Figure 5. Reactive Energy Load Performance............................................................................ 10 Figure 6. IRMS Load Performance ............................................................................................. 10 Figure 7. SPI Data and Clock Timing ......................................................................................... 15 Figure 8. Multi-device UART Timing........................................................................................... 15 Figure 9. Signal Flow for V1, I1, P1, Q1 Measurements ............................................................ 17 Figure 10. Signal Flow for V2, I2, P2, and Q2 Measurements ................................................... 17 Figure 11. Low-rate Calculations ................................................................................................ 18 Figure 12. Power-on Reset Timing ............................................................................................. 20 Figure 13. Channel Selection and Tamper Protection Flow ....................................................... 21 Figure 14. Automatic Channel Selection .................................................................................... 22 Figure 15. Energy Pulse Generation and Digital Output Control ................................................ 23 Figure 16. Sag, Swell, and Overcurrent Detect .......................................................................... 24 Figure 17. Phase Sequence A, B, C for Rising Edge Transition ................................................ 25 Figure 18. Phase Sequence C, B, A for Rising Edge Transition ................................................ 25 Figure 19. Byte Sequence for Page Select................................................................................. 27 Figure 20. Byte Sequence for Register Read ............................................................................. 27 Figure 21. Byte Sequence for Register Write ............................................................................. 27 Figure 22. Byte Sequence for Instructions.................................................................................. 27 Figure 23. Byte Sequence for Checksum ................................................................................... 28 Figure 24. Calibration Data Flow ................................................................................................ 62 Figure 25. T Register vs. Force Temp ........................................................................................ 64 Figure 26. Typical Single-phase 3-Wire Connection .................................................................. 65 Figure 27. Typical Single-phase 2-Wire Connection .................................................................. 66 LIST OF TABLES Table 1. POR Thresholds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 Table 2. Meter Configuration Modes . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 21 Table 3. Command Format . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27 Table 4. Instruction Format . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27 4 DS893F1 CS5480 1. OVERVIEW The CS5480 is a CMOS power measurement integrated circuit that uses three analog-to-digital converters to measure line voltages, two currents and temperature. It calculates active, reactive, and apparent power as well as RMS voltage and current and peak voltage and current. It handles other system-related functions, such as energy pulse generation, voltage sag and swell, overcurrent and zero-crossing detection, and line frequency measurement. The CS5480 is optimized to interface to current transformers, shunt resistors, or Rogowski coils for current measurement and to resistive dividers or voltage transformers for voltage measurement. Two full-scale ranges are provided on the current inputs to accommodate different types of current sensors. The CS5480's three differential inputs have a common-mode input range from analog ground (GNDA) to the positive analog supply (VDDA). An on-chip voltage reference (nominally 2.4 volts) is generated and provided at analog output, VREF. Three digital outputs (DO1, DO2, and DO3) provide a variety of output signals, and depending on the mode selected, energy pulses, zero-crossings, or other choices. The CS5480 includes a UART/SPITM serial host interface to an external microcontroller. The serial select (SSEL) pin is used to configure the serial port to be a SPI or UART. SPI signals include serial data input (SDI), serial data output (SDO), and serial clock (SCLK). UART signals include serial data input (RX) and serial data output (TX). A chip select (CS) signal allows multiple CS5480s to share the same serial interface with the microcontroller. DS893F1 5 CS5480 XOUT VDDD GNDD MODE SSEL CS 2. PIN DESCRIPTION 24 23 22 21 20 19 XIN 1 18 SCLK RESET 2 17 RX/SDI IIN1- 3 16 TX/SDO IIN1+ 4 15 DO3 VIN+ 5 14 DO2 VIN- 6 13 DO1 Thermal Pad 7 8 9 10 11 12 IIN2- IIN2+ VREF- VREF+ GNDA VDDA Top-Down (Through Package) View 24-Pin QFN Package Clock Generator Crystal In Crystal Out 1,24 XIN, XOUT -- Connect to an external quartz crystal. Alternatively, an external clock can be supplied to the XIN pin to provide the system clock for the device. Digital Pins and Serial Data I/O Digital Outputs 13,14,15 DO1, DO2, DO3 -- Configurable digital outputs for energy pulses, interrupt, tamper indication, energy direction, and zero-crossings. Reset Serial Data I/O 2 16,17 RESET -- An active-low Schmitt-trigger input used to reset the chip. TX/SDO, RX/SDI -- UART/SPI serial data output/input. Serial Clock Input 18 SCLK -- Serial clock for the SPI. Serial Mode Select 20 SSEL -- Selects the type of the serial interface, UART or SPITM. Logic level one - UART selected. Logic level zero - SPI selected. Chip Select 19 CS -- Chip select for the UART/SPI. Operating Mode Select 21 MODE -- Connect to VDDA for proper operation. 5,6 VIN+, VIN- -- Differential analog input for the voltage channel. Analog Inputs/Outputs Voltage Input Current Inputs Voltage Reference 4,3,8,7 IIN1+, IIN1-, IIN2+, IIN2- -- Differential analog inputs for the current channels. 10,9 VREF+, VREF- -- The internal voltage reference. A 0.1 F bypass capacitor is required between these two pins. Internal Digital Supply 23 VDDD -- Decoupling pin for the internal 1.8V digital supply. A 0.1F bypass capacitor is required between this pin and GNDD. Digital Ground 22 GNDD -- Digital ground. Positive Analog Supply 12 VDDA -- The positive 3.3V analog supply. Analog Ground 11 GNDA -- Analog ground. - No Electrical Connection. Power Supply Connections Thermal Pad 6 DS893F1 CS5480 2.1 Analog Pins The CS5480 has a differential input (VIN) for voltage input and two differential inputs IIN1 IIN2) for current1 and current2 inputs. The CS5480 also has two voltage reference pins (VREF) between which a bypass capacitor should be placed. XIN XOUT 2.1.1 Voltage Input The output of the line voltage resistive divider or transformer is connected to the (VIN) input of the CS5480. The voltage channel is equipped with a 10x, fixed-gain amplifier. The full-scale signal level that can be applied to the voltage channel is 250mV. If the input signal is a sine wave, the maximum RMS voltage is 250mVp/ 2 176.78 mVrms, which is approximately 70.7% of maximum peak voltage. 2.1.2 Current1 and Current2 Inputs The output of the current-sensing shunt resistor, transformer, or Rogowski coil is connected to the IIN1 or IIN2 input pins of the CS5480. To accommodate different current-sensing elements, the current channel incorporates a programmable gain amplifier (PGA) with two selectable input gains, as described in Config0 register description section 6.6.1 Configuration 0 (Config0) - Page 0, Address 0 on page 35. There is a 10x gain setting and a 50x gain setting. The full-scale signal level for current channels is 50mV and 250mV for 50x and 10x gain settings, respectively. If the input signal is a sine wave, the maximum RMS voltage is 35.35mVRMS or 176.78mVRMS, which is approximately 70.7% of maximum peak voltage. 2.1.3 Voltage Reference The CS5480 generates a stable voltage reference of 2.4V between the VREF pins. The reference system also requires a filter capacitor of at least 0.1F between the VREF pins. The reference system is capable of providing a reference for the CS5480 but has limited ability to drive external circuitry. It is strongly recommended that nothing other than the required filter capacitor be connected to the VREF pins. 2.1.4 Crystal Oscillator An external, 4.096MHz quartz crystal can be connected to the XIN and XOUT pins, as shown in Figure 1. To reduce system cost, each pin is supplied with an on-chip load capacitor. DS893F1 C1 = 22pF C2 = 22pF Figure 1. Oscillator Connections Alternatively, an external connected to the XIN pin. clock source can be 2.2 Digital Pins 2.2.1 Reset Input The active-low RESET pin, when asserted for longer than 120s, will halt all CS5480 operations and reset internal hardware registers and states. When de-asserted, an initialization sequence begins, setting default register values. To prevent erroneous noise-induced resets to the CS5480, an external pull-up resistor and a decoupling capacitor are necessary on the RESET pin. 2.2.2 Digital Outputs The CS5480 provides three configurable digital outputs (DO1-DO3). They can be configured to output energy pulses, interrupt, zero-crossings, or energy directions. Refer to the description of the Config1 register in section 6.6.2 Configuration 1 (Config1) - Page 0, Address 1 on page 36 for more details. 2.2.3 UART/SPITM Serial Interface The CS5480 provides five pins--SSEL, RX/SDI, TX/SDO, CS, and SCLK--for communication between a host microcontroller and the CS5480. SSEL is an input that, when low, indicates to the CS5480 to use the SPI port as the serial interface to communicate with the host microcontroller. The SSEL pin has an internal weak pull-up. When the SSEL pin is left unconnected or pulled high externally, the UART port is used as the serial interface. 7 CS5480 2.2.3.1 SPI The CS5480 provides a Serial Peripheral Interface (SPI) that operates as a slave device in 4-wire mode and supports multiple slaves on the SPI bus. The 4-wire SPI includes CS, SCLK, SDI, and SDO signals. SLAVE 0 UART MASTER CS is the chip select input for the CS5480 SPI port. A high logic level de-asserts it, tri-stating the SDO pin and clearing the SPI interface. A low logic level enables the SPI port. Although the CS pin may be tied low for systems that do not require multiple SDO drivers, using the CS signal is strongly recommended to achieve a more reliable SPI communication. SDO is the serial data output from the CS5480. The CS5480 SPI transmits and receives data MSB first. Refer to Switching Characteristics on page 14 and Figure 7 on page 15 for more detailed information of SPI timing. 2.2.3.2 UART The CS5480 device contains an asynchronous, full-duplex UART. The UART may be used in either standard 2-wire communication mode (RX/TX) for connecting a single device or 3-wire communication mode (RX/TX/CS) for connecting multiple devices. When connecting a single CS5480 device, CS should be held low to enable the UART. Multiple CS5480 devices can communicate to the same master UART in the 3-wire mode by pulling a slave CS pin low during data transmissions. Common RX and TX signals are provided to all the slave devices, and each slave device requires a separate CS signal for enabling communication to that slave. The multi-device UART mode connections are shown in Figure 2. CS RX TX CSN SLAVE 1 CS RX TX SLAVE N CS RX TX SCLK is the serial clock input for the CS5480 SPI port. Serial data changes as a result of the falling edge of SCLK and is valid at the rising edge. The SCLK pin is a Schmitt-trigger input. SDI is the serial data input to the CS5480. CS0 TX RX CS1 Figure 2. Multi-device UART Connections The multi-device UART mode timing diagram provides the timing requirements for the CS control (see Figure 8. Multi-device UART Timing on page15). The CS5480 UART operates in 8-bit mode, which transmits a total of 10 bits per byte. Data is transmitted and received LSB first, with one start bit, eight data bits, and one stop bit. IDLE START 0 1 2 3 4 5 6 7 STOP IDLE DATA Figure 3. UART Serial Frame Format The baud rate is defined in the SerialCtrl register. After chip reset, the default baud rate is 600, if MCLK is 4.096MHz. The baud rate is based on the contents of bits BR[15:0] in the SerialCtrl register and is calculated as follows: BR[15:0] = Baud Rate x (524288/MCLK) or Baud Rate = BR[15:0] / (524288/MCLK) The maximum baud rate is 512K if MCLK is 4.096MHz. 2.2.4 MODE Pin The MODE pin must be tied to VDDA for normal operation. The MODE pin is used primarily for factory test procedures. 8 DS893F1 CS5480 3. CHARACTERISTICS AND SPECIFICATIONS RECOMMENDED OPERATING CONDITIONS Parameter Positive Analog Power Supply Specified Temperature Range Symbol VDDA TA Min 3.0 -40 Typ 3.3 - Max 3.6 +85 Unit V C POWER MEASUREMENT CHARACTERISTICS Parameter Active Energy (Note 1 and 2) Reactive Energy (Note 1 and 2) Apparent Power (Note 1 and 3) Current RMS (Note 1, 3, and 4) Symbol Min Typ Max Unit All Gain Ranges Current Channel Input Signal Dynamic Range 4000:1 PAvg - 0.1 - % All Gain Ranges Current Channel Input Signal Dynamic Range 4000:1 QAvg - 0.1 - % All Gain Ranges Current Channel Input Signal Dynamic Range 1000:1 S - 0.1 - % All Gain Ranges Current Channel Input Signal Dynamic Range 1000:1 IRMS - 0.1 - % Voltage Channel Input Signal Dynamic Range 20:1 VRMS - 0.1 - % PF - 0.1 - % Voltage RMS (Note 1 and 3) Power Factor (Note 1 and 3) All Gain Ranges Current Channel Input Signal Dynamic Range 1000:1 Notes: 1. Specifications guaranteed by design and characterization. 2. Active energy is tested with power factor (PF) = 1.0. Reactive energy is tested with Sin() = 1.0. Energy error measured at system level using a single energy pulse. Where: 1) One energy pulse = 0.5Wh or 0.5Varh; 2) VDDA = +3.3V 5%, TA = 25C, MCLK = 4.096MHz; 3) System is calibrated. 3. Calculated using register values; N 4000. 4. IRMS error calculated using register values. 1) VDDA = +3.3V 5%; TA = 25C; MCLK = 4.096MHz; 2) AC offset calibration applied. TYPICAL LOAD PERFORMANCE * * * Energy error measured at system level using single energy pulse; where one energy pulse = 0.5Wh or 0.5Varh. IRMS error calculated using register values. VDDA = +3.3V 5%; TA = 25C; MCLK = 4.096MHz. 1 Percent Error (%) 0.5 0 Lagging PF = 0.5 Leading PF = 0.5 PF = 1 -0.5 -1 0 500 1000 1500 2000 2500 3000 3500 4000 4500 Current Dynamic Range (x : 1) Figure 4. Active Energy Load Performance DS893F1 9 CS5480 1 Percent Error (%) 0.5 0 Lagging sin() = 0.5 Leading sin() = 0.5 sin() = 1 -0.5 -1 0 500 1000 1500 2000 2500 3000 3500 4000 4500 Current Dynamic Range (x : 1) Figure 5. Reactive Energy Load Performance 1 Percent Error (%) 0.5 0 IRMS Error IRMS Error -0.5 -1 0 500 1000 1500 Current Dynamic range (x : 1) Figure 6. IRMS Load Performance 10 DS893F1 CS5480 ANALOG CHARACTERISTICS * * * * Min / Max characteristics and specifications are guaranteed over all Recommended Operating Conditions. Typical characteristics and specifications are measured at nominal supply voltages and TA = 25C. VDDA = +3.3V 5%; GNDA = GNDD = 0V. All voltages with respect to 0V. MCLK = 4.096MHz. Parameter Symbol Min Typ Max Unit CMRR 80 - - dB -0.25 - VDDA V Analog Inputs (Current Channels) Common Mode Rejection (DC, 50, 60Hz) Common Mode+Signal Differential Full-scale Input Range [(IIN+) - (IIN-)] (Gain = 10) (Gain = 50) IIN - 250 50 - mVP mVP Total Harmonic Distortion (Gain = 50) THD 90 100 - dB Signal-to-Noise Ratio (SNR) (Gain = 10) SNR - 80 80 - dB dB - -115 - dB (Gain = 50) Crosstalk from Voltage Inputs at Full Scale (50, 60Hz) Crosstalk from Current Input at Full Scale (50, 60Hz) - -115 - dB Input Capacitance IC - 27 - pF Effective Input Impedance EII 30 - - k Offset Drift (Without the High-pass Filter) OD - 4.0 - V/C - 15 3.5 - VRMS VRMS Noise (Referred to Input) (Gain = 10) (Gain = 50) NI Power Supply Rejection Ratio (60Hz) (Gain = 10) (Gain = 50) PSRR 60 68 65 75 - dB dB (DC, 50, 60Hz) CMRR 80 - - dB -0.25 - VDDA V [(VIN+) - (VIN-)] VIN - 250 - mVP Total Harmonic Distortion THD 80 88 - dB Signal-to-Noise Ratio (SNR) SNR - 73 - dB - -115 - dB IC - 2.0 - pF Effective Input Impedance EII 2 - - M Noise (Referred to Input) NV - 40 - VRMS OD - 16.0 - V/C 60 65 - dB - 5 - C (Note 7) Analog Inputs (Voltage Channels) Common Mode Rejection Common Mode+Signal Differential Full-scale Input Range Crosstalk from Current Inputs at Full Scale (50, 60Hz) Input Capacitance Offset Drift (Without the High-pass Filter) Power Supply Rejection Ratio (Note 7) (60Hz) (Gain = 10x) PSRR Temperature Temperature Accuracy DS893F1 (Note 6) T 11 CS5480 Parameter Symbol Min Typ Max Unit PSCA - 3.9 - mA PC - 12.9 4.5 - mW mW Power Supplies Power Supply Currents (Active State) IA+ (VDDA = +3.3V) Power Consumption (Note 5) Notes: Active State (VDDA = +3.3V) Stand-by State 5. 6. 7. All outputs unloaded. All inputs CMOS level. Temperature accuracy measured after calibration is performed. Measurement method for PSRR: VDDA = +3.3V, a 150mV (zero-to-peak) (60Hz) sine wave is imposed onto the +3.3V DC supply voltage at the VDDA pin. The "+" and "-" input pins of both input channels are shorted to GNDA. The CS5480 is then commanded to continuous conversion acquisition mode, and digital output data is collected for the channel under test. The (zero-to-peak) value of the digital sinusoidal output signal is determined, and this value is converted into the (zero-to-peak) value of the sinusoidal voltage (measured in mV) that would need to be applied at the channel's inputs in order to cause the same digital sinusoidal output. This voltage is then defined as Veq PSRR is (in dB): 150 PSRR = 20 log ----------V eq VOLTAGE REFERENCE Parameter Reference Symbol Min Typ Max Unit VREF +2.3 +2.4 +2.5 V (Note 9) TCVREF - 25 - ppm/C (Note 10) VR - 25 - mV (Note 8) Output Voltage Temperature Coefficient Load Regulation Notes: 8. It is strongly recommended that no connection other than the required filter capacitor be made to VREF. 9. The voltage at VREF is measured across the temperature range. From these measurements the following formula is used to calculate the VREF temperature coefficient: VREF MAX - VREFMIN 1 TC VREF = ------------------------------------------------------------ ---------------------------------------------- 1.0 10 6 T A MAX - TA MIN VREF AVG 10. 12 Specified at maximum recommended output of 1A sourcing. VREF is a sensitive signal; the output of the VREF circuit has a high output impedance so that the 0.1F reference capacitor provides attenuation even to low-frequency noise, such as 50Hz noise on the VREF output. Therefore VREF is intended for the CS5480 only and should not be connected to any external circuitry. The output impedance is sufficiently high that standard digital multimeters can significantly load this voltage. The accuracy of the metrology IC cannot be guaranteed when a multimeter or any component other than the 0.1F capacitor is attached to VREF. If it is desired to measure VREF for any reason other than a very course indicator of VREF functionality, Cirrus recommends a very high input impedance multimeter such as the Keithley Model 2000 Digital Multimeter be used. Cirrus cannot guarantee the accuracy of the metrology with this meter connected to VREF. DS893F1 CS5480 DIGITAL CHARACTERISTICS * * * * Min / Max characteristics and specifications are guaranteed over all Recommended Operating Conditions. Typical characteristics and specifications are measured at nominal supply voltages and TA = 25C. VDDA = +3.3V 5%; GNDA = GNDD = 0V. All voltages with respect to 0V. MCLK = 4.096MHz. Parameter Master Clock Characteristics XIN Clock Frequency XIN Clock Duty Cycle Filter Characteristics Phase Compensation Range Input Sampling Rate Digital Filter Output Word Rate High-pass Filter Corner Frequency Input/Output Characteristics High-level Input Voltage (All Pins) Internal Gate Oscillator Symbol Min Typ Max Unit MCLK 2.5 40 4.096 - 5 60 MHz % -10.79 - MCLK/8 MCLK/1024 2.0 +10.79 - Hz Hz Hz VIH 0.6(VDDA) - - V VIL - - 0.6 V 1 0.5 0.5 10 V V V V A (60Hz, OWR = 4000Hz) (Both channels) OWR -3dB Low-level Input Voltage (All Pins) Input Leakage Current Iin VDDA-0.3 VDDA-0.3 - 3-state Leakage Current IOZ - - 10 A Digital Output Pin Capacitance Cout - 5 - pF High-level Output Voltage (Note 12) Low-level Output Voltage (Note 12) Notes: DO1-DO3, Iout = +10mA All Other Outputs, Iout = +5mA VOH DO1-DO3, Iout = -12mA All Other Outputs, Iout = -5mA VOL 11. All measurements performed under static conditions. 12. XOUT pin used for crystal only. Typical drive current<1mA. DS893F1 13 CS5480 SWITCHING CHARACTERISTICS * * * * Min / Max characteristics and specifications are guaranteed over all Recommended Operating Conditions. Typical characteristics and specifications are measured at nominal supply voltages and TA = 25C. VDDA = +3.3V 5%; GNDA = GNDD = 0V. All voltages with respect to 0V. Logic Levels: Logic 0 = 0V, Logic 1 = VDDA. Parameter Symbol Min Typ Max Unit DO1-DO3 Any Digital Output Except DO1-DO3 trise - 50 1.0 - s ns DO1-DO3 Any Digital Output Except DO1-DO3 tfall - 50 1.0 - s ns XTAL = 4.096 MHz (Note 14) tost - 60 - ms SCLK - - 2 MHz t1 t2 200 200 - - ns ns CS Enable to SCLK Falling t3 50 - - ns Data Set-up Time prior to SCLK Rising t4 50 - - ns Data Hold Time After SCLK Rising t5 100 - - ns SCLK Rising Prior to CS Disable t6 500 - - ns SCLK Falling to New Data Bit t7 - - 150 ns CS Rising to SDO Hi-Z t8 - - 250 ns CS Enable to RX START bit t9 5 - - ns STOP bit to CS Disable t10 500 - - ns CS Disable to TX IDLE Hold Time t11 - - 250 ns Rise Times (Note 13) Fall Times (Note 13) Start-up Oscillator Start-up Time SPI Timing Serial Clock Frequency Serial Clock (Note 15) Pulse Width High Pulse Width Low UART Timing Notes: 14 13. Specified using 10% and 90% points on waveform of interest. Output loaded with 50pF. 14. Oscillator start-up time varies with crystal parameters. This specification does not apply when using an external clock source. 15. The maximum SCLK is 2 MHz during a byte transaction. The minimum 1s idle time is required on the SCLK between two consecutive bytes. DS893F1 CS5480 CS t6 t1 t3 SCLK t2 t7 SDO MSB t4 SDI t8 MSB-1 LSB INTERMEDIATE BITS t5 MSB MSB-1 INTERMEDIATE BITS LSB Figure 7. SPI Data and Clock Timing CS t10 t9 TX RX START IDLE START LSB DATA MSB STOP IDLE LSB DATA MSB OPTIONAL OVERLAP INSTRUCTION * t11 IDLE STOP STOP * Reading registers during the optional overlap instruction requires the start to occur during the last byte transmitted by the part Figure 8. Multi-device UART Timing DS893F1 15 CS5480 ABSOLUTE MAXIMUM RATINGS Parameter DC Power Supplies Input Current (Note 16) (Notes 17 and 18) Input Current for Power Supplies Symbol Min Typ Max Unit VDDA -0.3 - +4.0 V IIN - - 10 mA - - - 50 - Output Current (Note 19) IOUT - - 100 mA Power Dissipation (Note 20) PD - - 500 mW Input Voltage (Note 21) VIN - 0.3 - (VDDA) + 0.3 V 2 Layer Board 4 Layer Board JA - 55 46 - C/W C/W Ambient Operating Temperature TA - 40 - 85 C Storage Temperature Tstg - 65 - 150 C Junction-to-Ambient Thermal Impedance Notes: 16. VDDA and GNDA must satisfy [(VDDA) - (GNDA)] + 4.0V. 17. Applies to all pins, including continuous overvoltage conditions at the analog input pins. 18. Transient current of up to 100mA will not cause SCR latch-up. 19. Applies to all pins, except VREF. 20. Total power dissipation, including all input currents and output currents. 21. Applies to all pins. WARNING: Operation at or beyond these limits may result in permanent damage to the device. Normal operation is not guaranteed at these extremes. 16 DS893F1 CS5480 VIN x10 MUX To V2 Digital Path 4th Order Modulator PMF DELAY CTRL IIR SINC3 V1 HPF Phase Shift V1DCOFF ... CPCC1[1:0] ... FPCC1[8:0] ... SYSGAIN Config 2 I1 DCOFF IIN1 4th Order Modulator PGA DELAY CTRL Epsilon ... ... 2 P1 I1 GAIN IIR SINC3 V1FLT[1:0] I1FLT[1:0] HPF INT MUX PC V1GAIN Q1 PMF I1 Registers Figure 9. Signal Flow for V1, I1, P1, Q1 Measurements 4. SIGNAL FLOW DESCRIPTION The signal flow consists of two current channels and a voltage channel. Even though the CS5480 has only one voltage channel or voltage analog signal input, there are two separate voltage digital signal paths (V1 and V2). Both V1 and V2 come from the same ADC output. Each current and voltage channel has its own differential input pin. 4.1 Analog-to-Digital Converters All three input channels use fourth-order delta-sigma modulators to convert the analog inputs to single-bit digital data streams. The converters sample at a rate of MCLK/8. This high sampling provides a wide dynamic range and simplifies anti-alias filter design. 4.2 Decimation Filters The single-bit modulator output data is widened to 24 bits and down sampled to MCLK/1024 with low-pass decimation filters. These decimation filters are third-order Sinc filters. The outputs of the filters are passed through an IIR "anti-sinc" filter. 4.3 IIR Filters The IIR filters are used to compensate for the amplitude roll-off of the decimation filters. The droop-correction filter flattens the magnitude response of the channel out to the Nyquist frequency, thus allowing for accurate measurements of up to 2kHz (MCLK = 4.096MHz). By default, the IIR filters are enabled. The IIR filters can be bypassed by setting the IIR_OFF bit in the Config2 register. MUX The signal flow for voltage measurement, current measurement, and the other calculations is shown in Figures 9, 10, and 11. PMF DELAY CTRL From V Channel ADC IIR SINC3 V2 HPF Phase Shift PC ... CPCC2[1:0] ... FPCC2[8:0] ... SYSGAIN Config 2 I2 DCOFF IIN2 PGA 4th Order Modulator DELAY CTRL SINC3 V2GAIN IIR Epsilon ... V2FLT[1:0] I2FLT[1:0] ... 2 P2 I2 GAIN HPF INT PMF MUX V2DCOFF Q2 I2 Registers Figure 10. Signal Flow for V2, I2, P2, and Q2 Measurements DS893F1 17 CS5480 4.4 Phase Compensation Phase compensation changes the phase of voltage relative to current by adding a delay in the decimation filters. The amount of phase shift is set by the PC register bits CPCCx[1:0] and FPCCx[8:0] for current channels. For voltage channels, only bits CPCCx[1:0] affect the delay. Fine phase compensation control bits, FPCCx[8:0], provide up to 1/OWR delay in the current channels. Coarse phase compensation control bits, CPCCx[1:0], provide an additional 1/OWR delay in the current channel or up to 2/OWR delay in the voltage channel. Negative delay in voltage channel can be implemented by setting a longer delay in the current channel than the voltage channel. For a OWR of 4000Hz, the delay range is 500s, a phase shift of 8.99 at 50Hz and 10.79 at 60Hz. The step size is 0.008789 at 50Hz and 0.010547 at 60Hz. 4.5 DC Offset and Gain Correction The system and CS5480 inherently have component tolerances and gain and offset errors, which can be removed using the gain and offset registers. Each measurement channel has its own set of gain and offset registers. For every instantaneous voltage and current sample, the offset and gain values are used to correct DC offset and gain errors in the channel (see section 7. System Calibration on page 62 for more details). 4.6 High-pass and Phase Matching Filters Optional high-pass filters (HPF in Figures 9 and 10) remove any DC component from the selected signal paths. Each power calculation contains a current and voltage channel. If an HPF is enabled in only one N V1(V2) /N channel, a phase matching filter (PMF) should be applied to the other channel to match the phase response of the HPF. For AC power measurement, high-pass filters should be enabled on the voltage and current channels. For information about how to enable and disable the HPF or PMF on each channel, refer to section 6.6.3 Configuration 2 (Config2) - Page 16, Address 0 on page 38. 4.7 Digital Integrators Optional digital integrators (INT in Figures 9 and 10) are implemented on both current channels (I1, I2) to compensate for the 90 phase shift and 20dB/decade gain generated by the Rogowski coil current sensor. When a Rogowski coil is used as the current sensor, the integrator (INT) should be enabled on that current channel. For information about how to enable and disable the INT on each current channel, refer to section 6.6.3 Configuration 2 (Config2) - Page 16, Address 0 on page 38. 4.8 Low-rate Calculations All the RMS and power results come from low-rate calculations by averaging the output word rate (OWR) instantaneous values over N samples, where N is the value stored in the SampleCount register. The low-rate interval or averaging period is N divided by OWR (4000Hz if MCLK = 4.096MHz). N is the preset value in the SampleCount register and should not be set less than 100. By default, the SampleCount is 4000. With MCLK = 4.096MHz, the averaging period is fixed at N/4000 = 1 second, regardless of the line frequency. V1RMS (V2RMS) Config 2 ... APCM ... I1 ACOFF (I2ACOFF ) /N + - I1RMS (I2RMS) MUX N I1 (I2) Q1 OFF (Q2OFF ) N Q1 (Q2) /N + + Q1AVG (Q2AVG) X P1OFF (P2OFF ) N P1 (P2) S1 (S2) /N + + Inverse P1AVG (P2AVG) X Registers + + X PF1 (PF2) Figure 11. Low-rate Calculations 18 DS893F1 CS5480 4.8.1 RMS Current and Voltage The root mean square (RMS in Figure 11) calculations are performed on N instantaneous current and voltage samples using Equation 1: N-1 I RMS = I2 n n=0 -------------------N N-1 V RMS = V2 n n=0 ---------------------N Eq. 1 the corresponding channel peak register documented in the register map. This peak value is updated every N samples. 4.8.6 Power Factor Power factor (PF1, PF2) is active power divided by apparent power as shown in Equation 4. The sign of the power factor is determined by the active power. P ACTIVE PF = ---------------------S 4.8.2 Active Power The instantaneous voltage and current samples are multiplied to obtain the instantaneous power (P1, P2) (see Figures 9 and 11). The product is then averaged over N samples to compute active power (P1AVG, P2AVG). 4.8.3 Reactive Power Instantaneous reactive power (Q1, Q2) are sample rate results obtained by multiplying instantaneous current (I1, I2) by instantaneous quadrature voltage (V1Q, V2Q), which are created by phase shifting the instantaneous voltage (V1, V2) 90 degrees using first-order integrators (see Figures 9 and 11). The gain of these integrators is inversely related to line frequency, so their gain is corrected by the Epsilon register, which is based on line frequency. Reactive power (Q1AVG, Q2AVG) is generated by integrating the instantaneous quadrature power over N samples. Eq. 4 4.9 Average Active Power Offset The average active power offset registers, P1OFF (P2OFF), can be used to offset erroneous power sources resident in the system not originating from the power line. Residual power offsets are usually caused by crosstalk into current channels from voltage channels, or from ripple on the meter's or chip's power supply, or from inductance from a nearby transformer. These offsets can be either positive or negative, indicating crosstalk coupling either in phase or out of phase with the applied voltage input. The power offset registers can compensate for either condition. To use this feature, measure the average power at no load. Take the measured result (from the P1AVG (P2AVG) register), invert (negate) the value, and write it to the associated average active power offset register, P1OFF (P2OFF). 4.8.4 Apparent Power 4.10 Average Reactive Power Offset By default, the CS5480 calculates the apparent power (S1, S2) as the product of RMS voltage and current as shown in Equation 2: The average reactive power offset registers, Q1OFF (Q2OFF), can be used to offset erroneous power sources resident in the system not originating from the power line. Residual reactive power offsets are usually caused by crosstalk into current channels from voltage channels, or from ripple on the meter's or chip's power supply, or from inductance from a nearby transformer. S = V RMS I RMS Eq. 2 The CS5480 also provides an alternate apparent power calculation method, which uses real power (P1AVG, P2AVG) and reactive power (Q1AVG, Q2AVG) to calculate apparent power, as shown in Equation 3: S = Q AVG 2 + P AVG 2 Eq. 3 The APCM bit in the Config2 register controls which method is used for apparent power calculation. 4.8.5 Peak Voltage and Current Peak current (I1PEAK, I2PEAK ) and peak voltage (VPEAK ) are calculated over N samples and recorded in DS893F1 These offsets can be either positive or negative, depending on the phase angle between the crosstalk coupling and the applied voltage. The reactive power offset registers can compensate for either condition. To use this feature, measure the average reactive power at no load. Take the measured result from the Q1AVG (Q2AVG) register, invert (negate) the value and write it to the associated reactive power offset register, Q1OFF (Q2OFF). 19 CS5480 5. FUNCTIONAL DESCRIPTION 5.1 Power-on Reset Table 1. POR Thresholds The CS5480 has an internal power supply supervisor circuit that monitors the VDDA and VDDD power supplies and provides the master reset to the chip. If any of these voltages are in the reset range, the master reset is triggered. The CS5480 has dedicated power-on reset (POR) circuits for the analog supply and digital supply. During power-up, both supplies have to be above the rising threshold for the master reset to be de-asserted. Each POR is divided into two blocks: rough and fine. Rough POR triggers the fine POR. Rough POR depends only on the supply voltage. The trip point for the fine POR is dependent on bandgap voltage for precise control. The POR circuit also acts as a brownout detect. The fine POR detects supply drops and asserts the master reset. The rough and fine PORs have hysteresis in their rise and fall thresholds, which prevents the reset signal from chattering. Figure 9 shows the POR outputs for each of the power supplies. The POR_Fine_VDDA and POR_Fine_VDDD signals are AND-ed to form the actual power-on reset signal to the digital circuity. The digital circuitry, in turn, holds the master reset signal for 130ms and then de-asserts the master reset. VDDA Vth5 Vth2 Vth1 Vth6 POR_Rough_VDDA POR_Fine_VDDA Vth4 VDDD Vth7 Vth8 Vth3 Typical POR Threshold VDDA VDDD Rising Falling Rough Vth1 = 2.34V Vth6 = 2.06V Fine Vth2 = 2.77V Vth5 = 2.59V Rough Vth3 = 1.20V Vth8 = 1.06V Fine Vth4 = 1.51V Vth7 = 1.42V 5.2 Power Saving Modes Power Saving modes for the CS5480 are accessed through the Host Commands (see section 6.1 Host Commands on page 27). * Standby: Powers down all the ADCs, rough buffer, and the temperature sensor. Standby mode disables the system time calculations. Use the wake-up command to come out of standby mode. * Wake-up: Clears the ADC power-down bits and starts the system time calculations. After any of these commands are completed, the DRDY bit is set in the Status0 register. 5.3 Zero-crossing Detection Zero-crossing detection logic is implemented in CS5480. One current and one voltage channel can be selected for zero-crossing detection. The IZX_CH control bits in the Config0 register are used to select the zero-crossing channel. A low-pass filter can be enabled by setting ZX_LPF bit in register Config2. The low-pass filter has a cut-off frequency of 80Hz. It is used to eliminate any harmonics and help the zero-crossing detection on the 50Hz or 60Hz fundamental component. The zero-crossing level (ZXLevel) register is used to set the minimum threshold over which the channel peak has to exceed in order for the zero-crossing detection logic to function. 5.4 Line Frequency Measurement POR_Rough_VDDD POR_Fine_VDDD POR_Fine_VDDA POR_Fine_VDDD Master Reset 130ms Figure 12. Power-on Reset Timing 20 If the Automatic Frequency Calculation bit (AFC) in the Config2 register is set, the line frequency calculation on voltage channel 1 will be enabled. The Epsilon register will be updated automatically with the line frequency information. The Frequency Update (FUP) bit in the Status0 interrupt status register is set when the frequency calculation is completed. When the line frequency is 60Hz, the frequency is updated approximately every 8 seconds with a resolution of 0.1%. The Epsilon register is also used to set the gain of the 90 phase shift filter used in the quadrature power DS893F1 CS5480 Table 2. Meter Configuration Modes calculation. The value in the Epsilon register is the ratio of the line frequency to the output word rate (OWR). For 50Hz line frequency and 4000Hz OWR, Epsilon is 50/4000 (0.0125) (the default). For 60Hz line frequency, it is 60/4000 (0.015). Meter Mode MCFG [1:0] Total Power Calculations 2 5.5 Meter Configuration Modes 1V-2I There are two distinct meter configuration modes in the CS5480 that affect how the total active, reactive, and apparent power calculations are performed. The CS5480 has power results for each current channel as well as total power registers (PSUM, QSUM, and SSUM). The total power register is calculated from either one or both channels, depending on the meter configuration modes. See Table 2 for power calculations in each mode. N /N 2 , 2 The Meter Configuration (MCFG) bits in the configuration (Config2) register set the meter configuration modes. For each meter mode, the current channels are interpreted differently. In the one voltage and two line currents (1V - 2I) mode, the CS5480 treats the two currents as individual contributors to the overall power. In the one voltage, one line current, and one neutral current (1V - 1I - 1N) mode, the currents are treated as duplicate copies of the same load current, and the total power is calculated from the highest current or the one the customer has specified. The MCFG multiplexers in Figure 13 show the data path for both modes. P1 01 , 1V-1I-1N (I1RMS > I2RMS)* (P1AVG > P2AVG)* 00 (Default) 1V-1I-1N (I1RMS < I2RMS)* (P1AVG < P2AVG)* 00 (Default) 0 P1AVG 1 I1RMS 0 VFRMS 1 I2RMS /2 P2AVG P2 /N Q1 /N N PSUM 00 1 N 01 0 VFIX (Config2) Q1AVG 0 1 /2 01 Q SUM 00 Q2 N /N Q2AVG S1 0 1 /2 01 SSUM 00 ICHAN (IHOLD = 1) S2 MCFG[1:0] (Config2) Figure 13. Channel Selection and Tamper Protection Flow DS893F1 21 CS5480 5.6 Tamper Detection and Correction 5.6.1.1 Automatic Channel Selection In the 1V-1I-1N meter configuration mode, the CS5480 provides flexibility for the user and application program to adjust the anti-tampering scheme automatically or manually. Automatic channel selection is enabled by default. For manual channel selection refer to section 5.6.1.2 Manual Channel Selection on page 23. Automatic channel selection is standard in the CS5480. When tampering is detected, the CS5480 will automatically select the channel with the greater PxAVG or IxRMS magnitude as the contributor to the total power registers. Using either PxAVG or IxRMS magnitude depends on the setting of the IVSP bit in the Config2 register. The CS5480 provides compensation for at least two forms of meter tampering -- current and voltage tampering. To avoid repeated channel transitions at light load, the Channel Select Minimum Amplitude (PMIN (IRMSMIN)) register sets a minimum level for automatic channel selection. When either P1AVG (I1RMS) or P2AVG (I2RMS) is greater than PMIN (IRMSMIN), the CS5480 will enable automatic channel selection. Within the automatic selection region, the Channel Select Level (IchanLEVEL) register sets a minimum difference that will allow an automatic channel change. The channel select level provides hysteresis to prevent repeated channel transitions that would occur when the primary line current and neutral current are nearly equal. 5.6.1 Anti-tampering on Current In the 1V-1I-1N mode, current tampering is deterred by an automatic or manual channel selection scheme. A dedicated second neutral current input is provided in the event that the primary current input is impaired by tampering. 1 2 Channel 1 - Active 3 Channel 1 - Remains Active Channel 2 - Active P1AVG Channel Select Level (Ichan LEVEL) 2% minimum difference P2AVG Channel Select Level (Ichan LEVEL) 2% minimum difference Automatic Channel Selection Region Disabled Automatic Channel Selection Region Channel Select Minimum Amplitude PMIN (IRMSMIN) Figure 14. Automatic Channel Selection Figure 14 shows how the automatic channel selection is performed. In this figure, the magnitudes of P1AVG and P2AVG are used for automatic channel selection (IVSP = 0) and IchanLEVEL = 1.02. * 22 The P1AVG and P2AVG must meet the Channel Select Minimum Amplitude (IchanLEVEL). The highest channel is active, P1AVG in this example. * * Even when the active channel (P1AVG) moves below the previously lower channel (P2AVG), the channel selection does not change. The new channel selection is only made when the difference between P1AVG and P2AVG is greater than 2% x P1AVG or P2AVG > P1AVG x IchanLEVEL (1.02). DS893F1 CS5480 5.6.1.2 Manual Channel Selection In addition to automatic channel selection anti-tampering scheme, the CS5480 allows the user or application program to select the more appropriate energy channel manually. Configuration 2 (Config2) register bit IHOLD disable automatic channel selection, and ICHAN forces the selection of the contributor to the total power registers (see Figure 13). 5.6.2 Anti-tampering on Voltage An internal RMS voltage reference is also available in the event that the voltage input has been compromised by tampering. If the user application detects the voltage input has been impaired, it may choose to use the fixed internal RMS voltage reference in active power calculations by setting the VFIX bit in the Configuration 2 (Config2) reg- ister. The value of the Voltage Fixed RMS Reference (VFRMS) register is by default 0.707107 (full-scale RMS) but can be changed by the application program. Figure 13 shows the entry point for the VFRMS value. VFRMS has no phase relationship to I1RMS or I2RMS. Therefore, the VFRMS only affects the active power calculation paths. 5.7 Energy Pulse Generation The CS5480 provides three independent energy pulse generation blocks (EPG1, EPG2, and EPG3) in order to simultaneously output active, reactive, and apparent energy pulses on any of the three digital output pins (DO1, DO2, and DO3). The energy pulse frequency is proportional to the magnitude of the power. The energy pulse output is commonly used as the test output of a power meter. The host microcontroller can also use the energy pulses to accumulate the energy (see Figure 15). EPGx_ON (Config1) MCLK P1 AVG 0000 0000 P2 AVG 0001 0001 PSUM 0010 S1 AVG 0110 S2 AVG 0111 SSUM 1000 PULSE RATE P1 Sign 0100 P2 Sign 0101 PSUM Sign 0110 Q1 Sign 0111 Q2 Sign 1000 QSUM Sign 1001 RESERVED 1010 V1/V2 Crossing 1011 I1/I2 Crossing 1100 RESERVED 1101 1110 Hi-Z Interrupt (PulseCtrl) EPGxIN[3:0] 4 (PulseWidth) FREQ_RNG[3:0] 4 (PulseWidth) PW[7:0] 8 DOxMODE[3:0] (Config1) DO1 DO2_OD (Config1) Digital Output Mux (DO3) 0101 0011 Digital Output Mux (DO2) Q SUM RESERVED Digital Output Mux (DO1) 0100 Energy Pulse Generation (EPG3) Q2AVG Energy Pulse Generation (EPG2) 0011 0010 Energy Pulse Generation (EPG1) Q1AVG DO1_OD (Config1) DO2 DO3_OD (Config1) DO3 1111 4 Figure 15. Energy Pulse Generation and Digital Output Control DS893F1 23 CS5480 After reset, all three energy pulse generation blocks are disabled (DOxMODE[3:0] = Hi-Z). To output a desired energy pulse to a DOx pin, it is necessary to: * * * * Configure the pulse rate and width according to the meter constant. (Optional) Configure the output as open-drain or normal by setting or clearing appropriate DOx_OD bit(s) in the Config1 register. Select the input to the EPGx block by EPGxIN[3:0] in PulseCtrl register. Enable the EPGx block by setting the corresponding EPGx_ON bit and configure the DOx pin to output the EPGx result by setting appropriate DOxMODE[3:0] bits in the Config1 register. 5.7.1 Pulse Rate Before configuring the PulseRate register, the full-scale pulse rate needs to be calculated and the frequency range needs to be specified through FREQ_RNG[3:0] bits in the PulseWidth register. Refer to section 6.6.6 Pulse Output Width (PulseWidth) - Page 0, Address 8 on page 41. The FREQ_RNG[3:0] bits should be set to b[0110]. For example, if a meter has the meter constant of 1000imp/ kWh, a maximum voltage (UMAX) of 240V, and a maximum current (IMAX) of 100A, the maximum pulse rate is: [1000x(240x100/1000)] / 3600 = 6.6667Hz. Assume the meter is calibrated with UMAX and IMAX, and the Scale register contains the default value of 0.6. After gain calibration, the power register value will be 0.36, which represents 240x100 = 24kW or 6.6667Hz pulse output rate. The full-scale pulse rate is: Fout = 6.6667/0.36 = 18.5185Hz. By default, the PulseWidth register value is 1, and the Active-low time of each energy pulse is 265.6s. Note that the pulse width should never exceed the pulse period. 5.8 Voltage Sag, Voltage Swell, and Overcurrent Detection Voltage sag detection is used to determine when the voltage falls below a predetermined level for a specified interval of time (duration). Voltage swell and overcurrent detection determines when the voltage or current rises above a predetermined level for a specified interval of time. The duration is set by the value in the V1SagDUR (V2SagDUR), V1SwellDUR (V2Swell DUR), and I1OverDUR (I2OverDUR) registers. Setting any of these to zero (default) disables the detect feature for the given channel. The value is in output word rate (OWR) samples. The predetermined level is set by the values in the V1Sag LEVEL (V2Sag LEVEL), V1SwellLEVEL (V2SwellLEVEL), and I1OverLEVEL (I2Over LEVEL) registers. For each enabled input channel, the measured value is rectified and compared to the associated level register. Over the duration window, the number of samples above and below the level are counted. If the number of samples below the level exceeds the number of samples above, a Status0 register bit V1SAG (V2SAG) is set, indicating a sag condition. If the number of samples above the level exceeds the number of samples below, a Status0 register bit V1SWELL (V2SWELL) or I1OVER (I2OVER) is set, indicating a swell or overcurrent condition (see Figure 16). The CS5480 pulse generation block behaves as follows: * The pulse rate generated by full-scale (1.0decimal) power register: FOUT = (PulseRatex2000)/2FREQ_RNG * The PulseRate register value is: PulseRate = (FOUT x2FREQ_RNG)/2000 = (18.5186x64)/2000 L e ve l = 0.5925952 = 0x4BDA29 5.7.2 Pulse Width The PulseWidth register defines the Active-low time of each energy pulse: D u ra tio n Figure 16. Sag, Swell, and Overcurrent Detect Active-low = 250s+(PulseWidth/64000). 24 DS893F1 CS5480 A C B Figure 17. Phase Sequence A, B, C for Rising Edge Transition 5.9 Phase Sequence Detection Three phase meters using multiple CS5480 devices may be configured to sense the succession of voltage zero-crossings and determine which phase order is in service. The phase sequence detection within CS5480 involves counting the number of OWR samples from a starting command to the next voltage zero-crossing rising edge or falling for each phase. By comparing the count for each phase, the phase sequence can be easily determined: the smallest count is first, and the largest count is last. The phase sequence detection and control (PSDC) register provides the start command, zero-crossing direction and count results. Three CS5480 devices (one for each phase) must receive the start command at the same time so that all three devices begin simultaneously. The sequence detection is initiated by writing CODE = `10110' to PSDC[4:0] register bits, and by setting the direction bit DIR in PSDC[5]. This DIR bit defaults to '0' when negative-to-positive zero-cross detection is desired, or set to '1' when positive-to-negative zero-cross detection is desired. After the counting has started the devices will stop counting at the next specified zero-cross detection. The DONE bit of the PSDC register will be set, and the count result for each phase is stored in PSCNT [6:0] of the PSDC register. In order to give the CS5480 adequate time to complete phase sequence detection, a complete line-cycle (20ms for 50Hz) should pass before reading the PSCNT [6:0]. Figure 17 shows A, B, C phase sequence for the default rising edge transition, and Figure 18 shows C, B, A phase sequence for rising edge transition. C A B Figure 18. Phase Sequence C, B, A for Rising Edge Transition DS893F1 25 CS5480 5.10 Temperature Measurement 5.12.1 Write Protection The CS5480 has an internal temperature sensor, which is designed to measure temperature and optionally compensate for temperature drift of the voltage reference. Temperature measurements are stored in the Temperature register (T), which, by default, is configured to a range of 128 degrees on the Celsius (C) scale. Setting the DSP_Lock[4:0] bits in the RegLock register to 0x16 enables the CS5480 DSP lockable registers to be write-protected from the calculation engine. Setting the DSP_Lock[4:0] bits to 0x09 disables the write-protection mode. The application program can change both the scale and range of Temperature (T) by changing the Temperature Gain (TGAIN) and Temperature Offset (TOFF) registers. To enable temperature measurements: * Set Config0 register bit 23, bit 22, and bit 13. * Configure TGAIN register as 0x6B716. * Configure TOFF register as 0xD53998. The temperature register (T) updates every 2240 output word rate (OWR) samples. The Status0 register bit TUP indicates when T is updated. 5.11 Anti-Creep The anti-creep (no-load threshold) is used to determine if a no-load condition is detected. The |PSum| and |QSum| are compared to the value in the No Load Threshold register (LoadMin). If both |PSum| and |QSum| are less than this threshold, then PSum and QSum are forced to zero. If SSum is less than the value in LoadMin register, then SSum is forced to zero. 5.12 Register Protection To prevent the critical configuration and calibration registers from unintended changes, the CS5480 provides two enhanced register protection mechanisms: write protection and automatic checksum calculation. 26 Setting the HOST_Lock[4:0] bits in the RegLock register to 0x16 enables the CS5480 HOST lockable registers to be write-protected from the serial interface. Setting the HOST_Lock[4:0] bits to 0x09 disables the write-protection mode. For registers that are DSP lockable, HOST lockable, or both, refer to sections 6.2 Hardware Registers Summary (Page 0) on page 29, 6.3 Software Registers Summary (Page 16) on page 31, and 6.4 Software Registers Summary (Page 17) on page 33. 5.12.2 Register Checksum All the configuration and calibration registers are protected by checksum, if enabled. Refer to 6.2 Hardware Registers Summary (Page 0) on page 29, 6.3 Software Registers Summary (Page 16) on page 31, and 6.4 Software Registers Summary (Page 17) on page 33. The checksum for all registers marked with an asterisk symbol ( *) is computed at the rate of OWR. The checksum result is stored in the RegChk register. After the CS5480 has been fully configured and loaded with the calibrations, the host microcontroller should keep a copy of the checksum (RegChk_Copy) in its memory. In normal operation, the host microcontroller can read the RegChk register and compare it with the saved copy of the RegChk register. If the two values mismatch, a reload of configurations and calibrations into the CS5480 is necessary. The automatic checksum computation can be disabled by setting the REG_CSUM_OFF bit in the Config2 register. DS893F1 CS5480 6. HOST COMMANDS AND REGISTERS 6.1 Host Commands The first byte sent to the CS5480 SDI/RX pin contains the host command. Four types of host commands are required to read and write registers and instruct the calculation engine. The two most significant bits (MSBs) of the host command defines the function to be performed. The following table depicts the types of commands. A register write command is designated by setting the two MSBs of the command to binary `01'. The lower 6 bits of the register write command are the lower 6 bits of the 12-bit register address. A register write command must be followed by 3 bytes of data. SDI/RX Table 3. Command Format Function Binary Value Register Read 0 0 A5 A4 A3 A2 A1 A0 Register Write 0 1 A5 A4 A3 A2 A1 A0 Page Select 1 0 P5 P4 P3 P2 P1 P0 P[5:0] specifies the page. Instruction 1 1 C5 C4 C3 C2 C1 C0 C[5:0] specifies the instruction. Note A[5:0] specifies the register address. 6.1.1 Memory Access Commands 6.1.1.1 Page Select A page select command is designated by setting the two MSBs of the command to binary `10'. The page select command provides the CS5480 with the page number of the register to access. Register read and write commands access 1 of 64 registers within a specified page. Subsequent register reads and writes can be performed once the page has been selected. Page Select Cmd. An instruction command is designated by setting the two MSBs of the command to binary '11'. An Instruction command will interrupt any process currently running and initiate a new process in the CS5480. SDI/RX A register read is designated by setting the two MSBs of the command to binary `00'. The lower 6 bits of the register read command are the lower 6 bits of the 12-bit register address. After the register read command has been received, the CS5480 will send 3 bytes of register data onto the SDO/TX pin. Read Cmd. DATA DATA Figure 20. Byte Sequence for Register Read DS893F1 Instruction These new processes include calibration, power control, and soft reset. The following table depicts the types of instructions. Note that when the CS5480 is in continuous conversion mode, an unexpected or invalid instruction command could cause the device to stop continuous conversion and enter an unexpected operation mode. The host processor should keep monitoring the CS5480 operation status and react accordingly. Table 4. Instruction Format Function Binary Value 0 C4 C3 C2 C1 C0 Controls DATA DATA 6.1.2 Instructions 6.1.1.2 Register Read SDO/TX DATA Figure 21. Byte Sequence for Register Write Figure 19. Byte Sequence for Page Select SDI/RX DATA Write Cmd. Figure 22. Byte Sequence for Instructions The CS5480 memory has 12-bit addresses and is organized as P5 P4 P3 P2 P1 P0 A5 A4 A3 A2 A1 A0 in 64 pages of 64 addresses each. The higher 6 bits specify the page number. The lower 6 bits specify the address within the selected page. SDI/RX 6.1.1.3 Register Write 0 00001 - Software Reset 0 00010 - Standby 0 00011 - Wakeup 0 10100 - Single Conv. 0 10101 - Continuous Conv. 0 11000 - Halt Conv. 1 C4 C3 C2 C1 C0 1 00C2C1C0 DC Offset 1 10C2C1C0 AC Offset* 1 11C2C1C0 Gain Calibrations 1 C4 C3 C2 C1 C0 1 C4C3 1 C4C3 1 C4C3 1 C4C3 1 C4C3 001 010 011 100 110 I1 V1 I2 V2 All Four Note C [5] specifies the instruction type: 0 = Controls 1 = Calibrations For calibrations, C[4:3] specifies the type of calibration. *AC Offset calibration valid only for current channel For calibrations, C [2:0] specifies the channel(s). 27 CS5480 6.1.3 Checksum To improve the communication reliability on the serial interface, the CS5480 provides a checksum mechanism on transmitted and received signals. Checksum is disabled by default but can be enabled by setting the appropriate bit in the SerialCtrl register. When enabled, both host and CS5480 are expected to send one additional checksum byte after the normal command byte and the applicable 3-byte register data has been transmitted. SDI/RX The checksum is calculated by subtracting each transmit byte from 0xFF. Any overflow is truncated and the result wraps. The CS5480 executes the command only if the checksum transmitted by the host matches the checksum calculated locally. Otherwise, it sets a status bit (RX_CSUM_ERR in the Status0 register), ignores the command, and clears the serial interface in preparation for the next transmission. SDI/RX 28 Page Select Cmd. Checksum Page Select SDI/RX Instruction Checksum Instruction SDI/RX Read Cmd. CHECKSUM SDO/TX DATA DATA DATA CHECKSUM Read Command Write Cmd. DATA DATA DATA CHECKSUM Write Command Figure 23. Byte Sequence for Checksum 6.1.4 Serial Time Out In case a transaction from the host is not completed (for example, a data byte is missing in a register write), a time out circuit will reset the interface after 128ms. This will require that each byte be sent from the host within 128ms of the previous byte. DS893F1 CS5480 6.2 Hardware Registers Summary (Page 0) Address2 0* 1* 2 3* 4 5* 6 7* 8* 9* 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 25 26 27 28 29 30 31 32 33 34* 35 36 37 38 39 40 41 42 43 44 45 46 47 48 49 50 DS893F1 RA[5:0] 00 0000 00 0001 00 0010 00 0011 00 0100 00 0101 00 0110 00 0111 00 1000 00 1001 00 1010 00 1011 00 1100 00 1101 00 1110 00 1111 01 0000 01 0001 01 0010 01 0011 01 0100 01 0101 01 0110 01 0111 01 1000 01 1001 01 1010 01 1011 01 1100 01 1101 01 1110 01 1111 10 0000 10 0001 10 0010 10 0011 10 0100 10 0101 10 0110 10 0111 10 1000 10 1001 10 1010 10 1011 10 1100 10 1101 10 1110 10 1111 11 0000 11 0001 11 0010 Name Config0 Config1 Mask PC SerialCtrl PulseWidth PulseCtrl Status0 Status1 Status2 RegLock V1PEAK I1PEAK V2PEAK I2PEAK PSDC - Description1 Configuration 0 Configuration 1 Reserved Interrupt Mask Reserved Phase Compensation Control Reserved UART Control Energy Pulse Width Energy Pulse Control Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Interrupt Status Chip Status 0 Chip Status 1 Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Register Lock Control Reserved V1 Peak Voltage I1 Peak Current V2 Peak Voltage I2 Peak Current Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Phase Sequence Detection & Control Reserved Reserved DSP3 Y Y Y Y Y Y Y N N N N N N N N N HOST 3 Default Y 0x 80 2000 Y 0x 00 EEEE Y 0x 00 0000 Y 0x 00 0000 Y 0x 02 004D Y 0x 00 0001 Y 0x 00 0000 N 0x 80 0000 N 0x 80 1800 N 0x 00 0000 N 0x 00 0000 Y 0x 00 0000 Y 0x 00 0000 Y 0x 00 0000 Y 0x 00 0000 Y 0x 00 0000 29 CS5480 51 52 53 54 55 56 57 58 59 60 61 62 63 Notes: 30 11 0011 11 0100 11 0101 11 0110 11 0111 11 1000 11 1001 11 1010 11 1011 11 1100 11 1101 11 1110 11 1111 - Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved - (1) Warning: Do not write to unpublished or reserved register locations. (2) * Registers with checksum protection. (3) Registers that can be set to write protect from DSP and/or HOST. DS893F1 CS5480 6.3 Software Registers Summary (Page 16) Address2 0* 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 25 26 27 28 29 30 31 32* 33* 34* 35* 36* 37* 38* 39* 40* 41* 42* 43* 44* 45* 46 47 48 49 50 51* 52 DS893F1 RA[5:0] 00 0000 00 0001 00 0010 00 0011 00 0100 00 0101 00 0110 00 0111 00 1000 00 1001 00 1010 00 1011 00 1100 00 1101 00 1110 00 1111 01 0000 01 0001 01 0010 01 0011 01 0100 01 0101 01 0110 01 0111 01 1000 01 1001 01 1010 01 1011 01 1100 01 1101 01 1110 01 1111 10 0000 10 0001 10 0010 10 0011 10 0100 10 0101 10 0110 10 0111 10 1000 10 1001 10 1010 10 1011 10 1100 10 1101 10 1110 10 1111 11 0000 11 0001 11 0010 11 0011 11 0100 Name Config2 RegChk I1 V1 P1 P1AVG I1 RMS V1 RMS I2 V2 P2 P2 AVG I2 RMS V2 RMS Q1AVG Q1 Q2 AVG Q2 S1 PF1 S2 PF2 T PSUM SSUM Q SUM I1 DCOFF I1 GAIN V1 DCOFF V1 GAIN P1 OFF I1ACOFF Q1OFF I2 DCOFF I2 GAIN V2DCOFF V2GAIN P2 OFF I2 ACOFF Q2 OFF Epsilon Ichan LEVEL SampleCount - Description1 Configuration 2 Register Checksum I1 Instantaneous Current V1 Instantaneous Voltage Instantaneous Power 1 Active Power 1 I1 RMS Current V1 RMS Voltage I2 Instantaneous Current V2 Instantaneous Voltage Instantaneous Power 2 Active Power 2 I2 RMS Current V2 RMS Voltage Reactive Power 1 Instantaneous Reactive Power 1 Reactive Power 2 Instantaneous Reactive Power 2 Reserved Reserved Apparent Power 1 Power Factor 1 Reserved Reserved Apparent Power 2 Power Factor 2 Reserved Temperature Reserved Total Active Power Total Apparent Power Total Reactive Power I1 DC Offset I1 Gain V1 DC Offset V1 Gain Average Active Power 1 Offset I1 AC Offset Average Reactive Power 1 Offset I2 DC Offset I2 Gain V2 DC Offset V2 Gain Average Active Power 2 Offset I2 AC Offset Average Reactive Power 2 Offset Reserved Reserved Reserved Ratio of Line to Sample Frequency Automatic Channel Select Level Sample Count Reserved DSP3 Y N N N N N N N N N N N N N N N N N HOST 3 Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y N N Y Y N N Y Y N Y N N N Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y Y N Y N Y Y Y Default 0x 00 0200 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 40 0000 0x 00 0000 0x 40 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 40 0000 0x 00 0000 0x 40 0000 0x 00 0000 0x 00 0000 0x 00 0000 0x 01 999A 0x 82 8F5C 0x 00 0FA0 31 CS5480 53 54* 55* 56* 57 58* 59* 60* 61 62 63 Notes: 32 11 0101 11 0110 11 0111 11 1000 11 1001 11 1010 11 1011 11 1100 11 1101 11 1110 11 1111 TGAIN TOFF PMIN (IRMSMIN) TSETTLE LoadMIN VFRMS SYSGAIN Time - Reserved Temperature Gain Temperature Offset Channel Select Minimum Amplitude Filter Settling Time to Conv. Startup No Load Threshold Voltage Fixed RMS Reference System Gain System Time (in samples) Reserved Reserved Y Y Y Y Y Y N N Y Y Y Y Y Y Y Y 0x 06 EA89 0x D8 86FA 0x 00 624D 0x 00 001E 0x 00 0000 0x 5A 8279 0x 50 0000 0x 00 0000 - (1) Warning: Do not write to unpublished or reserved register locations. (2) * Registers with checksum protection. (3) Registers that can be set to write protect from DSP and/or HOST. DS893F1 CS5480 6.4 Software Registers Summary (Page 17) Address2 0* 1* 2 3 4* 5* 6 7 8* 9* 10 11 12* 13* 14 15 16 17 18 19 20 21 22 23 24 25 26 27 28 29 30 31 RA[5:0] 00 0000 00 0001 00 0010 00 0011 00 0100 00 0101 00 0110 00 0111 00 1000 00 1001 00 1010 00 1011 00 1100 00 1101 00 1110 00 1111 01 0000 01 0001 01 0010 01 0011 01 0100 01 0101 01 0110 01 0111 01 1000 01 1001 01 1010 01 1011 01 1100 01 1101 01 1110 01 1111 Notes: (1) Warning: Do not write to unpublished or reserved register locations. (2) * Registers with checksum protection. (3) Registers that can be set to write protect from DSP and/or HOST. DS893F1 Name V1SagDUR V1SagLEVEL I1OverDUR I1OverLEVEL V2SagDUR V2SagLEVEL I2OverDUR I2OverLEVEL - Description1 V1 Sag Duration V1 Sag Level Reserved Reserved I1 Overcurrent Duration I1 Overcurrent Level Reserved Reserved V2 Sag Duration V2 Sag Level Reserved Reserved I2 Overcurrent Duration I2 Overcurrent Level Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved DSP3 Y Y Y Y Y Y Y Y HOST 3 Default Y 0x 00 0000 Y 0x 00 0000 Y 0x 00 0000 Y 0x 7F FFFF Y 0x 00 0000 Y 0x 00 0000 Y 0x 00 0000 Y 0x 7F FFFF - 33 CS5480 6.5 Software Registers Summary (Page 18) Address2 28* 29 30 31 32 33 34 35 36 37 38 39 40 41 42 43* 44 45 46* 47* 48 49 50* 51* 52 53 54 55 56 57 58* 59 60 61 62 63* RA[5:0] 01 1100 01 1101 01 1110 01 1111 10 0000 10 0001 10 0010 10 0011 10 0100 10 0101 10 0110 10 0111 10 1000 10 1001 10 1010 10 1011 10 1100 10 1101 10 1110 10 1111 11 0000 11 0001 11 0010 11 0011 11 0100 11 0101 11 0110 11 0111 11 1000 11 1001 11 1010 11 1011 11 1100 11 1101 11 1110 11 1111 Notes: (1) Warning: Do not write to unpublished or reserved register locations. (2) * Registers with checksum protection. (3) Registers that can be set to write protect from DSP and/or HOST. 34 Name PulseRate INTGAIN V1Swell DUR V1Swell LEVEL V2Swell DUR V2Swell LEVEL ZX LEVEL Scale Description1 Energy Pulse Rate Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Reserved Rogowski Coil Integrator Gain Reserved Reserved V1 Swell Duration V1 Swell Level Reserved Reserved V2 Swell Duration V2 Swell Level Reserved Reserved Reserved Reserved Reserved Reserved Zero-Crossing Threshold Reserved Reserved Reserved Reserved I-Channel Gain Calibration Scale Value DSP3 Y Y Y Y Y Y Y Y HOST 3 Default Y 0x 80 0000 Y 0x 14 3958 Y 0x 00 0000 Y 0x 7F FFFF Y 0x 00 0000 Y 0x 7F FFFF Y 0x 10 0000 Y 0x 4C CCCC DS893F1 CS5480 6.6 Register Descriptions 22. "Default" = bit states after power-on or reset 23. DO NOT write a "1" to any unpublished register bit or to a bit published as "0". 24. DO NOT write a "0" to any bit published as "1". 25. DO NOT write to any unpublished register address. 6.6.1 Configuration 0 (Config0) - Page 0, Address 0 23 1 22 - 21 0 20 0 19 - 18 - 17 - 16 - 15 - 14 0 13 1 12 0 11 0 10 - 9 - 8 INT_POL 7 I2PGA[1] 6 I2PGA[0] 5 I1PGA[1] 4 I1PGA[0] 3 - 2 NO_OSC 1 IZX_CH 0 0 Default = 0x80 2000 [23:9] Reserved. INT_POL Interrupt Polarity. 0 = Active low (Default) 1 = Active high I2PGA[1:0] Select PGA gain for I2 channel. 00 = 10x gain (Default) 10 = 50x gain I1PGA[1:0] Select PGA gain for I1 channel. 00 = 10x gain (Default) 10 = 50x gain [3] Reserved. NO_OSC Disable crystal oscillator (making XIN a logic-level input). 0 = Crystal oscillator enabled (Default) 1 = Crystal oscillator disabled IZX_CH Select current channel for zero-cross detect. 0 = Selects current channel 1 for zero-cross detect (Default) 1 = Selects current channel 2 for zero-cross detect [0] Reserved. DS893F1 35 CS5480 6.6.2 Configuration 1 (Config1) - Page 0, Address 1 23 0 22 EPG3_ON 21 EPG2_ON 20 EPG1_ON 15 1 14 1 13 1 12 0 19 0 18 DO3_OD 17 DO2_OD 16 DO1_OD 11 10 9 8 DO3MODE[3] DO3MODE[2] DO3MODE[1] DO3MODE[0] 7 6 5 4 3 2 1 0 DO2MODE[3] DO2MODE[2] DO2MODE[1] DO2MODE[0] DO1MODE[3] DO1MODE[2] DO1MODE[1] DO1MODE[0] Default = 0x00 EEEE 36 [23] Reserved. EPG3_ON Enable EPG3 block. 0 = Disable energy pulse generation block 3 (Default) 1 = Enable energy pulse generation block 3 EPG2_ON Enable EPG2 block. 0 = Disable energy pulse generation block 2 (Default) 1 = Enable energy pulse generation block 2 EPG1_ON Enable EPG1 block. 0 = Disable energy pulse generation block 1 (Default) 1 = Enable energy pulse generation block 1 [19] Reserved. DO3_OD Allow the DO3 pin to be an open-drain output. 0 = Normal output (Default) 1 = Open-drain output DO2_OD Allow the DO2 pin to be an open-drain output. 0 = Normal output (Default) 1 = Open-drain output DO1_OD Allow the DO1 pin to be an open-drain output. 0 = Normal output (Default) 1 = Open-drain output [15:12] Reserved. DO3MODE[3:0] Output control for DO3 pin. 0000 = Energy pulse generation block 1 (EPG1) output 0001 = Energy pulse generation block 2 (EPG2) output 0010 = Energy pulse generation block 3 (EPG3) output 0011 = Reserved 0100 = P1 sign 0101 = P2 sign 0110 = PSUM sign 0111 = Q1 sign 1000 = Q2 sign 1001 = QSUM sign 1010 = Reserved 1011 = V1/V2 zero-crossing 1100 = I1/I2 zero-crossing 1101 = Reserved 1110 = Hi-Z, pin not driven (Default) 1111 = Interrupt DS893F1 CS5480 DO2MODE[3:0] Output control for DO2 pin. 0000 = Energy pulse generation block 1 (EPG1) output 0001 = Energy pulse generation block 2 (EPG2) output 0010 = Energy pulse generation block 3 (EPG3) output 0011 = Reserved 0100 = P1 sign 0101 = P2 sign 0110 = PSUM sign 0111 = Q1 sign 1000 = Q2 sign 1001 = QSUM sign 1010 = Reserved 1011 = V1/V2 zero-crossing 1100 = I1/I2 zero-crossing 1101 = Reserved 1110 = Hi-Z, pin not driven (Default) 1111 = Interrupt DO1MODE[3:0] Output control for DO1 pin. 0000 = Energy pulse generation block 1 (EPG1) output 0001 = Energy pulse generation block 2 (EPG2) output 0010 = Energy pulse generation block 3 (EPG3) output 0011 = Reserved 0100 = P1 sign 0101 = P2 sign 0110 = PSUM sign 0111 = Q1 sign 1000 = Q2 sign 1001 = QSUM sign 1010 = Reserved 1011 = V1/V2 zero-crossing 1100 = I1/I2 zero-crossing 1101 = Reserved 1110 = Hi-Z, pin not driven (Default) 1111 = Interrupt DS893F1 37 CS5480 6.6.3 Configuration 2 (Config2) - Page 16, Address 0 23 VFIX 22 POS 21 ICHAN 20 IHOLD 19 IVSP 18 MCFG[1] 17 MCFG[0] 16 - 15 - 14 APCM 13 - 12 ZX_LPF 11 0 10 REG_CSUM_OFF 9 AFC 8 I2FLT[1] 7 I2FLT[0] 6 V2FLT[1] 5 V2FLT[0] 4 I1FLT[1] 3 I1FLT[0] 2 V1FLT[1] 1 V1FLT[0] 0 IIR_OFF Default = 0x00 0200 VFIX Use internal RMS voltage reference instead of voltage input for average active power. 0 = Use voltage input. (Default) 1 = Use internal RMS voltage reference (VFRMS). POS Positive energy only. Suppress negative values in P1AVG and P2AVG. If a negative value is calculated, a zero result will be stored. 0 = Positive and negative energy (Default) 1 = Positive energy only ICHAN Chooses which current channel is used for the PSUM, QSUM, SSUM registers. Applicable only when MCFG[1:0] = 00 and IHOLD = 1. 0 = PSUM, QSUM, and SSUM registers are driven by current channel 1 (P1) (Default) 1 = PSUM, QSUM, and SSUM registers are driven by current channel 2 (P2). IHOLD IHOLD suspends automatic channel selection for total power calculations. Applicable only when MCFG[1:0] = 00. 0 = Energy channel selected automatically by magnitude compare and on IVSP bit (Default) 1 = Energy channel selected by user and depend on ICHAN configuration Refer to Channel Select Level and Channel Select Minimum Amplitude registers (IchanLEVEL) and PMIN (IRMSMIN) for the magnitudes compared. IVSP Use IRMS results instead of PAVG for automatic energy channel selection. Applicable only when MCFG[1:0] = 00 and IHOLD = 0. 0 = Use P1AVG and P2AVG instead of I1RMS and I2RMS (Default) 1 = Use I1RMS and I2RMS instead of P1AVG and P2AVG MCFG[1:0] Meter Configuration bits are used to control how the meter interprets the current channels when calculating total power -- independently or collectively. 00 = 1V, 1I + Neutral mode; PSUM = P1AVG or P2AVG, QSUM = Q1AVG or Q2AVG, SSUM = S1 or S2 (Default) 01 = 1V, 2I mode; PSUM = (P1AVG+P2AVG)/2, QSUM=(Q1AVG+Q2AVG)/2, SSUM=(S1+S2)/2 10 = Reserved 11 = Reserved [16:15] Reserved. APCM Selects the apparent power calculation method. 0 = VxRMS x IxRMS (Default) 1 = SQRT(PAVG2 + QAVG2) 38 [13] Reserved. ZX_LPF Enable LPF in zero-cross detect. 0 = LPF disabled (Default) 1 = LPF enabled [11] Reserved. DS893F1 CS5480 REG_CSUM_OFF Disable checksum on critical registers. 0 = Enable checksum on critical registers (Default) 1 = Disable checksum on critical registers AFC Enables automatic line frequency measurement which sets Epsilon every time a new line frequency measurement completes. Epsilon is used to control the gain of 90-degree phase shift integrator used in quadrature power calculations. 0 = Disable automatic line frequency measurement 1 = Enable automatic line frequency measurement (Default) I2FLT[1:0] Filter enable for current channel 2. 00 = No filter (Default) 01 = High-pass filter (HPF) on current channel 2 10 = Phase-matching filter (PMF) on current channel 2 11 = Rogowski coil integrator (INT) on current channel 2 V2FLT[1:0] Filter enable for voltage channel 2. 00 = No filter (Default) 01 = High-pass filter (HPF) on voltage channel 2 10 = Phase-matching filter (PMF) on voltage channel 2 11 = Reserved I1FLT[1:0] Filter enable for current channel 1. 00 = No filter (Default) 01 = High-pass filter (HPF) on current channel 1 10 = Phase-matching filter (PMF) on current channel 1 11 = Rogowski coil integrator (INT) on current channel 1 V1FLT[1:0] Filter enable for voltage channel 1. 00 = No filter (Default) 01 = High-pass filter (HPF) on voltage channel 1 10 = Phase-matching filter (PMF) on voltage channel 1 11 = Reserved IIR_OFF Bypass IIR filter. 0 = Do not bypass IIR filter (Default) 1 = Bypass IIR filter DS893F1 39 CS5480 6.6.4 Phase Compensation (PC) - Page 0, Address 5 23 CPCC2[1] 22 CPCC2[0] 21 CPCC1[1] 20 CPCC1[0] 19 - 18 - 17 FPCC2[8] 16 FPCC2[7] 15 FPCC2[6] 14 FPCC2[5] 13 FPCC2[4] 12 FPCC2[3] 11 FPCC2[2] 10 FPCC2[1] 9 FPCC2[0] 8 FPCC1[8] 7 6 5 4 3 2 1 0 FPCC1[7] FPCC1[6] FPCC1[5] FPCC1[4] FPCC1[3] FPCC1[2] FPCC1[1] FPCC1[0] Default = 0x00 0000 CPCC2[1:0] Coarse phase compensation control for I2 and V2. 00 = No extra delay 01 = 1 OWR delay in current channel 2 10 = 1 OWR delay in voltage channel 2 11 = 2 OWR delay in voltage channel 2 CPCC1[1:0] Coarse phase compensation control for I1 and V1. 00 = No extra delay 01 = 1 OWR delay in current channel 1 10 = 1 OWR delay in voltage channel 1 11 = 2 OWR delay in voltage channel 1 [19:18] Reserved. FPCC2[8:0] Fine phase compensation control for I2 and V2. Sets a delay in current, relative to voltage. Resolution: 0.008789 at 50Hz and 0.010547 at 60Hz (OWR = 4000) FPCC1[8:0] Fine phase compensation control for I1 and V1. Sets a delay in current, relative to voltage. Resolution: 0.008789 at 50Hz and 0.010547 at 60Hz (OWR = 4000) 6.6.5 UART Control (SerialCtrl) - Page 0, Address 7 23 - 22 - 21 - 20 - 19 - 18 17 RX_PU_OFF RX_CSUM_OFF 16 - 15 BR[15] 14 BR[14] 13 BR[13] 12 BR[12] 11 BR[11] 10 BR[10] 9 BR[9] 8 BR[8] 7 BR[7] 6 BR[6] 5 BR[5] 4 BR[4] 3 BR[3] 2 BR[2] 1 BR[1] 0 BR[0] Default = 0x02 004D [23:19] Reserved. RX_PU_OFF Disable the pull-up resistor on the RX input pin. 0 = Pull-up resistor enabled (Default) 1 = Pull-up resistor disabled RX_CSUM_OFF Disable the checksum on serial port data. 0 = Enable checksum 1 = Disable checksum (Default) 40 [16] Reserved. BR[15:0] Baud rate (serial bit rate). BR[15:0] = Baud Ratex524288/MCLK DS893F1 CS5480 6.6.6 Pulse Output Width (PulseWidth) - Page 0, Address 8 23 - 22 - 21 - 20 - 19 18 17 16 FREQ_RNG[3] FREQ_RNG[2] FREQ_RNG[1] FREQ_RNG[0] 15 PW[15] 14 PW[14] 13 PW[13] 12 PW[12] 11 PW[11] 10 PW[10] 9 PW[9] 8 PW[8] 7 6 5 4 3 2 1 0 PW[7] PW[6] PW[5] PW[4] PW[3] PW[2] PW[1] PW[0] Default = 0x00 0001 (265.6s at OWR = 4kHz) PulseWidth sets the energy pulse frequency range and the duration of energy pulses. The actual pulse duration is 250s plus the contents of PulseWidth divided by 64,000. PulseWidth is an integer in the range of 1 to 65,535. [23:20] Reserved. FREQ_RNG[3:0] Energy pulse (PulseRate) frequency range for 0.1% resolution. 0000 = Freq. range: 2kHz-0.238Hz (Default) 0001 = Freq. range: 1kHz-0.1192Hz 0010 = Freq. range: 500Hz-0.0596Hz 0011 = Freq. range: 250Hz-0.0298Hz 0100 = Freq. range: 125Hz-0.0149Hz 0101 = Freq. range: 62.5Hz-0.00745Hz 0110 = Freq. range: 31.25Hz-0.003725Hz 0111 = Freq. range: 15.625Hz-0.0018626Hz 1000 = Freq. range: 7.8125Hz-0.000931323Hz 1001 = Freq. range: 3.90625Hz-0.000465661Hz 1010 = Reserved ... 1111 = Reserved PW[15:0] Energy Pulse Width. 6.6.7 Pulse Output Rate (PulseRate) - Page 18, Address 28 MSB -(20) LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2 -6 2 -7 ..... 2 -17 2 -18 2 -19 2 -20 2 -21 2 -22 2 -23 Default= 0x80 0000 PulseRate sets the full-scale frequency for the energy pulse outputs. For a 4kHz sample rate, the maximum pulse rate is 2kHz. This is a two's complement value in the range of -1value1, with the binary point to the left of the MSB. Refer to section 5.5 Meter Configuration Modes on page 21 for more information. DS893F1 41 CS5480 6.6.8 Pulse Output Control (PulseCtrl) - Page 0, Address 9 23 - 22 - 21 - 20 - 19 - 18 - 17 - 16 - 15 - 14 - 13 - 12 - 11 EPG3IN[3] 10 EPG3IN[2] 9 EPG3IN[1] 8 EPG3IN[0] 7 6 5 4 3 2 1 0 EPG2IN[3] EPG2IN[2] EPG2IN[1] EPG2IN[0] EPG1IN[3] EPG1IN[2] EPG1IN[1] EPG1IN[0] Default = 0x00 0000 This register controls the input to the energy pulse generation block (EPGx). [23:12] Reserved. EPGxIN[3:0] Selects the input to the energy pulse generation block (EPGx). 0000 = P1AVG (Default) 0001 = P2AVG 0010 = PSUM 0011 = Q1AVG 0100 = Q2AVG 0101 = QSUM 0110 = S1 0111 = S2 1000 = SSUM 1001 = Unused ... 1111 = Unused 6.6.9 Register Lock Control (RegLock) - Page 0, Address 34 23 - 22 - 21 - 20 - 19 - 18 - 17 - 16 - 15 - 14 - 13 - 12 DSP_LCK[4] 11 DSP_LCK[3] 10 DSP_LCK[2] 9 DSP_LCK[1] 8 DSP_LCK[0] 7 6 5 4 3 2 1 0 - - - HOST_LCK[4] HOST_LCK[3] HOST_LCK[2] HOST_LCK[1] HOST_LCK[0] Default = 0x00 0000 [23:13] Reserved. DSP_LCK[4:0] DSP_LCK[4:0] = 0x16 sets the DSP lockable registers to be write protected from the CS5480 internal calculation engine. Writing 0x09 unlocks the registers. [7:5] Reserved. HOST_LCK[4:0] HOST_LCK[4:0] = 0x16 sets all the registers except RegLock, Status0, Status1, and Status2 to be write protected from the serial interface. Writing 0x09 unlocks the registers. 42 DS893F1 CS5480 6.6.10 Phase Sequence Detection and Control (PSDC) - Page 0, Address 48 23 DONE 22 PSCNT[6] 21 PSCNT[5] 20 PSCNT[4] 19 PSCNT[3] 18 PSCNT[2] 17 PSCNT[1] 16 PSCNT[0] 15 - 14 - 13 - 12 - 11 - 10 - 9 - 8 - 7 - 6 - 5 DIR 4 CODE[4] 3 CODE[3] 2 CODE[2] 1 CODE[1] 0 CODE[0] Default = 0x00 0000 DONE Indicates that phase sequence detection has completed successfully. If not set after one line-cycle, the phase sequence detection must be restarted after ensuring that the voltage input is satisfactory. PSCNT[6:0] Indicates the number of OWR samples counted by the phase sequence counter. It counts over an interval from the start command to the next rising or falling V-channel zero-crossing as determined by the DIR bit. [15:6] Reserved. DIR Set the zero-crossing edge direction, which will stop the phase sequence counter. 0 = Stop measuring at negative to positive zero-crossing - Rising Edge. (Default) 1 = Stop measuring at positive to negative zero-crossing - Falling Edge. CODE[4:0] Write 10110 to this location to start the phase sequence counter. 6.6.11 Checksum of Critical Registers (RegChk) - Page 16, Address 1 MSB 223 LSB 222 221 220 219 218 217 216 ..... 26 25 24 23 22 21 20 Default = 0x00 0000 This register contains the checksum of critical registers. DS893F1 43 CS5480 6.6.12 Interrupt Status (Status0) - Page 0, Address 23 23 DRDY 22 CRDY 21 WOF 20 - 19 - 18 MIPS 17 V2SWELL 16 V1SWELL 15 P2OR 14 P1OR 13 I2OR 12 I1OR 11 V2OR 10 V1OR 9 I2OC 8 I1OC 7 V2SAG 6 V1SAG 5 TUP 4 FUP 3 IC 2 RX_CSUM_ERR 1 CRC_ERR 0 RX_TO Default = 0x80 0000 The Status0 register indicates a variety of conditions within the chip. Writing a one to a Status0 register bit will clear that bit. Writing a `0' to any bit has no effect. DRDY Data Ready. During conversion, this bit indicates that low-rate results have been updated. It indicates completion of other host instruction and the reset sequence. CRDY Conversion Ready. Indicates that sample rate (output word rate) results have been updated. WOF Watchdog timer overflow. [20:19] Reserved. MIPS MIPS overflow. Sets when the calculation engine has not completed processing a sample before the next one arrives. V2SWELL (V1SWELL) V2 (V1) swell event detected. 44 P2OR (P1OR) Power out of range. Sets when the measured power would cause the P2 (P1) register to overflow. V2OR (V1OR) Voltage out of range. Set when the measured voltage would cause the V2 (V1) register to overflow. I2OC (I1OC) I2 (I1) overcurrent. [7] Reserved. V2SAG (V1SAG) V2 (V1) sag event detected. TUP Temperature updated. Indicates when the Temperature register (T) has been updated. FUP Frequency updated. Indicates the Epsilon register has been updated. IC Invalid command has been received. RX_CSUM_ERR Received data checksum error. Sets to `1' automatically if checksum error is detected on serial port received data. CRC_ERR ROM CRC error. Sets to `1' automatically if ROM CRC error is detected. RX_TO SDI/RX time out. Sets to `1' automatically when SDI/RX time out occurs. DS893F1 CS5480 6.6.13 Interrupt Mask (Mask) - Page 0, Address 3 23 DRDY 22 CRDY 21 WOF 20 - 19 - 18 MIPS 17 V2SWELL 16 V1SWELL 15 P2OR 14 P1OR 13 I2OR 12 I1OR 11 V2OR 10 V1OR 9 I2OC 8 I1OC 7 V2SAG 6 V1SAG 5 TUP 4 FUP 3 IC 2 RX_CSUM_ERR 1 CRC_ERR 0 RX_TO Default = 0x00 0000 The Mask register is used to control the activation of the INT pin. Writing a '1' to a Mask register bit will allow the corresponding Status0 register bit to activate the INT pin when set. [23:0] Enable/disable (mask) interrupts. 0 = Interrupt disabled (Default) 1 = Interrupt enabled 6.6.14 Chip Status 1 (Status1) - Page 0, Address 24 23 - 22 - 21 - 20 - 19 - 18 - 17 - 16 - 15 LCOM[7] 14 LCOM[6] 13 LCOM[5] 12 LCOM[4] 11 LCOM[3] 10 LCOM[2] 9 LCOM[1] 8 LCOM[0] 7 - 6 - 5 - 4 - 3 TOD 2 VOD 1 I2OD 0 I1OD Default = 0x80 1800 This register indicates a variety of conditions within the chip. [23:16] Reserved. LCOM[7:0] Indicates the value of the last serial command executed. [7:4] Reserved. TOD Modulator oscillation has been detected in the temperature ADC. VOD Modulator oscillation has been detected in the voltage ADC. I2OD (I1OD) Modulator oscillation has been detected in the current2 (current1) ADC. DS893F1 45 CS5480 6.6.15 Chip Status 2 (Status2) - Page 0, Address 25 23 - 22 - 21 - 20 - 19 - 18 - 17 - 16 - 15 - 14 - 13 - 12 - 11 - 10 - 9 - 8 - 7 - 6 - 5 QSUM_SIGN 4 Q2_SIGN 3 Q1_SIGN 2 PSUM_SIGN 1 P2_SIGN 0 P1_SIGN Default = 0x00 0000 This register indicates a variety of conditions within the chip. [23:6] Reserved. QSUM_SIGN Indicates the sign of the value contained in QSUM. 0 = positive value 1 = negative value Q2_SIGN Indicates the sign of the value contained in Q2AVG. 0 = positive value 1 = negative value Q1_SIGN Indicates the sign of the value contained in Q1AVG. 0 = positive value 1 = negative value PSUM_SIGN Indicates the sign of the value contained in PSUM. 0 = positive value 1 = negative value P2_SIGN Indicates the sign of the value contained in P2AVG. 0 = positive value 1 = negative value P1_SIGN Indicates the sign of the value contained in P1AVG. 0 = positive value 1 = negative value 6.6.16 Line to Sample Frequency Ratio (Epsilon) - Page 16, Address 49 MSB -(20) LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2 -6 2 -7 ..... 2 -17 2 -18 2 -19 2 -20 2 -21 2 -22 2 -23 Default = 0x01 999A (0.0125 or 50Hz/4.0kHz) Epsilon is the ratio of the input line frequency to the OWR. It can either be written by the application program or calculated automatically from the line frequency (from the voltage channel 1 input) using the AFC bit in the Config2 register. It is a two's complement value in the range of -1.0 value1.0, with the binary point to the right of the MSB. Negative values are not used. 46 DS893F1 CS5480 6.6.17 Automatic Channel Select Level (IchanLEVEL ) - Page 16, Address 50 MSB 20 LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2 -6 2 -7 ..... 2 -17 2 -18 2 -19 2 -20 2 -21 2 -22 2 -23 Default = 0x82 8F5C (1.02 or 2% minimum difference) Sets the hysteresis level for automatic energy channel selection. The channel select level register sets the hysteresis level for automatic energy channel selection. If the most-positive value of P1AVG and P2AVG (I1RMS and I2RMS) is greater than IchanLEVEL multiplied by the least-positive value, and is also greater than IchanMIN, the channel associated with the most-positive value will be used. If not, the previous channel selection will remain. The value in this register is an unsigned fixed-point value in the range of 0value2.0, with the binary point to the right of the MSB. A value of 1.0 or less indicates no hysteresis will be used. 6.6.18 Current Channel Minimum Amplitude (PMIN (IRMSMIN)) - Page 16, Address 56 MSB -(20) LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2 -6 2 -7 ..... 2 -17 2 -18 2 -19 2 -20 2 -21 2 -22 2 -23 Default = 0x00 624D (0.003) Sets the minimum level for automatic energy channel selection. The PMIN (IRMSMIN) register sets the minimum level for automatic energy channel selection. If the most-positive values of P1AVG (or I1RMS) register and P2AVG (or I2 RMS) register is less than PMIN (IRMSMIN), the previous channel selection will remain in use. It is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. Negative values are not used. 6.6.19 No Load Threshold (LoadMIN) - Page 16, Address 58 MSB -(20) LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2 -6 2 -7 ..... 2 -17 2 -18 2 -19 2 -20 2 -21 2 -22 2 -23 Default = 0x00 0000 LoadMIN is used to set the no-load threshold for the anti-creep function. When the magnitudes of PSUM and QSUM are less than LoadMIN, PSUM and QSUM are forced to zero. When the magnitude of SSUM is less than LoadMIN, SSUM is forced to zero. LoadMIN is a two's complement value in the range of -1.0 value1.0, with the binary point to the right of the MSB. Negative values are not used. DS893F1 47 CS5480 6.6.20 Voltage Fixed RMS Reference (VFRMS ) - Page 16, Address 59 MSB -(20) LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2 -6 2 -7 ..... 2 -17 2 -18 2 -19 2 -20 2 -21 2 -22 2-23 Default = 0x5A 8279 (0.7071068) The VFRMS register contains the internal RMS reference used when voltage input tampering is detected by the application program. The application may choose to set the VFIX bit in the Config2 register to force full-scale energy accumulation at the VFRMS level. This register holds two's complement value in the range of 0.0 value <1.0, with the binary point to the right of the MSB. Negative values are not used. 6.6.21 Sample Count (SampleCount) - Page 16, Address 51 MSB 0 LSB 222 221 220 219 218 217 216 ..... 26 25 24 23 22 21 20 Default = 0x00 0FA0 (4000) Determines the number of OWR samples to use in calculating low-rate results. SampleCount (N) is an integer in the range of 100 to 8,388,607. Values less than 100 should not be used. 6.6.22 Filter Settling Time for Conversion Startup (TSETTLE) - Page 16, Address 57 MSB 2 23 LSB 2 22 2 21 2 20 219 218 217 216 ..... 26 25 24 23 22 21 20 Default = 0x00 001E (30) Sets the number of OWR samples that will be used to allow filters to settle at the beginning of Conversion and Calibration commands. This is an integer in the range of 0 to 16,777,215 samples. 6.6.23 System Gain (SysGAIN) - Page 16, Address 60 MSB -(21) LSB 20 2 -1 2 -2 2 -3 2 -4 2 -5 2 -6 ..... 2-16 2-17 2-18 2-19 2-20 2-21 2-22 Default = 0x50 0000 (1.25) System Gain (SysGAIN) is applied to all channels. By default, SysGAIN = 1.25, but can be finely adjusted to compensate for voltage reference error. It is a two's complement value in the range of -2.0value2.0, with the binary point to the right of the second MSB. Values should be kept within 5% of 1.25. 48 DS893F1 CS5480 6.6.24 Rogowski Coil Integrator Gain (IntGAIN) - Page 18, Address 43 MSB -(20) LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2 -6 2 -7 ..... 2 -17 2-18 2 -19 2 -20 2 -21 2 -22 2 -23 Default = 0x14 3958 Gain for the Rogowski coil integrator. This must be programmed accordingly for 50Hz and 60Hz (0.0395 for 50Hz, 0.046875 for 60Hz). This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. Negative values are not used. 6.6.25 System Time (Time) - Page 16, Address 61 MSB 2 23 LSB 2 22 2 21 2 20 219 218 217 216 ..... 26 25 24 23 22 21 20 Default = 0x00 0000 System Time (Time) is measured in OWR samples. This is an unsigned integer in the range of 0 to 16,777,215 samples. At OWR = 4.0kHz, OWR will overflow every 1 hour, 9 minutes, and 54 seconds. Time can be used by the application to manage real-time events. 6.6.26 Voltage 1 Sag Duration (V1SagDUR ) - Page 17, Address 0 MSB 0 LSB 2 22 2 21 2 20 219 218 217 216 ..... 26 25 24 23 22 21 20 Default = 0x00 0000 Voltage 1 Sag Duration, V1SagDUR, determines the count of OWR samples utilized to determine a sag event. These are integers in the range of 0 to 8,388,607 samples. A value of zero disables the feature. 6.6.27 Voltage 1 Sag Level (V1SagLEVEL ) - Page 17, Address 1 MSB -(20) LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2 -6 2 -7 ..... 2 -17 2 -18 2 -19 2 -20 2 -21 2 -22 2 -23 Default = 0x00 0000 Voltage 1 Sag Level, V1SagLEVEL, establishes a threshold at which a sag event is triggered. This is a two's complement value in the range of -1.0value 1.0, with the binary point to the right of the MSB. Negative values are not used. DS893F1 49 CS5480 6.6.28 Current 1 Overcurrent Duration (I1OverDUR ) - Page 17, Address 4 MSB 0 LSB 2 22 2 21 2 20 219 218 217 216 ..... 26 25 24 23 22 21 20 Default = 0x00 0000 Current 1 Overcurrent Duration, I1OverDUR, determines the count of OWR samples utilized to determine an overcurrent event. This integer is in the range of 0 to 8,388,607 samples. A value of zero disables the feature. 6.6.29 Current 1 Overcurrent Level (I1OverLEVEL ) - Page 17, Address 5 MSB -(20) LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2 -6 2 -7 ..... 2 -17 2 -18 2 -19 2 -20 2 -21 2 -22 2-23 Default = 0x7F FFFF Current 1 Overcurrent Level, I1OverLEVEL, establishes a threshold at which an overcurrent event is triggered. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. Negative values are not used. 6.6.30 Voltage 2 Sag Duration (V2SagDUR ) - Page 17, Address 8 MSB 0 LSB 2 22 2 21 2 20 219 218 217 216 ..... 26 25 24 23 22 21 20 Default = 0x00 0000 Voltage 2 Sag Duration, V2SagDUR, determines the count of OWR samples utilized to determine a sag event. These are integers in the range of 0 to 8,388,607 samples. A value of zero disables the feature. 6.6.31 Voltage 2 Sag Level (V2SagLEVEL ) - Page 17, Address 9 MSB -(20) LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2-6 2-7 ..... 2 -17 2 -18 2 -19 2-20 2 -21 2 -22 2 -23 Default = 0x00 0000 Voltage 2 Sag Level, V2SagLEVEL, establishes a threshold at which a sag event is triggered. This is a two's complement value in the range of -1.0 value1.0, with the binary point to the right of the MSB. Negative values are not used. 50 DS893F1 CS5480 6.6.32 Current 2 Overcurrent Duration (I2OverDUR ) - Page 17, Address 12 MSB 0 LSB 2 22 2 21 220 219 218 217 216 ..... 26 25 24 23 22 21 20 Default = 0x00 0000 Current 2 Overcurrent Duration, I2OverDUR, determines the count of OWR samples utilized to determine an overcurrent event. These are integers in the range of 0 to 8,388,607 samples. A value of zero disables the feature. 6.6.33 Current 2 Overcurrent Level (I2OverLEVEL ) - Page 17, Address 13 MSB -(20) LSB 2 -1 2 -2 2 -3 2 -4 2 -5 2-6 2 -7 ..... 2 -17 2 -18 2 -19 2-20 2-21 2 -22 2 -23 Default = 0x7F FFFF Current 2 Overcurrent Level, I2OverLEVEL, establishes a threshold at which an overcurrent event is triggered. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. Negative values are not used. 6.6.34 Voltage 1 Swell Duration (V1SwellDUR ) - Page 18, Address 46 MSB 0 LSB 2 22 2 21 2 20 219 218 217 216 ..... 26 25 24 23 22 21 20 Default = 0x00 0000 Voltage 1 Swell Duration, V1SwellDUR, determines the count of OWR samples utilized to determine a swell event. These are integers in the range of 0 to 8,388,607 samples. A value of zero disables the feature. 6.6.35 Voltage 1 Swell Level (V1SwellLEVEL ) - Page 18, Address 47 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x7F FFFF Voltage 1 Swell Level, V1SwellLEVEL, establishes a threshold at which a swell event is triggered. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. Negative values are not used. DS893F1 51 CS5480 6.6.36 Voltage 2 Swell Duration (V2SwellDUR ) - Page 18, Address 50 MSB 0 LSB 222 221 220 219 218 217 216 ..... 26 25 24 23 22 21 20 Default = 0x00 0000 Voltage 2 Swell Duration, V2SwellDUR, determines the count of OWR samples utilized to determine a swell event. These are integers in the range of 0 to 8,388,607 samples. A value of zero disables the feature. 6.6.37 Voltage 2 Swell Level (V2SwellLEVEL ) - Page 18, Address 51 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x7F FFFF Voltage 2 Swell Level, V2SwellLEVEL, establishes a threshold at which a swell event is triggered. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. Negative values are not used. 6.6.38 Instantaneous Current 1 (I1) - Page 16, Address 2 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 I1 contains instantaneous current measurements for current channel 1. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.39 Instantaneous Voltage 1 (V1) - Page 16, Address 3 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 V1 contains instantaneous voltage measurements for voltage channel 1. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 52 DS893F1 CS5480 6.6.40 Instantaneous Active Power 1 (P1) - Page 16, Address 4 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 P1 contains instantaneous power measurements for current and voltage channels 1. Values in registers I1 and V1 are multiplied to generate this value. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.41 Active Power 1 (P1AVG) - Page 16, Address 5 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Instantaneous power is averaged over each low-rate interval (SampleCount samples) and then added with power offset (P1OFF) to compute active power (P1AVG). This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.42 RMS Current 1 (I1RMS ) - Page 16, Address 6 MSB 2-1 LSB 2-2 2-3 2-4 2-5 2-6 2-7 2-8 ..... 2-18 2-19 2-20 2-21 2-22 2-23 2-24 Default = 0x00 0000 I1RMS contains the root mean square (RMS) values of I1, calculated during each low-rate interval. This is an unsigned value in the range of 0value1.0, with the binary point to the left of the MSB. 6.6.43 RMS Voltage 1 (V1RMS ) - Page 16, Address 7 MSB 2-1 LSB 2-2 2-3 2-4 2-5 2-6 2-7 2-8 ..... 2-18 2-19 2-20 2-21 2-22 2-23 2-24 Default = 0x00 0000 V1RMS contains the root mean square (RMS) value of V1, calculated during each low-rate interval. This is an unsigned value in the range of 0value1.0, with the binary point to the left of the MSB. DS893F1 53 CS5480 6.6.44 Instantaneous Current 2 (I2) - Page 16, Address 8 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 I2 contains instantaneous current measurements for current channel 2. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.45 Instantaneous Voltage 2 (V2) - Page 16, Address 9 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 V2 contains instantaneous voltage measurements for voltage channel 1. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.46 Instantaneous Active Power 2 (P2) - Page 16, Address 10 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 P2 contains instantaneous power measurements for current and voltage channels 2. Values in registers I2 and V are multiplied to generate this value. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.47 Active Power 2 (P2AVG ) - Page 16, Address 11 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Instantaneous power is averaged over each low-rate interval (SampleCount samples) to compute active power (P2AVG). This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 54 DS893F1 CS5480 6.6.48 RMS Current 2 (I2RMS) - Page 16, Address 12 MSB 2-1 LSB 2-2 2-3 2-4 2-5 2-6 2-7 2-8 ..... 2-18 2-19 2-20 2-21 2-22 2-23 2-24 Default = 0x00 0000 I2RMS contains the root mean square (RMS) value of I2, calculated during each low-rate interval. This is an unsigned value in the range of 0value1.0, with the binary point to the left of the MSB. 6.6.49 RMS Voltage 2 (V2RMS ) - Page 16, Address 13 MSB 2-1 LSB 2-2 2-3 2-4 2-5 2-6 2-7 2-8 ..... 2-18 2-19 2-20 2-21 2-22 2-23 2-24 Default = 0x00 0000 V2RMS contains the root mean square (RMS) value of V2, calculated during each low-rate interval. This is an unsigned value in the range of 0value1.0, with the binary point to the left of the MSB. 6.6.50 Reactive Power 1 (Q1Avg ) - Page 16, Address 14 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Reactive power 1 (Q1AVG) is Q1 averaged over each low-rate interval (SampleCount samples) and corrected by Q1OFF. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.51 Instantaneous Quadrature Power 1 (Q1) - Page 16, Address 15 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Instantaneous quadrature power, Q1, the product of V1 shifted 90 degrees and I1. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. DS893F1 55 CS5480 6.6.52 Reactive Power 2 (Q2Avg ) - Page 16, Address 16 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Reactive power 2 (Q2AVG) is Q2 averaged over each low-rate interval (SampleCount samples). This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.53 Instantaneous Quadrature Power 2 (Q2) - Page 16, Address 17 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Instantaneous quadrature power, Q2, the product of V2 shifted 90 degrees and I2. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.54 Peak Current 1 (I1PEAK) - Page 0, Address 37 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Peak Current 1 (I1PEAK) contains the value of the instantaneous current 1 sample with the greatest magnitude detected during the last low-rate interval. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.55 Peak Voltage 1 (V1PEAK) - Page 0, Address 36 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Peak voltage 1 (V1PEAK) contains the value of the instantaneous voltage 1 sample with the greatest magnitude detected during the last low-rate interval. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 56 DS893F1 CS5480 6.6.56 Apparent Power 1 (S1) - Page 16, Address 20 MSB 0 LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Apparent power 1 (S1) is the product of V1RMS and I1RMS or SQRT(P1AVG2 + Q1AVG2). This is an unsigned value in the range of 0 value 1.0, with the binary point to the right of the MSB. 6.6.57 Power Factor 1 (PF1) - Page 16, Address 21 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Power factor 1 (PF1) is calculated by dividing active power 1 (P1AVG) by apparent power 1 (S1). The sign is determined by the active power (P1AVG) sign. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.58 Peak Current 2 (I2PEAK) - Page 0, Address 39 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Peak current, I2PEAK, contains the value of the instantaneous current 2 sample with the greatest magnitude detected during the last low-rate interval. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.59 Peak Voltage 2 (V2PEAK) - Page 0, Address 38 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Peak voltage, V2PEAK, contains the value of the instantaneous voltage 2 sample with the greatest magnitude detected during the last low-rate interval. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. DS893F1 57 CS5480 6.6.60 Apparent Power 2 (S2) - Page 16, Address 24 MSB 0 LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Apparent power 2 (S2) is the product of V2RMS and I2RMS or SQRT(P2AVG2 + Q2AVG2). This is an unsigned value in the range of 0 value 1.0, with the binary point to the right of the MSB. 6.6.61 Power Factor 2 (PF2) - Page 16, Address 25 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Power factor 2 (PF2) is calculated by dividing active power 2 (P2AVG) by apparent power 2 (S2). The sign is determined by the active power (P2AVG) sign. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.62 Temperature (T) - Page 16, Address 27 MSB -(27) LSB 26 25 24 23 22 21 20 ..... 2-10 2-11 2-12 2-13 2-14 2-15 2-16 Default = 0x00 0000 T contains results from the on-chip temperature measurement. By default, T uses the Celsius scale, and is a two's complement value in the range of -128.0value128.0 (C), with the binary point to the right of bit 16. T can be rescaled by the application using the TGAIN and TOFF registers. 6.6.63 Total Active Power (PSUM ) - Page 16, Address 29 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 PSUM = P1AVG +P2AVG if MCFG[1:0] = 01 PSUM = P1AVG or P2AVG if MCFG[1:0] = 00 This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 58 DS893F1 CS5480 6.6.64 Total Apparent Power (SSUM ) - Page 16, Address 30 MSB 0 LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 SSUM = S1+S2 if MCFG[1:0] = 01 SSUM = S1 or S2 if MCFG[1:0] = 00 This is an unsigned value in the range of 0 value1.0, with the binary point to the right of the MSB. 6.6.65 Total Reactive Power (QSUM ) - Page 16, Address 31 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 QSUM = Q1AVG +Q2AVG if MCFG[1:0] = 01 QSUM = Q1AVG or Q2AVG if MCFG[1:0] = 00 This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.66 DC Offset for Current (I1DCOFF , I2DCOFF ) - Page 16, Address 32, 39 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 DC offset registers I1DCOFF and I2DCOFF are initialized to zero on reset. During DC offset calibration, selected registers are written with the inverse of the DC offset measured. The application program can also write the DC offset register values. These are two's complement values in the range of -1.0value1.0, with the binary point to the right of the MSB. 6.6.67 DC Offset for Voltage (V1DCOFF , V2DCOFF ) - Page 16, Address 34, 41 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 DC offset registers V1DCOFF and V2DCOFF are initialized to zero on reset. During DC offset calibration, selected registers are written with the inverse of the DC offset measured. The application program can also write the DC offset register values. These are two's complement values in the range of -1.0value1.0, with the binary point to the right of the MSB. DS893F1 59 CS5480 6.6.68 Gain for Current (I1GAIN , I2GAIN ) - Page 16, Address 33, 40 MSB 21 LSB 20 2-1 2-2 2-3 2-4 2-5 2-6 ..... 2-16 2-17 2-18 2-19 2-20 2-21 2-22 Default = 0x40 0000 (1.0) Gain registers I1GAIN and I2GAIN are initialized to 1.0 on reset. During gain calibration, selected registers are written with the multiplicative inverse of the gain measured. These are unsigned, fixed-point values in the range of 0value4.0, with the binary point to the right of the second MSB. 6.6.69 Gain for Voltage (V1GAIN , V2GAIN ) - Page 16, Address 35, 42 MSB 21 LSB 20 2-1 2-2 2-3 2-4 2-5 2-6 ..... 2-16 2-17 2-18 2-19 2-20 2-21 2-22 Default = 0x40 0000 (1.0) Gain registers V1GAIN and V2GAIN are initialized to 1.0 on reset. During gain calibration, selected register are written with the multiplicative inverse of the gain measured. These are unsigned fixed-point values in the range of 0value4.0, with the binary point to the right of the second MSB. 6.6.70 Average Active Power Offset (P1OFF, P2OFF ) - Page 16, Address 36, 43 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Average Active Power offset P1OFF (P2OFF ) is added to averaged power to yield P1AVG (P2AVG ) register results. It can be used to reduce systematic energy errors. These are two's complement values in the range of -1.0 value 1.0, with the binary point to the right of the MSB. 6.6.71 Average Reactive Offset (Q1OFF , Q2OFF ) - Page 16, Address 38, 45 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x00 0000 Average Reactive Power offset Q1OFF (Q2OFF ) is added to averaged reactive power to yield Q1AVG (Q2AVG ) register results. It can be used to reduce systematic energy errors. These are two's complement values in the range of -1.0 value 1.0, with the binary point to the right of the MSB. 6.6.72 AC Offset for Current (I1ACOFF, I2ACOFF ) - Page 16, Address 37, 44 MSB 2-1 LSB 2-2 2-3 2-4 2-5 2-6 2-7 2-8 ..... 2-18 2-19 2-20 2-21 2-22 2-23 2-24 Default = 0x00 0000 AC offset registers I1ACOFF and I2ACOFF are initialized to zero on reset. They are used to reduce systematic errors in the RMS results. These are unsigned values in the range of 0 value 1.0, with the binary point to the left of the MSB. 60 DS893F1 CS5480 6.6.73 Temperature Gain (TGAIN ) - Page 16, Address 54 MSB 223 LSB 222 221 220 219 218 217 216 ..... 26 25 24 23 22 21 2-20 2-21 2-22 2-21 2-22 20 Default = 0x06 EA89 Refer to section 5.9 Phase Sequence Detection on page 25 for more information. 6.6.74 Temperature Offset (TOFF ) - Page 16, Address 55 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-23 Default = 0xD8 86FA Refer to section 5.9 Phase Sequence Detection on page 25 for more information. 6.6.75 Calibration Scale (Scale) - Page18, Address 63 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-23 Default = 0x4C CCCC (0.6) The Scale register is used in the gain calibration to set the level of calibrated results of I-channel RMS. During gain calibration, the IxRMS results register is divided into the Scale register. The quotient is put into the IxGAIN register. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. Negative values are not used. 6.6.76 Zero-crossing Threshold (ZXLEVEL) - Page 18, Address 58 MSB -(20) LSB 2-1 2-2 2-3 2-4 2-5 2-6 2-7 ..... 2-17 2-18 2-19 2-20 2-21 2-22 2-23 Default = 0x10 0000 (0.125) ZXLEVEL is the level that the peak instantaneous voltage/current must exceed for the zero-crossing detection to function. This is a two's complement value in the range of -1.0value1.0, with the binary point to the right of the MSB. Negative values are not used. DS893F1 61 CS5480 7. SYSTEM CALIBRATION averaged during a calibration. The calibration procedure takes the time of N +TSETTLE OWR samples. As N is increased, the calibration takes more time but the accuracy of calibration results tends to increase. Component tolerances, residual ADC offset, and system noise require a meter to be calibrated before it meets a specific accuracy requirement. The CS5480 provides an on-chip calibration algorithm to operate the system calibration quickly and easily. Benefiting from the excellent linearity and low noise level of the CS5480, normally a CS5480 meter only needs one calibration at a single load point to achieve accurate measurements over the full load range. The DRDY bit in the Status0 register will be set at the completion of calibration commands. If an overflow occurs during calibration, other Status0 bits may be set as well. 7.1.1 Offset Calibration 7.1 Calibration in General During offset calibrations, no line voltage or current should be applied to the meter. In other words, the differential signal on voltage inputs VIN or current inputs IIN1 (IIN2) of the CS5480 should be 0V. The CS5480 provides DC offset and gain calibration that can be applied to the instantaneous voltage and current measurements and AC offset calibration, which can be applied to the current RMS calculation. 7.1.1.1 DC Offset Calibration Since the voltage and current channels have independent offset and gain registers, offset and gain calibration can be performed on any channel independently. The DC offset calibration command measures and averages DC values read on specified voltage or current channels at zero input and stores the inverse result in the associated offset registers. This DC offset will be added to instantaneous measurements in subsequent conversions, removing the offset. The data flow of the calibration is shown in Figure 24. Note that in Figure 24 the AC offset registers and gain registers affect the output results differently than the DC offset registers. The DC offset and gain values are applied to the voltage/current signals very early in the signal path; the DC offset register and gain register values affect all CS5480 results. This is not true for the AC offset correction. The AC offset registers only affect the results of the RMS current calculation. The gain register for the channel being calibrated should be set to 1.0 prior to performing DC offset calibration. DC offset calibration is not required if the high-pass filter is enabled on that channel because the DC component will be removed by the high-pass filter. 7.1.1.2 Current Channel AC Offset Calibration The CS5480 must be operating in its active state and ready to accept valid commands. Refer to section 6.1.2 Instructions on page 27 for different calibration commands. The value in the SampleCount register determines the number (N) of OWR samples that are The AC offset calibration command measures the residual RMS value on the current channel at zero input and stores the squared result in the associated AC offset register. This AC offset will be subtracted from to V*, I* Registers IN Modulator N Filter DC Offset* VRMS*, IRMS* Registers N N Gain* -1 AC Offset* N -1 * Denotes readable/writable register DC 0.6(SCALE) RMS * RMS Figure 24. Calibration Data Flow 62 DS893F1 CS5480 RMS measurements in subsequent conversions, removing the AC offset on the associated current channel. The AC offset register for the channel being calibrated should first be cleared prior to performing the calibration. The high-pass filter should be enabled if AC offset calibration is used. It is recommended that TSETTLE be set to 2000ms before performing an AC offset calibration. Note that the AC offset register holds the square of RMS value measured during calibration. Therefore, it can hold a maximum RMS noise of 0xFFFFFF . This is the maximum RMS noise that AC offset correction can remove. 7.1.2 Gain Calibration Prior to executing the gain calibration command, gain registers for any path to be calibrated (VxGAIN, IxGAIN) should be set to 1.0, and TSETTLE should be set to 2000 ms. For gain calibration, a reference signal must be applied to the meter. During gain calibration, the voltage RMS result register (VxRMS) is divided into 0.6, and the current RMS result register (IxRMS) is divided into the Scale register. The quotient is put into the associated gain register. The gain calibration algorithm attempts to adjust the gain register (VxGAIN, IxGAIN) such that the voltage RMS result register (VxRMS) equals 0.6, and the current RMS result register (IxRMS) equal the Scale register. Note that for the gain calibration, there are some limitations on choosing the reference level and the Scale register value. Using a reference or a scale that is too large or too small can cause register overflow during calibration or later during normal operation. Either condition can set Status register bits I1OR (I2OR), or VOR. The maximum value that the gain register can attain is four. Using inappropriate reference levels or scale values may also cause the CS5480 to attempt to set the gain register higher than four, therefore the gain calibration result will be invalid. The Scale register is 0.6 by default. The maximum voltage (UMAX Volts) and current (IMAX Amps) of the meter should be used as the reference signal level if the Scale register is 0.6. After gain calibration, 0.6 of the VxRMS (IxRMS) register represents UMAX Volts (IMAX Amps) for the line voltage (load current); 0.36 of the PAVG, QAVG, or Sx register represents UMAX xIMAX Watts, Vars, or VAs for the active, reactive, or apparent power. If the calibration is performed with UMAX Volts and ICAL Amps and ICAL <IMAX, the Scale register needs to be scaled down to 0.6xICAL /IMAX before performing gain calibration. After gain calibration, 0.6 of the VxRMS DS893F1 register represents UMAX Volts, 0.6 x ICAL /IMAX of the IxRMS register represents ICAL Amps, and 0.36 x ICAL /IMAX of the PxAVG, QxAVG, or Sx register represents UMAX x ICAL Watts, Vars, or VAs. 7.1.3 Calibration Order 1) If the HPF option is enabled, then any DC component that may be present in the selected signal channel will be removed, and a DC offset calibration is not required. However, if the HPF option is disabled, the DC offset calibration should be performed. When using high-pass filters, it is recommended that the DC offset register for the corresponding channel be set to 0. Before performing DC offset calibration, the DC offset register should be set to zero, and the corresponding gain register should be set to one. 2) If there is an AC offset in the IxRMS calculation, the AC offset calibration should be performed on the current channel. Before performing AC offset calibration, the AC offset register should be set to zero. It is recommended that TSETTLE be set to 2000ms before performing an AC offset calibration. 3) Perform the gain calibration. 4) If an AC offset calibration was performed (step 2), then the AC offset may need to be adjusted to compensate for the change in gain (step 3). This can be accomplished by restoring zero to the AC offset register and then perform an AC offset calibration. The adjustment could also be done by multiplying the AC offset register value that was calculated in step 2 by the gain calculated in step 3 and updating the AC offset register with the product. 7.2 Phase Compensation A phase compensation mechanism is provided to adjust for meter-to-meter variation in signal path delays. Phase offset between a voltage channel and its corresponding current channel can be calculated by using the power factor (PF1, PF2) register after a conversion. 1) Apply a reference voltage and current with a lagging power factor to the meter. The reference current waveform should lag the voltage with a 60 phase shift. 2) Start continuous conversion. 3) Accumulate multiple readings of the PF1 or PF2 register. 4) Calculate the average power factor, PFavg. 5) Calculate phase offset = arccos(PFavg) - 60. 63 CS5480 Once the phase offset is known, the CPCCx and FPCCx bits for that channel are calculated and programmed in the PC register. CPCCx bits are used if either: * * The phase offset is more than 1 output word rate (OWR) sample. More delay is needed on the voltage channel. The compensation resolution is 0.008789 at 50Hz and 0.010547 at 60Hz at an OWR of 4000Hz. 7.3 Temperature Sensor Calibration Temperature sensor calibration involves the adjustment of two parameters: temperature gain (TGAIN) and temperature offset (TOFF). These values must be known in order to calibrate the temperature sensor. 7.3.1 Temperature Offset and Gain Calibration To obtain the optimal temperature offset (TOFF) register value and temperature (TGAIN) register value, it is necessary to measure the temperature (T) register at a minimum of two points (T1 and T2) across the meter operating temperature range. The two temperature points must be far enough apart to yield reasonable accuracy, for example 25 C and 85 C. Obtain a linear fit of these points ( y = m x + b ), where the slope (m) and intercept (b) can be obtained. T2 Y= m *x +b Force Temperature (C) 6) If the phase offset is negative, then the delay should be added only to the current channel. Otherwise, add more delay to the voltage channel than to the current channel to compensate for a positive phase offset. m T1 b T Register Value Figure 25. T Register vs. Force Temp TOFF and TGAIN are calculated using the following equations: b T OFF = ----m T GAIN = m 64 DS893F1 CS5480 8. BASIC APPLICATION CIRCUITS Figure 26 shows the CS5480 configured to measure power in a single-phase, 3-wire system with 1 voltage and 2 currents (1V-2I). Figure 27 shows the CS5480 configured to measure power in a single-phase, 2-wire system with 1 voltage, 1 line current and 1 neutral current (1V-1I-1N). In these diagrams, current transformers (CTs) are used to sense the line load currents, and resistive voltage dividers are used to sense the line voltage. +3.3V L1 N +3.3V 0.1F 0.1F L2 Wh VDDA MODE VDDD VIN+ Varh +3.3V 27nF SSEL 27nF 1K VIN- +3.3V DO1 5 x 330K 1K DO2 DO3 RX CS5480 1/2 R BURDEN 1K CT TX IIN1+ CS 27nF 1/2 R BURDEN 27nF 1K Interrupt IIN1- 4.096MHz XOUT VREF+ 1/2 R BURDEN 1K IIN2+ 27nF 1/2 R BURDEN 27nF 1K LOA D 0.1 F VREF- CT LOA D Application Processor XIN IIN2- +3.3V 10K RESET GNDA GNDD 0.1 F 1 Voltage and 2 Current Figure 26. Typical Single-phase 3-Wire Connection DS893F1 65 CS5480 +3.3V 0.1F 0.1F L N Wh VDDA MODE VDDD VIN + +3.3V Varh +3.3V 27nF SSEL 27nF 1K VIN - +3.3V DO1 5 x 330K 1K DO2 DO3 RX CS5480 1/2 R BURDEN 1K CT TX IIN1+ 27nF CS 27nF XIN 1/2 R BURDEN 1K Interrupt IIN1- 4.096MHz XOUT VREF+ 1/2 R BURDEN CT 1K IIN227nF 27nF LOA D 0.1 F VREF- 1/2 R BURDEN 1K Application Processor IIN2+ +3.3V 10K RESET GNDA GNDD 0. 1F 1 Voltage , 1 Line Current, and 1 Neutral Current Figure 27. Typical Single-phase 2-Wire Connection 66 DS893F1 CS5480 9. PACKAGE DIMENSIONS 24 QFN (4mmX4mm BODY with EXPOSED PAD) PACKAGE DRAWING Dimension A A1 A3 b D D2 e E E2 L aaa bbb ddd eee MIN 0.80 0.00 0.20 2.40 2.40 0.35 mm NOM 0.90 0.02 0.20 REF 0.25 4.00 BSC 2.50 0.50 BSC 4.00 BSC 2.50 0.40 0.15 0.10 0.05 0.08 MAX 1.00 0.05 MIN 0.031 0.000 0.30 0.008 2.60 0.094 2.60 0.45 0.094 0.014 inch NOM 0.035 0.001 0.008 REF 0.010 0.157 BSC 0.098 0.020 BSC 0.157 BSC 0.098 0.016 0.006 0.004 0.002 0.003 MAX 0.039 0.002 0.012 0.102 0.102 0.018 Notes: 1. Controlling dimensions are in millimeters. 2. Dimensions and tolerances per ASME Y14.5M. 3. This drawing conforms to JEDEC outline MO-220, variation VGGD-6 with the exception of features D2 and E2, which are per supplier designations. 4. Recommended reflow profile is per JEDEC/IPC J-STD-020. DS893F1 67 CS5480 10. ORDERING INFORMATION Model CS5480-INZ/B0 Temperature Package -40 to +85 C 24-pin QFN 11. ENVIRONMENTAL, MANUFACTURING, AND HANDLING INFORMATION Model Peak Reflow Temp MSL Rating* Max Floor Life 260 C 3 7 Days CS5480-INZ/B0 * MSL (Moisture Sensitivity Level) as specified by IPC/JEDEC J-STD-020. 12. REVISION HISTORY Revision Date Changes PP1 Mar 2011 Add Tamper Detection support. PP2 May 2011 Revised 24 QFN (4.00mm Body) Package Drawing. PP3 Sep 2011 Changes to reflect B0 Silicon. Addition of Typical Load Performance section. PP4 Dec 2011 Edited for content and clarity. F1 Jan 2012 Updated the revision for publication. Contacting Cirrus Logic Support For all product questions and inquiries contact a Cirrus Logic Sales Representative. To find the one nearest to you go to www.cirrus.com IMPORTANT NOTICE Cirrus Logic, Inc. and its subsidiaries ("Cirrus") believe that the information contained in this document is accurate and reliable. However, the information is subject to change without notice and is provided "AS IS" without warranty of any kind (express or implied). Customers are advised to obtain the latest version of relevant information to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied at the time of order acknowledgment, including those pertaining to warranty, indemnification, and limitation of liability. No responsibility is assumed by Cirrus for the use of this information, including use of this information as the basis for manufacture or sale of any items, or for infringement of patents or other rights of third parties. This document is the property of Cirrus and by furnishing this information, Cirrus grants no license, express or implied under any patents, mask work rights, copyrights, trademarks, trade secrets or other intellectual property rights. Cirrus owns the copyrights associated with the information contained herein and gives consent for copies to be made of the information only for use within your organization with respect to Cirrus integrated circuits or other products of Cirrus. This consent does not extend to other copying such as copying for general distribution, advertising or promotional purposes, or for creating any work for resale. CERTAIN APPLICATIONS USING SEMICONDUCTOR PRODUCTS MAY INVOLVE POTENTIAL RISKS OF DEATH, PERSONAL INJURY, OR SEVERE PROPERTY OR ENVIRONMENTAL DAMAGE ("CRITICAL APPLICATIONS"). CIRRUS PRODUCTS ARE NOT DESIGNED, AUTHORIZED OR WARRANTED FOR USE IN PRODUCTS SURGICALLY IMPLANTED INTO THE BODY, AUTOMOTIVE SAFETY OR SECURITY DEVICES, LIFE SUPPORT PRODUCTS OR OTHER CRITICAL APPLICATIONS. INCLUSION OF CIRRUS PRODUCTS IN SUCH APPLICATIONS IS UNDERSTOOD TO BE FULLY AT THE CUSTOMER'S RISK AND CIRRUS DISCLAIMS AND MAKES NO WARRANTY, EXPRESS, STATUTORY OR IMPLIED, INCLUDING THE IMPLIED WARRANTIES OF MERCHANTABILITY AND FITNESS FOR PARTICULAR PURPOSE, WITH REGARD TO ANY CIRRUS PRODUCT THAT IS USED IN SUCH A MANNER. IF THE CUSTOMER OR CUSTOMER'S CUSTOMER USES OR PERMITS THE USE OF CIRRUS PRODUCTS IN CRITICAL APPLICATIONS, CUSTOMER AGREES, BY SUCH USE, TO FULLY INDEMNIFY CIRRUS, ITS OFFICERS, DIRECTORS, EMPLOYEES, DISTRIBUTORS AND OTHER AGENTS FROM ANY AND ALL LIABILITY, INCLUDING ATTORNEYS' FEES AND COSTS, THAT MAY RESULT FROM OR ARISE IN CONNECTION WITH THESE USES. Cirrus Logic, Cirrus, the Cirrus Logic logo designs, EXL Core, and the EXL Core logo design are trademarks of Cirrus Logic, Inc. All other brand and product names in this document may be trademarks or service marks of their respective owners. SPI is a trademark of Motorola, Inc. 68 DS893F1