Integrated Circuit True RMS-to-DC Converter AD536A Data Sheet FUNCTIONAL BLOCK DIAGRAM FEATURES True rms-to-dc conversion Laser trimmed to high accuracy 0.2% maximum error (AD536AK) 0.5% maximum error (AD536AJ) Wide response capability Computes rms of ac and dc signals 450 kHz bandwidth: V rms > 100 mV 2 MHz bandwidth: V rms > 1 V Signal crest factor of 7 for 1% error dB output with 60 dB range Low power: 1.2 mA quiescent current Single- or dual-supply operation Monolithic integrated circuit -55C to +125C operation (AD536AS) AD536A +VS ABSOLUTE VALUE COM SQUARER/ DIVIDER dB + CAV CURRENT MIRROR 25k RL IOUT +VS BUFFER IN 25k The AD536A is a complete monolithic integrated circuit that performs true rms-to-dc conversion. It offers performance comparable or superior to that of hybrid or modular units costing much more. The AD536A directly computes the true rms value of any complex input waveform containing ac and dc components. A crest factor compensation scheme allows measurements with 1% error at crest factors up to 7. The wide bandwidth of the device extends the measurement capability to 300 kHz with less than 3 dB errors for signal levels greater than 100 mV. An important feature of the AD536A, not previously available in rms converters, is an auxiliary dB output pin. The logarithm of the rms output signal is brought out to a separate pin to allow the dB conversion, with a useful dynamic range of 60 dB. Using an externally supplied reference current, the 0 dB level can be conveniently set to correspond to any input level from 0.1 V to 2 V rms. The AD536A is laser trimmed to minimize input and output offset voltage, to optimize positive and negative waveform symmetry (dc reversal error), and to provide full-scale accuracy at 7 V rms. As a result, no external trims are required to achieve the rated unit accuracy. The input and output pins are fully protected. The input circuitry can take overload voltages well beyond the supply levels. Loss of supply voltage with the input connected to external circuitry does not cause the device to fail. The output is short-circuit protected. BUFFER OUT 80k -VS 00504-001 BUF GENERAL DESCRIPTION Rev. F VIN Figure 1. The AD536A is available in two accuracy grades (J and K) for commercial temperature range (0C to 70C) applications, and one grade (S) rated for the -55C to +125C extended range. The AD536AK offers a maximum total error of 2 mV 0.2% of reading, while the AD536AJ and AD536AS have maximum errors of 5 mV 0.5% of reading. All three versions are available in a hermetically sealed 14-lead DIP or a 10-pin TO-100 metal header package. The AD536AS is also available in a 20-terminal leadless hermetically sealed ceramic chip carrier. The AD536A computes the true root-mean-square level of a complex ac (or ac plus dc) input signal and provides an equivalent dc output level. The true rms value of a waveform is a more useful quantity than the average rectified value because it relates directly to the power of the signal. The rms value of a statistical signal also relates to its standard deviation. An external capacitor is required to perform measurements to the fully specified accuracy. The value of this capacitor determines the low frequency ac accuracy, ripple amplitude, and settling time. The AD536A operates equally well from split supplies or a single supply with total supply levels from 5 V to 36 V. With 1 mA quiescent supply current, the device is well suited for a wide variety of remote controllers and battery-powered instruments. Document Feedback Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. 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Technical Support www.analog.com AD536A Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 Frequency Response .....................................................................9 General Description ......................................................................... 1 AC Measurement Accuracy and Crest Factor ...........................9 Functional Block Diagram .............................................................. 1 Applications Information .............................................................. 11 Revision History ............................................................................... 2 Typical Connections .................................................................. 11 Specifications..................................................................................... 3 Optional External Trims For High Accuracy ......................... 11 Absolute Maximum Ratings............................................................ 5 Single-Supply Operation ........................................................... 12 ESD Caution .................................................................................. 5 Choosing the Averaging Time Constant ................................. 12 Pin Configurations and Function Descriptions ........................... 6 Outline Dimensions ....................................................................... 14 Theory of Operation ........................................................................ 8 Ordering Guide .......................................................................... 15 Connections for dB Operation ................................................... 8 REVISION HISTORY 11/14--Rev. E to Rev. F Change to Figure 1 ........................................................................... 1 Changes to Table 1 ............................................................................ 3 Change to Figure 16 ....................................................................... 12 Changes to Ordering Guide .......................................................... 15 Changes to Connections for dB Operation Section .................. 11 Changes to Figure 17...................................................................... 12 Changes to Frequency Response Section .................................... 12 Updated Outline Dimensions ....................................................... 14 Changes to Ordering Guide .......................................................... 15 7/12--Rev. D to Rev. E Reorganized Layout ............................................................ Universal Changes to Figure 1 .......................................................................... 1 Changes to Figure 6 .......................................................................... 8 Changes to Figure 7 .......................................................................... 9 Changes to Figure 13, Figure 14, and Figure 15 ......................... 11 Changes to Figure 16, Figure 17, and Single-Supply Operation Section .............................................................................................. 12 Changes to Figure 21 ...................................................................... 13 Updated Outline Dimensions ....................................................... 14 3/06--Rev. B to Rev. C Updated Format .................................................................. Universal Changed Product Description to General Description ................1 Changes to General Description .....................................................1 Changes to Table 1.............................................................................3 Changes to Table 2.............................................................................5 Added Pin Configurations and Function Descriptions ...............6 Changed Standard Connection to Typical Connections .............8 Changed Single Supply Connection to Single Supply Operation............................................................................................9 Changes to Connections for dB Operation................................. 11 Changes to Figure 17...................................................................... 12 Updated Outline Dimensions ....................................................... 14 Changes to Ordering Guide .......................................................... 15 8/08--Rev. C to Rev. D Changes to Features Section............................................................ 1 Changes to General Description Section ...................................... 1 Changes to Figure 1 .......................................................................... 1 Changes to Table 2 ............................................................................ 5 Change to Figure 2 ........................................................................... 5 Changes to Figure 15 ...................................................................... 10 6/99--Rev. A to Rev. B 1/76--Revision 0: Initial Version Rev. F | Page 2 of 15 Data Sheet AD536A SPECIFICATIONS TA = +25C and 15 V dc, unless otherwise noted. Table 1. Parameter TRANSFER FUNCTION CONVERSION ACCURACY Total Error, Internal Trim1 (See Figure 13) vs. Temperature TMIN to +70C AD536AJ Typ Max VOUT = Avg(VIN)2 Min Min AD536AK Typ Max VOUT = Avg(VIN)2 Min AD536AS Typ Max VOUT = Avg(VIN)2 5 0.5 2 0.2 5 0.5 mV % of rdg 0.1 0.01 0.05 0.005 0.1 0.005 0.3 0.005 mV % of rdg/C +70C to +125C vs. Supply Voltage DC Reversal Error Total Error, External Trim1 (See Figure 16) ERROR VS. CREST FACTOR2 Crest Factor 1 to Crest Factor 2 Crest Factor = 3 Crest Factor = 7 FREQUENCY RESPONSE3 Bandwidth for 1% Additional Error (0.09 dB) VIN = 10 mV VIN = 100 mV VIN = 1 V 3 dB Bandwidth VIN = 10 mV VIN = 100 mV VIN = 1 V AVERAGING TIME CONSTANT (See Figure 19) INPUT CHARACTERISTICS Signal Range, 15 V Supplies Continuous RMS Level Peak Transient Input Continuous RMS Level, VS = 5 V Peak Transient Input, VS = 5 V Maximum Continuous Nondestructive Input Level (All Supply Voltages) Input Resistance Input Offset Voltage OUTPUT CHARACTERISTICS Offset Voltage, VIN = COM (See Figure 13) vs. Temperature vs. Supply Voltage Voltage Swing, 15 V Supplies 5 V Supply dB OUTPUT, 0 dB = 1 V rms (See Figure 7) Error, 7 mV < VIN < 7 V rms Scale Factor Scale Factor Temperature Coefficient Uncompensated IREF for 0 dB = 1 V rms IREF Range 0.1 0.01 0.2 3 0.3 0.1 0.01 0.1 2 0.1 Specified accuracy -0.1 -1.0 mV % of rdg/V mV % of rdg mV % of rdg Specified accuracy -0.1 -1.0 % of rdg % of rdg 5 45 120 5 45 120 kHz kHz kHz 90 450 2.3 25 90 450 2.3 25 90 450 2.3 25 kHz kHz MHz ms/F 0 to 7 0 to 2 V rms V peak V rms 0 to 2 7 7 V peak 25 25 25 V peak 20 2 k mV 2 mV 0.2 mV/C mV/V V V 0.6 dB mV/dB dB/C 20 2 1 2 0.1 0.1 +12.5 +0.33 20 20 7 16.67 0.8 0.4 -3 -0.033 0 to 7 20 0 to 2 5 1 mV % of rdg/C 5 45 120 20 0 to +11 0 to +2 0.1 0.01 0.2 3 0.3 Specified accuracy -0.1 -1.0 0 to 7 13.33 Unit 13.33 0 to +11 0 to +2 0.6 80 100 16.67 0.5 20 1 0.5 1 0.1 0.1 +12.5 0.2 -3 -0.033 5 1 +0.33 20 Rev. F | Page 3 of 15 13.33 0 to +11 0 to +2 0.3 80 100 16.67 0.8 0.2 +12.5 0.5 -3 -0.033 5 1 +0.33 20 80 100 % of rdg/C A A AD536A Parameter IOUT TERMINAL IOUT Scale Factor IOUT Scale Factor Tolerance Output Resistance Voltage Compliance BUFFER AMPLIFIER Input and Output Voltage Range Input Offset Voltage, RS = 25 k Input Bias Current Input Resistance Output Current Short-Circuit Current Output Resistance Small-Signal Bandwidth Slew Rate4 POWER SUPPLY Voltage Rated Performance Dual Supply Single Supply Quiescent Current Total VS, 5 V to 36 V, TMIN to TMAX TEMPERATURE RANGE Rated Performance Storage NUMBER OF TRANSISTORS Data Sheet Min 20 AD536AJ Typ 40 10 25 -VS to (+VS - 2.5 V) Max 20 30 -VS to (+VS - 2.5V) Min AD536AK Typ 40 10 25 -VS to (+VS - 2.5 V) 20 Max 20 30 -VS to (+VS - 2.5V) 0.5 20 108 4 60 (+5 mA, -130 A) 4 60 (+5 mA, -130 A) 1.2 0 -55 1 5 15 3.0 +5 2 +70 +150 65 0.5 1 5 15 4 60 20 0.5 1 5 20 30 Unit A/V rms % k V V 0.5 20 108 20 18 +36 40 10 25 -VS to (+VS - 2.5 V) Max mV nA (+5 mA, -130 A) 0.5 3.0 +5 20 AD536AS Typ -VS to (+VS - 2.5V) 0.5 20 108 20 Min 15 18 +36 1.2 0 -55 2 +70 +150 65 3.0 +5 1.2 -55 -55 65 Accuracy is specified for 0 V to 7 V rms, dc or 1 kHz sine wave input with the AD536A connected as in the figure referenced. Error vs. crest factor is specified as an additional error for 1 V rms rectangular pulse input, pulse width = 200 s. Input voltages are expressed in volts rms, and error is expressed as a percentage of the reading. 4 With 2 k external pull-down resistor. 1 2 3 Rev. F | Page 4 of 15 mA MHz V/s 18 +36 V V V 2 mA +125 +150 C C Data Sheet AD536A ABSOLUTE MAXIMUM RATINGS Stresses at or above those listed under Absolute Maximum Ratings may cause permanent damage to the product. This is a stress rating only; functional operation of the product at these or any other conditions above those indicated in the operational section of this specification is not implied. Operation beyond the maximum operating conditions for extended periods may affect product reliability. Table 2. Parameter Supply Voltage Dual Supply Single Supply Internal Power Dissipation Maximum Input Voltage Buffer Maximum Input Voltage Maximum Input Voltage Storage Temperature Range Operating Temperature Range AD536AJ/AD536AK AD536AS Lead Temperature (Soldering, 60 sec) ESD Rating Thermal Resistance JA1 10-Pin Header (H-10 Package) 20-Terminal LCC (E-20 Package) 14-Lead SBDIP (D-14 Package) 14-Lead CERDIP (Q-14 Package) 18 V +36 V 500 mW 25 V peak VS 25 V peak -55C to +150C ESD CAUTION 0C to +70C -55C to +125C 300C 1000 V 150C/W 95C/W 95C/W 95C/W JA is specified for the worst-case conditions, that is, a device soldered in a circuit board for surface-mount packages. 0.1315 (3.340) COM 10 +VS 14 RL 9 IOUT 8 0.0807 (2.050) VIN 1A1 VIN 1B1 BUF IN 7 -VS CAV dB BUF OUT 3 4 5 6 PAD NUMBERS CORRESPOND TO PIN NUMBERS FOR THE TO-100 14-LEAD CERAMIC DIP PACKAGE. 1BOTH PADS SHOWN MUST BE CONNECTED TO V . IN THE AD536A IS AVAILABLE IN LASER-TRIMMED CHIP FORM. SUBSTRATE CONNECTED TO -VS. Figure 2. Die Dimensions and Pad Layout Dimensions shown in inches and (millimeters) Rev. F | Page 5 of 15 00504-002 1 Rating AD536A Data Sheet PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS VIN 1 14 +VS NC 2 13 NC 12 NC -VS 3 AD536A TOP VIEW 11 NC (Not to Scale) 10 COM dB 5 BUF OUT 6 9 RL BUF IN 7 8 IOUT NC = NO CONNECT 00504-003 CAV 4 Figure 3. D-14 and Q-14 Packages Pin Configuration Table 3. D-14 and Q-14 Packages Pin Function Descriptions Pin No. 1 2 3 4 5 6 7 8 9 10 11 12 13 14 Mnemonic VIN NC -VS CAV dB BUF OUT BUF IN IOUT RL COM NC NC NC +VS Description Input Voltage No Connection Negative Supply Voltage Averaging Capacitor Log (dB) Value of the RMS Output Voltage Buffer Output Buffer Input RMS Output Current Load Resistor Common No Connection No Connection No Connection Positive Supply Voltage IOUT BUF IN 10 1 COM 2 9 AD536A TOP VIEW (Not to Scale) +VS 3 BUF OUT 7 dB 6 4 VIN 8 5 CAV -VS 00504-004 RL Figure 4. H-10 Package Pin Configuration Table 4. H-10 Package Pin Function Descriptions Pin No. 1 2 3 4 5 6 7 8 9 10 Mnemonic RL COM +VS VIN -VS CAV dB BUF OUT BUF IN IOUT Description Load Resistor Common Positive Supply Voltage Input Voltage Negative Supply Voltage Averaging Capacitor Log (dB) Value of the RMS Output Voltage Buffer Output Buffer Input RMS Output Current Rev. F | Page 6 of 15 1 20 19 -VS 4 18 NC NC 5 AD536A 17 NC CAV 6 TOP VIEW (Not to Scale) 16 NC NC 7 12 13 RL BUF IN 11 NC 10 IOUT 9 BUF OUT dB 8 15 NC 14 COM NC = NO CONNECT 00504-005 NC 2 NC 3 +VS NC AD536A VIN Data Sheet Figure 5. E-20 Package Pin Configuration Table 5. E-20 Package Pin Function Descriptions Pin No. 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 Mnemonic NC VIN NC -VS NC CAV NC dB BUF OUT BUF IN NC IOUT RL COM NC NC NC NC NC +VS Description No Connection Input Voltage No Connection Negative Supply Voltage No Connection Averaging Capacitor No Connection Log (dB) Value of the RMS Output Voltage Buffer Output Buffer Input No Connection RMS Output Current Load Resistor Common No Connection No Connection No Connection No Connection No Connection Positive Supply Voltage Rev. F | Page 7 of 15 AD536A Data Sheet THEORY OF OPERATION The AD536A embodies an implicit solution of the rms equation that overcomes the dynamic range as well as other limitations inherent in a straightforward computation of rms. The actual computation performed by the AD536A follows the equation V 2 V rms = Avg IN V rms VOUT = 2R2 x I rms = VIN rms Figure 6 is a simplified schematic of the AD536A. Note that it is subdivided into four major sections: absolute value circuit (active rectifier), squarer/divider, current mirror, and buffer amplifier. The input voltage (VIN), which can be ac or dc, is converted to a unipolar current (I1) by the active rectifiers (A1, A2). I1 drives one input of the squarer/divider, which has the transfer function I4 = I /I3 2 I The output current, I4, of the squarer/divider drives the current mirror through a low-pass filter formed by R1 and the externally connected capacitor, CAV. If the R1 CAV time constant is much greater than the longest period of the input signal, then I4 is effectively averaged. The current mirror returns a current I3, which equals Avg[I4], back to the squarer/divider to complete the implicit rms computation. Thus, CURRENT MIRROR 14 +VS 10 COM I3 4 A3 I2 I1 VIN Q3 Q2 A1 12k Q4 9 R2 25k RL 25k ONE-QUADRANT SQUARER/DIVIDER NOTES 1. PINOUTS ARE FOR 14-LEAD DIP. Figure 6. Simplified Schematic 80k CONNECTIONS FOR dB OPERATION The logarithmic (or decibel) output of the AD536A is one of its most powerful features. The internal circuit computing dB works accurately over a 60 dB range. The connections for dB measurements are shown in Figure 7. Select the 0 dB level by adjusting R1 for the proper 0 dB reference current (which is set to cancel the log output current from the squarer/divider at the desired 0 dB point). The external op amp provides a more convenient scale and allows compensation of the +0.33%/C scale factor drift of the dB output pin. 5 For dB calibration, 6 1. 2. 3. 4. Q5 A2 12k 8 IOUT BUF IN BUFFER dB OUT 7 A4 Q1 |VIN|R-1 1 R3 25k R1 0.4mA 25k FS BUF OUT 3 -VS 00504-106 0.2mA FS ABSOLUTE VALUE; VOLTAGE-CURRENT CONVERTER The dB output is derived from the emitter of Q3 because the voltage at this point is proportional to -log VIN. The emitter follower, Q5, buffers and level shifts this voltage so that the dB output voltage is zero when the externally supplied emitter current (IREF) to Q5 approximates I3. The temperature-compensating resistor, R2, is available online in several styles from Precision Resistor Company, Inc., (Part Number AT35 and Part Number ST35). The average temperature coefficients of R2 and R3 result in the +3300 ppm required to compensate for the dB output. The linear rms output is available at Pin 8 on the DIP or Pin 10 on the header device with an output impedance of 25 k. Some applications require an additional buffer amplifier if this output is desired. I4 = Avg[II2/I4] = II rms R4 50k The current mirror also produces the output current, IOUT, which equals 2I4. IOUT can be used directly or can be converted to a voltage with R2 and buffered by A4 to provide a low impedance voltage output. The transfer function of the AD536A results in the following: Set VIN = 1.00 V dc or 1.00 V rms. Adjust R1 for dB output = 0.00 V. Set VIN = +0.1 V dc or 0.10 V rms. Adjust R5 for dB output = -2.00 V. Any other desired 0 dB reference level can be used by setting VIN and adjusting R1 accordingly. Note that adjusting R5 for the proper gain automatically provides the correct temperature compensation. Rev. F | Page 8 of 15 Data Sheet AD536A VIN NC 2 -VS -VS + C1, CAV +VS C2 CAV dB 0.1F BUF OUT dB OUT 3mV/dB BUF IN ABSOLUTE VALUE 1 14 AD536A 12 NC 11 NC 4 CURRENT MIRROR 5 10 9 6 COM RL 25k 8 BUF 7 +VS 4.6V TO 18V +E 13 NC SQUARER/ DIVIDER 3 +VS IOUT EOUT AD580J 2.5V -E R1 500k 0dB REF ADJUST R4 33.2k dB SCALE FACTOR ADJUST +VS R6 24.9k LINEAR rms OUTPUT R5 5k 7 2 R3 60.4 OP77 3 6 TEMPERATURE COMPENSATED dB OUTPUT +100mV/dB 4 R21 1k 00504-107 -VS 1SPECIAL TC COMPENSATION RESISTOR, +3300ppm/C, PRECISION RESISTOR COMPANY PART NUMBER AT 35 OR PART NUMBER ST35. Figure 7. dB Connection FREQUENCY RESPONSE The AD536A utilizes a logarithmic circuit in performing the implicit rms computation. As with any log circuit, bandwidth is proportional to signal level. The solid lines in the graph of Figure 8 represent the frequency response of the AD536A at input levels from 10 mV rms to 7 V rms. The dashed lines indicate the upper frequency limits for 1%, 10%, and 3 dB of reading additional error. For example, note that a 1 V rms signal produces less than 1% of reading additional error up to 120 kHz. A 10 mV signal can be measured with 1% of reading additional error (100 V) up to only 5 kHz. Figure 9 illustrates a curve of reading error for the AD536A for a 1 V rms input signal with crest factors from 1 to 11. A rectangular pulse train (pulse width = 100 s) was used for this test because it is the worst-case waveform for rms measurement (all of the energy is contained in the peaks). The duty cycle and peak amplitude were varied to produce crest factors from 1 to 11 while maintaining a constant 1 V rms input amplitude. T O 0 = DUTY CYCLE = CF = 1/ IN (rms) = 1 V rms VP 100s T 100s 1 VOUT (V) 10% 3dB 1V rms INPUT 0.1 100mV rms INPUT 0.01 1k 10k 100k FREQUENCY (Hz) 1M 10M 00504-016 10mV rms INPUT 0 -1 -2 -3 -4 1 2 3 4 Figure 8. High Frequency Response 5 6 7 CREST FACTOR 8 9 10 Figure 9. Error vs. Crest Factor Crest factor is often overlooked when determining the accuracy of an ac measurement. The definition of crest factor is the ratio of the peak signal amplitude to the rms value of the signal (CF = VP/V rms). Most common waveforms, such as sine and triangle waves, have relatively low crest factors (<2). Waveforms that resemble low duty cycle pulse trains, such as those occurring in switching power supplies and SCR circuits, have high crest factors. For example, a rectangular pulse train with a 1% duty cycle has a crest factor of 10 (CF = 1n). Rev. F | Page 9 of 15 INCREASE IN ERROR (% OF READING) AC MEASUREMENT ACCURACY AND CREST FACTOR 10 1V rms CF = 10 1 0.1 1s 1V rms CF = 3 10s 100s PULSE WIDTH (s) 1000s Figure 10. Error vs. Pulse Width Rectangular Pulse 11 00504-017 1% 1 00504-018 7V rms INPUT INCREASE IN ERROR (% of Reading) 10 AD536A Data Sheet 25 PEAK INPUT OR OUTPUT (V) 20 VIN 15 10 VOUT 5 20 VIN 15 VOUT 10 5 0 6 10 16 VOLTS (DUAL SUPPLY) 18 0 5 10 20 30 VOLTS (SINGLE SUPPLY) Figure 12. Input and Output Voltage Ranges vs. Single Supply Figure 11. Input and Output Voltage Ranges vs. Dual Supply Rev. F | Page 10 of 15 00504-022 2.5 00504-019 PEAK INPUT OR OUTPUT (V) 25 Data Sheet AD536A APPLICATIONS INFORMATION NC The AD536A is simple to connect to for the majority of high accuracy rms measurements, requiring only an external capacitor to set the averaging time constant. The standard connection is shown in Figure 13 through Figure 15. In this configuration, the AD536A measures the rms of the ac and dc levels present at the input, but shows an error for low frequency input as a function of the filter capacitor, CAV, as shown in Figure 19. Thus, if a 4 F capacitor is used, the additional average error at 10 Hz is 0.1%; at 3 Hz, the additional average error is 1%. CAV AD536A 1 NC 2 -VS -VS 3 dB 5 BUF OUT SQUARER/ DIVIDER CURRENT MIRROR 6 7 BUF IN 13 NC 12 NC 11 NC COM 9 RL 8 IOUT Figure 13. 14-Lead Standard RMS Connection IOUT RL BUF IN 25k AD536A CURRENT MIRROR +VS BUF BUF OUT VOUT SQUARER/ DIVIDER +VS VIN CAV -VS NC 2 1 NC 20 19 ABSOLUTE VALUE 4 AD536A SQUARER/ DIVIDER 6 CURRENT MIRROR 10 11 NC 9 BUF IN VOUT 25k BUF dB 8 12 13 RL 7 IOUT NC 18 NC 17 NC 16 NC 15 NC COM 14 Figure 15. 20-Terminal Standard RMS Connection The input and output signal ranges are a function of the supply voltages; these ranges are shown in Figure 11 and Figure 12. The AD536A can also be used in an unbuffered voltage output mode by disconnecting the input to the buffer. The output then appears unbuffered across the 25 k resistor. The buffer amplifier can then be used for other purposes. Further, the AD536A can be used in a current output mode by disconnecting the 25 k resistor from ground. The output current is available at Pin 8 (IOUT, Pin 10 on the H-10 package) with a nominal scale of 40 A per V rms input positive output. The accuracy and offset voltage of the AD536A is adjustable with external trims, as shown in Figure 16. R4 trims the offset. Note that the offset trim circuit adds 365 in series with the internal 25 k resistor. This causes a 1.5% increase in scale factor, which is compensated for by R1. The scale factor adjustment range is 1.5%. The trimming procedure is as follows: 1. 2. CAV -VS NC 5 CAV dB ABSOLUTE VALUE 00504-020 COM -VS +VS OPTIONAL EXTERNAL TRIMS FOR HIGH ACCURACY 10 25k BUF +VS 14 4 CAV VOUT +VS ABSOLUTE VALUE 00504-006 VIN 3 BUF OUT The accuracy at higher frequencies is according to specification. To reject the dc input, add a capacitor in series with the input, as shown in Figure 17. Note that the capacitor must be nonpolar. If the AD536A supply rails contain a considerable amount of high frequency ripple, it is advisable to bypass both supply pins to ground with 0.1 F ceramic capacitors, located as close to the device as possible. VIN VIN CAV 00504-021 TYPICAL CONNECTIONS 3. Figure 14. 10-Pin Standard RMS Connection Ground the input signal, VIN, and adjust R4 to provide 0 V output from Pin 6. Alternatively, adjust R4 to provide the correct output with the lowest expected value of VIN. Connect the desired full-scale input level to VIN, either dc or a calibrated ac signal (1 kHz is the optimum frequency). Trim R1 to provide the correct output at Pin 6. For example, 1.000 V dc input provides 1.000 V dc output. A 1.000 V peak-to-peak sine wave should provide a 0.707 V dc output. Any residual errors are caused by device nonlinearity. The major advantage of external trimming is to optimize device performance for a reduced signal range; the AD536A is internally trimmed for a 7 V rms full-scale range. Rev. F | Page 11 of 15 AD536A Data Sheet CAV CHOOSING THE AVERAGING TIME CONSTANT SCALE FACTOR ADJUST VIN ABSOLUTE VALUE 1 R1 500k NC 2 -VS -VS CAV AD536A 11 NC CURRENT MIRROR dB 5 BUF OUT VOUT BUF IN 6 10 25k BUF 7 +VS R4 OFFSET 50k ADJUST 12 NC 4 9 8 -VS COM R3 750k RL R2 365k At higher frequencies, the average output of the AD536A approaches the rms value of the input signal. The actual output of the AD536A differs from the ideal output by a dc (or average) error and some amount of ripple, as shown in Figure 18. EO IDEAL EO IOUT 00504-007 25k The AD536A computes the rms of both ac and dc signals. If the input is a slowly varying dc signal, the output of the AD536A tracks the input exactly. +VS 13 NC SQUARER/ DIVIDER 3 14 +VS DC ERROR = EO - EO (IDEAL) Figure 16. Optional External Gain and Output Offset Trims Refer to Figure 17 for single supply-rail configurations between 5 V and 36 V. When powered from a single supply, the input stage (VIN pin) is internally biased at a voltage between ground and the supply, and the input signal ac coupled. Biasing the device between the supply and ground is simply a matter of connecting the COM pin to an external resistor divider and bypassing to ground. The resistor values are large, minimizing power consumption, as the COM pin current is only 5 A. Note that the 10 k and 20 k resistors connected to the COM pin (Figure 17) are asymmetrical, that is, the voltage at the COM pin is 1/3 of the supply. This ratio of input bias to supply is optimum for the precision rectifier (aka absolute value circuit) input circuit employed for rectifying ac input waveforms and ensures full input symmetry for low signal voltages. Capacitor C2 is required for AC input coupling, however an external dc return is unnecessary because biasing occurs internally. SelectC2 for the desired low frequency breakpoint using an input resistance of 16.7 k for the 1/RC calculation; C2 = 1 F for a cutoff at 10 Hz. Figure 11 and Figure 12 show the input and output signal ranges for dual and single supply configurations, respectively. The load resistor, RL, provides a path to sink output sink current when an input signal is disconnected. DOUBLE FREQUENCY RIPPLE TIME Figure 18. Typical Output Waveform for Sinusoidal Input The dc error is dependent on the input signal frequency and the value of CAV. Use Figure 19 to determine the minimum value of CAV, which yields a given percentage of dc error above a given frequency using the standard rms connection. The ac component of the output signal is the ripple. There are two ways to reduce the ripple. The first method involves using a large value of CAV. Because the ripple is inversely proportional to CAV, a tenfold increase in this capacitance affects a tenfold reduction in ripple. When measuring waveforms with high crest factors, such as low duty cycle pulse trains, the averaging time constant should be at least 10 times the signal period. For example, a 100 Hz pulse rate requires a 100 ms time constant, which corresponds to a 4 F capacitor (time constant = 25 ms per F). CAV VIN NONPOLARIZED VIN NC 2 -VS CAV dB VOUT BUF OUT RL BUF IN 10k TO 1k 1 3 ABSOLUTE VALUE AD536A +VS 13 NC SQUARER/ DIVIDER 12 NC +VS 0.1F 20k 11 NC 4 5 14 CURRENT MIRROR 6 10 9 COM RL 0.1F 25k 7 BUF 8 IOUT 10k 00504-008 C2 1F AVERAGE EO - EO 00504-009 SINGLE-SUPPLY OPERATION Figure 17. Single-Supply Connection Rev. F | Page 12 of 15 Data Sheet AD536A The primary disadvantage in using a large CAV to remove ripple is that the settling time for a step change in input level is increased proportionately. Figure 19 illustrates that the relationship between CAV and 1% settling time is 115 ms for each microfarad of CAV. The settling time is twice as great for decreasing signals as it is for increasing signals. The values in Figure 19 are for decreasing signals. Settling time also increases for low signal levels, as shown in Figure 20. % 01 0. 10 R R O R ER R 1 O R ER R VALUES FOR CAV AND 1% SETTLING TIME 0.1 FOR STATED % OF READING AVERAGING ERROR1 ACCURACY 20% DUE TO COMPONENT TOLERANCE 0.1 0.01 10 100 1k INPUT FREQUENCY (Hz) 10k VIN VIN -VS NC -VS CAV 2 3 dB BUF OUT BUF IN Figure 19. Error/Settling Time Graph for Use with the Standard RMS Connection (See Figure 13 Through Figure 15) + - ABSOLUTE VALUE AD536A 5 +VS 12 NC 11 NC CURRENT MIRROR 6 7 +VS 14 13 NC SQUARER/ DIVIDER 4 CAV 1PERCENT DC ERROR AND PERCENT RIPPLE (PEAK) SETTLING TIME RELATIVE TO 1V rms INPUT SETTLING TIME 1 25k 9 8 BUF Rx 24k C2 10 COM RL IOUT - C31 + 10.0 Vrms OUT 1FOR SINGLE POLE, SHORT Rx, REMOVE C3. Figure 21. Two-Pole Postfilter 5.0 2.5 1m 10m 100m 1 rms INPUT LEVEL (V) 10 00504-011 1.0 Figure 20. Settling Time vs. Input Level A better method to reduce output ripple is the use of a postfilter. Figure 21 shows a suggested circuit. If a single-pole filter is used (C3 removed, RX shorted) and C2 is approximately twice the value of CAV, the ripple is reduced, as shown in Figure 22, and settling time is increased. For example, with CAV = 1 F and C2 = 2.2 F, the ripple for a 60 Hz input is reduced from 10% of reading to approximately 0.3% of reading. Rev. F | Page 13 of 15 DC ERROR OR RIPPLE (% of Reading) 7.5 10 PEAK-TO-PEAK RIPPLE CAV = 1F PEAK-TO-PEAK RIPPLE (ONE POLE) CAV = 1F, C2 = 2.2F 1 Rx = 0 DC ERROR CAV = 1F (ALL FILTERS) PEAK-TO-PEAK RIPPLE CAV = 1F C2 = C3 = 2.2F (TWO-POLE) 0.1 10 100 1k 10k FREQUENCY (Hz) Figure 22. Performance Features of Various Filter Types (See Figure 13 to Figure 15 for Standard RMS Connection) 00504-013 1 0.01 100k For a more detailed explanation of these topics, refer to the RMS to DC Conversion Application Guide, 2nd Edition. 00504-010 O R ER 1% 1 % 10 REQUIRED CAV (F) O R ER 1% 0. 10 FOR 1% SETTLING TIME IN SECONDS MULTIPLY READING BY 0.115 100 The two-pole postfilter uses an active filter stage to provide even greater ripple reduction without substantially increasing the settling times over a circuit with a one-pole filter. The values of CAV, C2, and C3 can then be reduced to allow extremely fast settling times for a constant amount of ripple. Caution should be exercised in choosing the value of CAV, because the dc error is dependent on this value and is independent of the postfilter. 00504-012 100 The settling time, however, is increased by approximately a factor of 3. Therefore, the values of CAV and C2 can be reduced to permit faster settling times while still providing substantial ripple reduction. AD536A Data Sheet OUTLINE DIMENSIONS 0.005 (0.13) MIN 0.080 (2.03) MAX 8 14 1 PIN 1 0.310 (7.87) 0.220 (5.59) 7 0.100 (2.54) BSC 0.765 (19.43) MAX 0.200 (5.08) MAX 0.200 (5.08) 0.125 (3.18) 0.023 (0.58) 0.014 (0.36) 0.320 (8.13) 0.290 (7.37) 0.060 (1.52) 0.015 (0.38) 0.150 (3.81) MIN SEATING PLANE 0.070 (1.78) 0.030 (0.76) 0.015 (0.38) 0.008 (0.20) CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. \ Figure 23. 14-Lead Side-Brazed Ceramic Dual In-Line Package [SBDIP] (D-14) Dimensions shown in inches and (millimeters) 0.200 (5.08) REF 0.100 (2.54) REF 0.015 (0.38) MIN 0.075 (1.91) REF 0.095 (2.41) 0.075 (1.90) 19 18 0.358 (9.09) 0.342 (8.69) SQ 0.358 (9.09) MAX SQ 0.011 (0.28) 0.007 (0.18) R TYP 0.075 (1.91) REF 0.088 (2.24) 0.054 (1.37) 3 20 4 0.028 (0.71) 0.022 (0.56) 1 BOTTOM VIEW 0.050 (1.27) BSC 8 14 13 9 45 TYP 0.055 (1.40) 0.045 (1.14) 0.150 (3.81) BSC CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 24. 20-Terminal Ceramic Leadless Chip Carrier [LCC] (E-20-1) Dimensions shown in inches and (millimeters) 0.005 (0.13) MIN 14 1 PIN 1 0.098 (2.49) MAX 8 0.310 (7.87) 0.220 (5.59) 7 0.100 (2.54) BSC 0.785 (19.94) MAX 0.200 (5.08) MAX 0.200 (5.08) 0.125 (3.18) 0.023 (0.58) 0.014 (0.36) 0.320 (8.13) 0.290 (7.37) 0.060 (1.52) 0.015 (0.38) 0.150 (3.81) MIN SEATING 0.070 (1.78) PLANE 0.030 (0.76) 15 0 0.015 (0.38) 0.008 (0.20) CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 25. 14-Lead Ceramic Dual In-Line Package [CERDIP] (Q-14) Dimensions shown in inches and (millimeters) Rev. F | Page 14 of 15 022106-A 0.100 (2.54) 0.064 (1.63) Data Sheet AD536A REFERENCE PLANE 0.500 (12.70) MIN 0.185 (4.70) 0.165 (4.19) 0.160 (4.06) 0.110 (2.79) PIN 5 IS INTEGRAL CONNECTION TO HEADER 0.370 (9.40) 0.335 (8.51) 0.021 (0.53) 0.016 (0.40) 0.335 (8.51) 0.305 (7.75) 0.115 (2.92) BSC 6 8 4 9 3 2 0.040 (1.02) MAX BASE & SEATING PLANE 7 5 0.230 (5.84) BSC 10 1 0.045 (1.14) 0.025 (0.65) 0.034 (0.86) 0.025 (0.64) BOTTOM VIEW 36 BSC DIMENSIONS PER JEDEC STANDARDS MO-006-AF CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. 11-19-2013-A 0.050 (1.27) MAX Figure 26. 10-Pin Metal Header Package [TO-100] (H-10) Dimensions shown in inches and (millimeters) ORDERING GUIDE Model1 AD536AJD AD536AJDZ AD536AKD AD536AKDZ AD536AJH AD536AJHZ AD536AKH AD536AKHZ AD536AJQ AD536ASD AD536ASD/883B AD536ASE/883B AD536ASH AD536ASH/883B AD536ASCHIPS 5962-89805012A 5962-8980501CA 5962-8980501IA 1 Temperature Range 0C to +70C 0C to +70C 0C to +70C 0C to +70C 0C to +70C 0C to +70C 0C to +70C 0C to +70C 0C to +70C -55C to +125C -55C to +125C -55C to +125C -55C to +125C -55C to +125C -55C to +125C -55C to +125C -55C to +125C -55C to +125C Package Description 14-Lead Side-Brazed Ceramic Dual In-Line Package [SBDIP] 14-Lead Side-Brazed Ceramic Dual In-Line Package [SBDIP] 14-Lead Side-Brazed Ceramic Dual In-Line Package [SBDIP] 14-Lead Side-Brazed Ceramic Dual In-Line Package [SBDIP] 10-Pin Metal Header Package [TO-100] 10-Pin Metal Header Package [TO-100] 10-Pin Metal Header Package [TO-100] 10-Pin Metal Header Package [TO-100] 14-Lead Ceramic Dual In Line Package [CERDIP] 14-Lead Side-Brazed Ceramic Dual In-Line Package [SBDIP] 14-Lead Side-Brazed Ceramic Dual In-Line Package [SBDIP] 20-Terminal Ceramic Leadless Chip Carrier [LCC] 10-Pin Metal Header Package [TO-100] 10-Pin Metal Header Package [TO-100] Die 20-Terminal Ceramic Leadless Chip Carrier [LCC] 14-Lead Side-Brazed Ceramic Dual In-Line Package [SBDIP] 10-Pin Metal Header Package [TO-100] Z = RoHS Compliant Part. (c)1976-2014 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D00504-0-11/14(F) Rev. F | Page 15 of 15 Package Option D-14 D-14 D-14 D-14 H-10 H-10 H-10 H-10 Q-14 D-14 D-14 E-20-1 H-10 H-10 E-20-1 D-14 H-10 Mouser Electronics Authorized Distributor Click to View Pricing, Inventory, Delivery & Lifecycle Information: Analog Devices Inc.: 5962-8980501CA AD536AKDZ AD536ASE/883B AD536AJDZ AD536ASH AD536ASD AD536AJD AD536AJHZ AD536ASH/883B AD536AKHZ 5962-89805012A AD536ASD/883B 5962-8980501IA AD536AKD AD536AJH AD536AKH AD536AJQ