LTC5598IUF#TRPBF - Linear Technology

LTC5598

5598f

TYPICAL APPLICATION

DESCRIPTION

5MHz to 1600MHz

High Linearity Direct

Quadrature Modulator

The LTC

5598 is a direct I/Q modulator designed for high

performance wireless applications, including wireless

infrastructure. It allows direct modulation of an RF signal

using differential baseband I and Q signals. It supports

point-to-point microwave link, GSM, EDGE, CDMA,

700MHz band LTE, CDMA2000, CATV applications and

other systems. It may also be conﬁ gured as an image

reject upconverting mixer, by applying 90° phase-shifted

signals to the I and Q inputs.

The I/Q baseband inputs consist of voltage-to-current

converters that in turn drive double-balanced mixers.

The outputs of these mixers are summed and applied

to a buffer, which converts the differential mixer signals

to a 50Ω single-ended buffered RF output. The four

balanced I and Q baseband input ports are intended for

DC coupling from a source with a common-mode voltage

level of about 0.5V. The LO path consists of an LO buffer

with single-ended or differential inputs, and precision

quadrature generators that produce the LO drive for the

mixers. The supply voltage range is 4.5V to 5.25V, with

about 168mA current.

5MHz to 1600MHz Direct Conversion Transmitter Application

L, LT, LTC and LTM are registered trademarks of Linear Technology Corporation.

All other trademarks are the property of their respective owners.

FEATURES

APPLICATIONS

n Frequency Range: 5MHz to 1600MHz

n High Output IP3: +27.7dBm at 140MHz

+22.9dBm at 900MHz

n Low Output Noise Floor at 6MHz Offset:

No Baseband AC Input: –161.2dBm/Hz

OUT = 5.5dBm: –160dBm/Hz

n Low LO Feedthrough: –55dBm at 140MHz

n High Image Rejection: –50.4dBc at 140MHz

n Integrated LO Buffer and LO Quadrature Phase

Generator

n 50Ω Single-Ended LO and RF Ports

n >400MHz Baseband Bandwidth

n 24-Lead QFN 4mm × 4mm Package

n Pin-Compatible with Industry Standard Pin-Out

n Shut-down Mode

n Point-to-Point Microwave Link

n Military Radio

n Basestation Transmitter GSM/EDGE/CDMA2K

n 700MHz LTE Basestation Transmitter

n Satellite Communication

n CATV/Cable Broadband Modulator

n 13.56MHz/UHF RFID Modulator

90o

LTC5598

10nF

50Ω 10nF 470nF

10nF

BASEBAND

GENERATOR

RF = 5MHz

TO 1600MHz

1nF

4.7μF

V-I

I-CHANNEL

Q-CHANNEL

VCC

5598 TA01

I-DAC

Q-DAC

VCO/SYNTHESIZER RF OUTPUT POWER (dBm)

NOISE FLOOR AT 6MHz OFFSET (dBm/Hz)

–152

–154

–156

–158

–160

–162

5598 TA02

8246–4 –2 0–12 –10 –8 –6–14

fLO = 140MHz; fBB = 2kHz; CW (NOTE 3)

20dBm

19.3dBm

13.4dBm

10.4dBm

8.4dBm

6.4dBm

Noise Floor vs RF Output Power

and Differential LO Input Power

LTC5598

5598f

PIN CONFIGURATION ABSOLUTE MAXIMUM RATINGS

Supply Voltage .........................................................5.6V

Common Mode Level of BBPI, BBMI and

BBPQ, BBMQ ...........................................................0.6V

LOP, LOM Input ....................................................20dBm

Voltage on Any Pin

Not to Exceed ...................................–0.3V to VCC + 0.3V

TJMAX .................................................................... 150°C

Operating Temperature Range..................–40°C to 85°C

Storage Temperature Range ...................–65°C to 150°C

(Note 1)

24 23 22 21 20 19

7 8 9

TOP VIEW

UF PACKAGE

24-LEAD (4mm s 4mm) PLASTIC QFN

10 11 12

325

GND

LOP

LOM

GND

CAPA

VCC2

GNDRF

VCC1

GND

BBMI

BBPI

GND

CAPB

GND

BBMQ

BBPQ

GND

TJMAX = 150°C, θJA = 37°C/W

EXPOSED PAD (PIN 25) IS GND, MUST BE SOLDERED TO PCB

ORDER INFORMATION

LEAD FREE FINISH TAPE AND REEL PART MARKING PACKAGE DESCRIPTION TEMPERATURE RANGE

LTC5598IUF#PBF LTC5598IUF#TRPBF 5598 24-Lead (4mm × 4mm) Plastic QFN –40°C to 85°C

Consult LTC Marketing for parts speciﬁ ed with wider operating temperature ranges.

Consult LTC Marketing for information on non-standard lead based ﬁ nish parts.

For more information on lead free part marking, go to: http://www.linear.com/leadfree/

For more information on tape and reel speciﬁ

cations, go to: http://www.linear.com/tapeandreel/

LTC5598

5598f

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

RF OUTPUT (RF)

fRF RF Frequency Range 5 to 1600 MHz

S22, ON RF Output Return Loss EN = High, 5MHz to 1600MHz <–20 dB

fLO = 140MHz, fRF = 139.9MHz

GVConversion Voltage Gain 20 • Log (VRF, OUT, 50Ω/VIN, DIFF, I or Q)–2dB

POUT Absolute Output Power 1VPP,DIFF on each I&Q Inputs 2 dBm

OP1dB Output 1dB Compression 8.5 dBm

OIP2 Output 2nd Order Intercept (Notes 4, 5) 74 dBm

OIP3 Output 3rd Order Intercept (Notes 4, 6) 27.7 dBm

NFloor RF Output Noise Floor No Baseband AC Input Signal (Note 3)

POUT = 4.6dBm (Note 3) PLO, SE = 10dBm

POUT = 5.5dBm (Note 3) PLO, DIFF = 20dBm

–161.2

–154.5

–160

dBm/Hz

IR Image Rejection (Note 7) –50.4 dBc

LOFT LO Feedthrough

(Carrier Leakage)

EN = High (Note 7)

EN = Low (Note 7)

–55

–78

dBm

fLO = 450MHz, fRF = 449.9MHz

GVConversion Voltage Gain 20 • Log (VRF, OUT, 50Ω/VIN, DIFF, I or Q) –5.0 –2.1 0.5 dB

POUT Absolute Output Power 1VPP,DIFF on each I&Q Inputs 1.9 dBm

OP1dB Output 1dB Compression 8.4 dBm

OIP2 Output 2nd Order Intercept (Notes 4, 5) 72 dBm

OIP3 Output 3rd Order Intercept (Notes 4, 6) 25.5 dBm

NFloor RF Output Noise Floor No Baseband AC Input Signal (Note 3) –160.9 dBm/Hz

IR Image Rejection (Note 7) –55 dBc

LOFT LO Feedthrough

(Carrier Leakage)

EN = High (Note 7)

EN = Low (Note 7)

–51

–68

dBm

fLO = 900MHz, fRF = 899.9MHz

GVConversion Voltage Gain 20 • Log (VRF, OUT, 50Ω/VIN, DIFF, I or Q)–2dB

POUT Absolute Output Power 1VPP,DIFF on each I&Q Inputs 2 dBm

OP1dB Output 1dB Compression 8.5 dBm

OIP2 Output 2nd Order Intercept (Notes 4, 5) 69 dBm

OIP3 Output 3rd Order Intercept (Notes 4, 6) 22.9 dBm

NFloor RF Output Noise Floor No Baseband AC Input Signal (Note 3)

POUT = 5.2dBm (Note 3) PLO, SE = 10dBm

–160.3

–154.5

dBm/Hz

IR Image Rejection (Note 7) –54 dBc

LOFT LO Feedthrough

(Carrier Leakage)

EN = High (Note 7)

EN = Low (Note 7)

–48

–54

dBm

ELECTRICAL CHARACTERISTICS

CC = 5V, EN = 5V, TA = 25ºC, PLO = 0dBm, single-ended; BBPI, BBMI,

BBPQ, BBMQ common-mode DC voltage VCMBB = 0.5VDC, I&Q baseband input signal = 100kHz CW, 0.8VPP,DIFF each, I&Q 90° shifted

(lower side-band selection), unless otherwise noted. (Note 11)

LTC5598

5598f

ELECTRICAL CHARACTERISTICS

CC = 5V, EN = 5V, TA = 25ºC, PLO = 0dBm, single-ended; BBPI, BBMI,

BBPQ, BBMQ common-mode DC voltage VCMBB = 0.5VDC, I&Q baseband input signal = 100kHz CW, 0.8VPP,DIFF each, I&Q 90° shifted

(lower side-band selection), unless otherwise noted. (Note 11)

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

LO INPUT (LOP)

fLO LO Frequency Range 5 to 1600 MHz

PLO,DIFF Differential LO Input Power Range –10 to 20 dBm

PLO, SE Single-Ended LO Input Power Range –10 to 12 dBm

S11, ON LO Input Return Loss EN = High –10.5 dB

S11, OFF LO Input Return Loss EN = Low –9.6 dB

BASEBAND INPUTS (BBPI, BBMI, BBPQ, BBMQ)

BWBB Baseband Bandwidth -3dB Bandwidth >400 MHz

Ib,BB Baseband Input Current Single-Ended –68 μA

RIN, SE Input Resistance Single-Ended –7.4 kΩ

VCMBB DC Common-Mode Voltage Externally Applied 0.5 V

VSWING Amplitude Swing No Hard Clipping, Single-Ended 0.86 VP-P

POWER SUPPLY (VCC1, VCC2)

VCC Supply Voltage 4.5 5 5.25 V

ICC(ON) Supply Current EN = High, ICC1+ ICC2 130 165 200 mA

ICC(OFF) Supply Current, Sleep Mode EN = 0V, ICC1+ ICC2 0.24 0.9 mA

tON Turn-On Time EN = Low to High (Notes 8, 10) 75 ns

tOFF Turn-Off Time EN = High to Low (Notes 9, 10) 10 ns

POWER UP/DOWN

Enable Input High Voltage

Input High Current

EN = High

EN = 5V

μA

Sleep Input Low Voltage

Input Low Current

EN = Low

EN = 0V –40

μA

Note 1: Stresses beyond those listed under Absolute Maximum Ratings

may cause permanent damage to the device. Exposure to any Absolute

Maximum Rating condition for extended periods may affect device

reliability and lifetime.

Note 2: The LTC5598 is guaranteed functional over the operating

temperature range –40ºC to 85ºC.

Note 3: At 6MHz offset from the LO signal frequency. 100nF between BBPI

and BBMI, 100nF between BBPQ and BBMQ.

Note 4: Baseband is driven by 2MHz and 2.1MHz tones with 1VPP,DIFF for

two-tone signals at each I or Q input (0.5VPP,DIFF for each tone).

Note 5: IM2 is measured at LO frequency – 4.1MHz.

Note 6: IM3 is measured at LO frequency – 1.9 MHz and LO frequency

– 2.2MHz.

Note 7: Amplitude average of the characterization data set without image

or LO feedthrough nulling (unadjusted).

Note 8: RF power is within 10% of ﬁ nal value.

Note 9: RF power is at least 30dB lower than in the ON state.

Note 10: External coupling capacitors at pins LOP, LOM and RF are 100pF

each.

Note 11: Tests are performed as shown in the conﬁ guration of Figure 10.

The LO power is applied to J3 while J5 is terminated with 50Ω to ground

for single-ended LO drive.

LTC5598

5598f

TYPICAL PERFORMANCE CHARACTERISTICS

TEMPERATURE (°C)

–40

140

SUPPLY CURRENT (mA)

170

160

150

180

85–15 10 35

5598 G01

5.25V

5.0V

4.5V

Output IP2 vs RF Frequency

Output 1dB Compression

vs RF Frequency

LO Feedthrough to RF Output

vs LO Frequency

Image Rejection vs LO Frequency

Noise Floor vs RF Frequency

(No AC Baseband Input Signal)

Supply Current vs Temperature Voltage Gain vs RF Frequency Output IP3 vs RF Frequency

VCC = 5V, EN = 5V, TA = 25ºC, fRF = fLO – fBB, PLO =

0dBm single-ended, BBPI, BBMI, BBPQ, BBMQ common-mode DC voltage VCMBB = 0.5VDC, I&Q baseband input signal = 100kHz,

0.8VPP,DIFF, two-tone baseband input signal = 2MHz, 2.1MHz, 0.5VPP,DIFF each tone, I&Q 90° shifted (lower side-band selection);

fNOISE = fLO – 6MHz; unless otherwise noted. (Note 11)

RF Two-Tone Power (Each Tone),

IM2 and IM3 vs RF Frequency

RF FREQUENCY (MHz)

VOLTAGE GAIN (dB)

–1

–3

–2

–4

–5 1000

5598 G02

10010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

RF FREQUENCY (MHz)

OIP3 (dBm)

17 1000

5598 G03

10010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

RF FREQUENCY (MHz)

OIP2 (dBm)

5598 G04

100 100010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

RF FREQUENCY (MHz)

OP1dB (dBm)

5598 G05

100 100010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

LO FREQUENCY (MHz)

LO FEEDTHROUGH (dBm)

–40

–50

–60

–70

5598 G06

100 100010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

LO FREQUENCY (MHz)

IMAGE REJECTION (dBc)

–20

–30

–40

–50

–60

–70

5598 G07

100 100010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

RF FREQUENCY (MHz)

NOISE FLOOR (dBm/Hz)

–145

–155

–150

–160

–165

5598 G08

100 100010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

(NOTE 3)

RF FREQUENCY (MHz)

PRF,TONE (dBm)

IM2 (dBm), IM3 (dBm)

–50

–40

–30

–20

–10

–60

–40

–90

–80

–70

–60

–50

–100

5598 G09

100010010

fRF, EACH = fLO – fBB1

fIM3 = fLO + 2*fBB1 +f

BB2

fIM3 = fLO – 2*fBB1 +f

BB2

fIM2 = fLO – fBB1 –f

BB2

LTC5598

5598f

LO Feedthrough to RF Output

vs LO Frequency (PLO = 10dBm)

Image Rejection vs LO Frequency

(PLO = 10dBm)

RF Two-Tone Power (Each Tone),

IM2 and IM3 vs RF Frequency

(PLO = 10dBm)

Output IP3 vs RF Frequency

(PLO = 10dBm)

Output IP2 vs RF Frequency

(PLO = 10dBm)

Output 1dB Compression

vs RF Frequency (PLO = 10dBm)

TYPICAL PERFORMANCE CHARACTERISTICS

VCC = 5V, EN = 5V, TA = 25ºC, fRF = fLO – fBB, PLO =

0dBm single-ended, BBPI, BBMI, BBPQ, BBMQ common-mode DC voltage VCMBB = 0.5VDC, I&Q baseband input signal = 100kHz,

0.8VPP,DIFF, two-tone baseband input signal = 2MHz, 2.1MHz, 0.5VPP,DIFF each tone, I&Q 90° shifted (lower side-band selection);

fNOISE = fLO – 6MHz; unless otherwise noted. (Note 11)

Voltage Gain vs RF Frequency

(PLO = 10dBm)

RF Two-Tone Power (Each Tone),

IM2 and IM3 vs Baseband Voltage

and Temperature (fLO = 140MHz)

RF Two-Tone Power (Each Tone),

IM2 and IM3 vs Baseband Voltage

and Temperature (fLO = 900MHz)

fRF, EACH = fLO –fBB1

fIM3 = fLO – 2*fBB1 +f

BB2

fIM3 = fLO + 2*fBB1 +f

BB2

fIM2 = fLO – fBB1 –f

BB2

I AND Q BASEBAND VOLTAGE (VPP, DIFF, EACH TONE)

0.1

PRF, TONE (dBm)

–40

–30

–20

–10

–50

–30

–80

–70

–60

–50

–40

–90

5598 G10

IM2 (dBm), IM3 (dBm)

I AND Q BASEBAND VOLTAGE (VPP, DIFF, EACH TONE)

0.1

PRF,TONE (dBm)

IM2 (dBm), IM3 (dBm)

–40

–30

–20

–10

–50

–30

–80

–70

–60

–50

–40

–90

5598 G11

fRF, EACH = fLO – fBB1

fIM3 = fLO + 2*fBB1 +f

BB2

fIM3 = fLO – 2*fBB1 +f

BB2

fIM2 = fLO – fBB1 –f

BB2

RF FREQUENCY (MHz)

VOLTAGE GAIN (dB)

–1

–4

–3

–2

–5

5598 G12

100010010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

PLO = 10dBm

RF FREQUENCY (MHz)

OIP3 (dBm)

5598 G13

100010010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

RF FREQUENCY (MHz)

OIP2 (dBm)

5598 G14

100010010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

RF FREQUENCY (MHz)

OP1dB (dBm)

5598 G15

100010010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

LO FREQUENCY (MHz)

LO FEEDTHROUGH (dBm)

–40

–50

–60

–70

5598 G16

100010010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

LO FREQUENCY (MHz)

IMAGE REJECTION (dBc)

–20

–30

–40

–50

–60

–70

5598 G17

100010010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

RF FREQUENCY (MHz)

PRF, TONE (dBm)

IM2 (dBm), IM3 (dBm)

–60

–40

–100

5598 G18

100010010

fRF, EACH = fLO – fBB1

fIM3 = fLO – 2*fBB1 +f

BB2

fIM3 = fLO + 2*fBB1 +f

BB2

fIM2 = fLO – fBB1 –f

BB2

LTC5598

5598f

Noise Floor vs RF Frequency

(PLO = 10dBm, No AC Baseband

Input Signal)

Image Rejection DistributionLO Feedthrough Distribution

Gain Distribution

LO Feedthrough to RF Output

vs LO Frequency for EN = Low

Output IP3 Distribution at 25°C

TYPICAL PERFORMANCE CHARACTERISTICS

VCC = 5V, EN = 5V, TA = 25ºC, fRF = fLO – fBB, fLO =

450MHz, PLO = 0dBm single-ended, BBPI, BBMI, BBPQ, BBMQ common-mode DC voltage VCMBB = 0.5VDC, I&Q baseband input signal

= 100kHz, 0.8VPP,DIFF, two-tone baseband input signal = 2MHz, 2.1MHz, 0.5VPP,DIFF each tone, I&Q 90° shifted (lower side-band

selection); fNOISE = fLO – 6MHz; unless otherwise noted. (Note 11)

RF FREQUENCY (MHz)

NOISE FLOOR (dBm/Hz)

–145

–150

–155

–160

–165

5598 G19

100010010

5V, 25°C

5.25V, 25°C

4.5V, 25°C

5V, –40°C

5V, 85°C

(NOTE 3)

LO FREQUENCY (MHz)

LO FEEDTHROUGH (dBm)

–40

–80

–60

–100

–120

–140

5598 G20

100010010

PLO = 10dBm

PLO = 0dBm

–40°C

85°C

GAIN (dB)

PERCENTAGE (%)

5598 G21

–1.9–2–2.2 –2.1–2.3–2.4

85oC

25oC

–40oC

OIP3 (dBm)

PERCENTAGE (%)

5598 G22

26.8 27.225.6 26 26.424.8 25.224.424

LO FEEDTHROUGH (dBm)

PERCENTAGE (%)

5598 G23

–42 –38–54 –50 –46–62 –58–66–70

85oC

25oC

–40oC

IMAGE REJECTION (dBc)

PERCENTAGE (%)

5598 G24

–42–46–62 –58 –54 –50–66–70

85oC

25oC

–40oC

NOISE FLOOR (dBm/Hz)

PERCENTAGE (%)

5598 G25

–160.4 –160–161.2 –160.8–161.6–162–162.4

85oC

25oC

–40oC

NO RF

Noise Floor Distribution

LO FREQUENCY (MHz)

IMAGE REJECTION (dBc)

–80

–70

–60

–50

–40

–30

–20

–10

5598 G20a

100010010

C8 = 0

C8 = 470nF

Image Rejection vs LO Frequency

(PLO = 10dBm)

RF OUTPUT POWER (dBm)

NOISE FLOOR AT 6MHz OFFSET (dBm/Hz)

–152

–154

–156

–160

–158

–162

5598 G20b

86420–2–4–6–8–10–12–14

20dBm

19.3dBm

13.4dBm

10.4dBm

8.4dBm

6.4dBm

fLO = 140MHz; fBB = 2kHz; CW (NOTE 3)

Noise Floor vs RF Output Power and

Differential LO Input Power

LTC5598

5598f

BLOCK DIAGRAM

PIN FUNCTIONS

EN (Pin 1): Enable Input. When the Enable Pin voltage is

higher than 2 V, the IC is turned on. When the input voltage

is less than 1 V, the IC is turned off. If not connected, the

IC is enabled.

GND (Pins 2, 5, 8, 11, 12, 19, 20, 23 and 25): Ground.

Pins 2, 5, 8, 11, 12, 19, 20, 23 and exposed pad 25 are

connected to each other internally. For best RF performance,

pins 2, 5, 8, 11, 12, 19, 20, 23 and the Exposed Pad 25

should be connected to RF ground.

LOP (Pin 3): Positive LO Input. This LO input is internally

biased at about 2.3V. An AC de-coupling capacitor should

be used at this pin to match to an external 50Ω source.

LOM (Pin 4): Negative LO Input. This input is internally biased

at about 2.3V. An AC de-coupling capacitor should be used at

this pin via a 50Ω to ground for best OIP2 performance.

CAPA, CAPB (Pins 6, 7): External capacitor pins. A cap-

acitor between the CAPA and the CAPB pin can be used in

order to improve the image rejection for frequencies below

100MHz. A capacitor value of 470nF is recommended.

These pins are internally biased at about 2.3V.

BBMQ, BBPQ (Pins 9, 10): Baseband Inputs for the

Q-channel, each high input impedance. They should be

externally biased at 0.5V common-mode level and not be

left ﬂ oating. Applied common-mode voltage must stay

below 0.6VDC.

NC (Pins 13, 15): No Connect. These pins are ﬂ oating.

GNDRF (Pins 14, 17): Ground. Pins 14 and 17 are connected

to each other internally and function as the ground return for

the RF output buffer. They are connected via back-to-back

diodes to the exposed pad 25. For best LO suppression

performance those pins should be grounded separately

from the exposed paddle 25. For best RF performance,

pins 14 and 17 should be connected to RF ground.

RF (Pin 16): RF Output. The RF output is a DC-coupled

single-ended output with approximately 50Ω output

impedance at RF frequencies. An AC coupling capacitor

should be used at this pin to connect to an external

load.

VCC (Pins 18, 24): Power Supply. It is recommended to

use 1nF and 4.7μF capacitors for decoupling to ground

on each of these pins.

BBPI, BBMI (Pins 21, 22): Baseband Inputs for the Q-

channel, each high input impedance. They should be

externally biased at 0.5V common-mode level and not be

left ﬂ oating. Applied common-mode voltage must stay

below 0.6VDC.

Exposed Pad (Pin 25): Ground. This pin must be soldered

to the printed circuit board ground plane.

90o

LTC5598

V-I

GNDRF

LOP LOM CAPA CAPB

EN 1

3118

GND

24 18

13 15

BBPI

BBMI

BBPQ

BBMQ

252320

GND

764 5598 BD

GND

VCC1 VCC2

LTC5598

5598f

The LTC5598 consists of I and Q input differential voltage-

to-current converters, I and Q up-conversion mixers, an

RF output buffer, an LO quadrature phase generator and

LO buffers.

External I and Q baseband signals are applied to the

differential baseband input pins, BBPI, BBMI, and BBPQ,

BBMQ. These voltage signals are converted to currents and

translated to RF frequency by means of double-balanced

up-converting mixers. The mixer outputs are combined

in an RF output buffer, which also transforms the output

impedance to 50Ω. The center frequency of the resulting

RF signal is equal to the LO signal frequency. The LO input

drives a phase shifter which splits the LO signal into in-

phase and quadrature LO signals. These LO signals are then

applied to on-chip buffers which drive the up-conversion

mixers. In most applications, the LOP input is driven by

the LO source via an optional matching network, while

the LOM input is terminated with 50Ω to RF ground via

a similar optional matching network. The RF output is

single-ended and internally 50Ω matched.

Baseband Interface

The circuit is optimized for a common mode voltage of

0.5V which should be externally applied. The baseband

pins should not be left ﬂ oating because the internal

PNP’s base current will pull the common mode voltage

higher than the 0.6V limit. This condition may damage

the part. In shut-down mode, it is recommended to have

a termination to ground or to a 0.5V source with a value

lower than 1kΩ. The PNP’s base current is about –68μA

in normal operation.

The baseband inputs (BBPI, BBMI, BBPQ, BBMQ) present

a single-ended input impedance of about –7.4kΩ each.

Because of the negative input impedance, it is important

to keep the source resistance at each baseband input low

enough such that the parallel value remains positive vs

baseband frequency. At each of the four baseband inputs, a

capacitor of 4pF in series with 30Ω is connected to ground.

This is in parallel with a PNP emitter follower (see Figure 1).

The baseband bandwidth depends on the source impedance.

For a 25Ω source impedance, the baseband bandwidth

(–1dB) is about 300MHz. If a 5.6nH series inductor is

APPLICATIONS INFORMATION

inserted in each of the four baseband connections, the

–1dB baseband bandwidth increases to about 800MHz.

It is recommended to include the baseband input impedance

in the baseband lowpass ﬁ lter design. The input impedance

of each baseband input is given in Table 1.

Table 1. Single-Ended BB Port Input Impedance vs Frequency

for EN = High and VCMBB = 0.5VDC

FREQUENCY

(MHz)

BB INPUT

IMPEDANCE

REFLECTION COEFFICIENT

MAG ANGLE

0.1 –10578 – j263 1.01 –0.02

1 –8436 – j1930 1.011 –0.15

2 –6340 – j3143 1.013 –0.36

4 –3672 – j3712 1.014 –0.78

8 –1644 – j2833 1.015 –1.51

16 –527 – j1765 1.016 –2.98

30 –177 – j1015 1.017 –5.48

60 –45.2 – j514 1.017 –11

100 –13.2 – j306 1.014 –18.5

140 –0.2 – j219 1 –25.7

200 4.5 – j151 0.982 –36.6

300 10.4 – j99.4 0.921 –52.9

400 12.3 – j72.4 0.854 –68.2

500 14.7 – j57.5 0.780 –79.9

600 15.5 – j46.3 0.720 –91.4

The baseband inputs should be driven differentially;

otherwise, the even-order distortion products may degrade

the overall linearity performance. Typically, a DAC will

Figure 1. Simpliﬁ ed Circuit Schematic

of the LTC5598 (Only I-Half is Drawn)

BBPI

BBMI

GND

LOMI LOPI

GNDRF

FROM

55682 F01

30Ω

4pF

LTC5598

VCC1 = 5V

VCMBB = 0.5VDC

VCC2 = 5V

BUFFER

LTC5598

5598f

APPLICATIONS INFORMATION

be the signal source for the LTC5598. A reconstruction

ﬁ lter should be placed between the DAC output and the

LTC5598’s baseband inputs.

In Figure 2 a typical baseband interface is shown, using

a ﬁ fth-order lowpass ladder ﬁ lter.

in Table 3. In Table 4 and 5, the LOP port input impedance

is given for EN = High and Low under the condition of

PLO = 10dBm. Figure 4 shows the LOP port return loss

for the standard demo board (schematic is shown in

Figure 10) when the LOM port is terminated with 50Ω to

GND. The values of L1, L2, C9 and C10 are chosen such

that the bandwidth for the LOP port of the standard demo

board is maximized while meeting the LO input return loss

S11, ON < –10dB.

Table 2. LOP Port Input Impedance vs Frequency for EN = High

and PLO = 0dBm (LOM AC Coupled With 50Ω to Ground).

FREQUENCY

(MHz)

LO INPUT

IMPEDANCE

REFLECTION COEFFICIENT

MAG ANGLE

0.1 333 – j10.0 0.739 –0.5

1 318 – j59.9 0.737 –3.3

2 285 – j94.7 0.728 –6.1

4 227 – j120 0.708 –10.6

8 154 – j124 0.678 –18.7

16 89.9 – j95.4 0.611 –33.0

30 60.4 – j60.6 0.420 –41.3

60 54.8 – j35.8 0.489 –51.5

100 43.6 – j24.4 0.261 –89.9

200 37.9 – j17.3 0.235 –113

400 31.8 – j12.4 0.266 –137

800 23.6 – j8.2 0.374 –156

1000 19.8 – j5.5 0.437 –165

1250 16.0 – j1.8 0.515 –175

1500 13.6 + j2.4 0.574 174

1800 12.1 + j7.3 0.618 162

BBPI

R2A

1007

L2A

L2B

GND

0.5VDC

R2B

1007

BBMI

5598 F02

R1A

1007

R1B

1007

L1A

L1B

DAC

0mA TO 20mA

Figure 2. Baseband Interface with 5th Order Filter

and 0.5VCM DAC (Only I Channel is Shown)

For each baseband pin, a 0 to 1V swing is developed

corresponding to a DAC output current of 0mA to 20mA.

The maximum sinusoidal single side-band RF output power

is about +7.3dBm for full 0V to 1V swing on each I- and

Q- channel baseband input (2VPP, DIFF).

LO Section

The internal LO chain consists of poly-phase phase shifters

followed by LO buffers. The LOP input is designed as a

single-ended input with about 50Ω input impedance. The

LOM input should be terminated with 50Ω through a DC

blocking capacitor.

The LOP and LOM inputs can be driven differentially in

case an exceptionally low large-signal output noise ﬂ oor

is required (see graph 5598 G20b).

A simpliﬁ ed circuit schematic for the LOP, LOM, CAPA

and CAPB inputs is given in Figure 3. A feedback path is

implemented from the LO buffer outputs to the LO inputs

in order to minimize offsets in the LO chain by storing the

offsets on C5, C7 and C8 (see Figure 10). Optional capacitor

C8 improves the image rejection below 100MHz (see

graph 5598 G20a). Because of the feedback path, the input

impedance for PLO = 0dBm is somewhat different than

for PLO = 10dBm for the lower part of the operating

frequency range. In Table 2, the LOP port input impedance

vs frequency is given for EN = High and PLO = 0dBm. For

EN = Low and PLO = 0dBm, the input impedance is given

VCC1

2.8V

(4.3V IN

SHUTDOWN)

LOP LOM

CAPA

CAPB

5598 F03

Figure 3. Simpliﬁ ed Circuit Schematic for the

LOP, LOM, CAPA and CAPB Inputs.

LTC5598

5598f

APPLICATIONS INFORMATION

Table 3. LOP Port Input Impedance vs Frequency for EN = Low

and PLO = 0dBm (LOM AC Coupled with 50Ω to Ground).

FREQUENCY

(MHz)

LO INPUT

IMPEDANCE

REFLECTION COEFFICIENT

MAG ANGLE

0.1 1376 – j84.4 0.930 –0.3

1 541 – j1593 0.980 –3.2

2 177 – j877 0.977 –6.2

4 75.3 – j452 0.965 –12.2

8 49.2 – j228 0.918 –23.6

16 43.3 – j117 0.784 –41.8

30 40.7 – j64.1 0.585 –62.7

60 39.1 – j34.6 0.382 –86

100 37.6 – j23.8 0.296 –102

200 33.4 – j16.4 0.275 –124

400 27.5 – j11.1 0.320 –145

800 20.1 – j4.9 0.430 –167

1000 17.5 – j1.6 0.479 –176

1250 15.3 + j2.1 0.532 175

1500 13.8 + j5.6 0.571 167

1800 12.8 + j9.7 0.605 157

Table 4. LOP Port Input Impedance vs Frequency for EN = High

and PLO = 10dBm (LOM AC Coupled with 50Ω to Ground).

FREQUENCY

(MHz)

LO INPUT

IMPEDANCE

REFLECTION COEFFICIENT

MAG ANGLE

0.1 360-j14.8 0.756 –0.7

1 349-j70.5 0.758 –3.2

2 311-j113 0.752 –6.0

4 240-j148 0.739 –10.9

8 148-j146 0.715 –19.7

16 81.3-j102 0.641 –35.2

30 55.4-j61.6 0.506 –54.7

60 45.7-j34.4 0.341 –77.4

100 43.0-j24.1 0.261 –91.6

200 38.0-j17.1 0.234 –114

400 32.0-j12.5 0.265 –137

800 23.6-j8.3 0.374 –156

1000 19.8-j5.6 0.438 –165

1250 15.8-j1.7 0.520 –176

1500 13.5+j2.4 0.575 174

1800 12.0+j7.3 0.619 162

Table 5. LOP Port Input Impedance vs Frequency for EN = Low

and PLO = 10dBm (LOM AC Coupled with 50Ω to Ground).

FREQUENCY

(MHz)

LO INPUT

IMPEDANCE

REFLECTION COEFFICIENT

MAG ANGLE

0.1 454 – j30.5 0.802 –0.9

1 423 – j102 0.780 –3.2

2 365 – j165 0.796 –5.9

4 249 – j219 0.798 –11.4

8 117 – j179 0.781 –22.4

16 60.7 – j106 0.697 –40.3

30 43.1 – j62.0 0.559 –62.4

60 38.6 – j34.6 0.386 –86.7

100 37.6 – j23.9 0.297 –102

200 33.5 – j16.5 0.274 –124

400 27.6 – j11.3 0.319 –145

800 20.2 – j5.1 0.429 –166

1000 17.7 – j1.7 0.478 –175

1250 15.2 + j2.0 0.533 175

1500 13.9 + j5.4 0.570 167

1800 12.9 + j9.5 0.604 158

FREQUENCY (MHz)

RETURN LOSS (dB)

–10

–5

–15

–20

100

10 1000

–25

5598 F04

EN = LOW; PLO = 0dBm

EN = LOW; PLO = 10dBm

EN = HIGH; PLO = 0dBm

EN = HIGH; PLO = 10dBm

C9, C10: 2.2pF; L1, L2: 3.3nH;

C5, C7: 10nF

Figure 4. LOP Port Return Loss vs Frequency

for Standard Board (See Figure 10)

LTC5598

5598f

The LOP port return loss for the low end of the operating

frequency range can be optimized using extra 120Ω

terminations at the LO inputs (replace C9 and C10 with 120Ω

resistors, see Figure 10), and is shown in Figure 5.

The large-signal noise ﬁ gure can be improved with a

higher LO input power. However, if the LO input power is

too large and causes internal clipping in the phase shifter

section, the image rejection can be degraded rapidly. This

clipping point depends on the supply voltage, LO frequency,

temperature and single-ended vs differential LO drive. At

fLO = 140MHz, VCC = 5V, T = 25°C and single-ended LO

drive, this clipping point is at about 16.6dBm. For 4.5V it

lowers to 14.6dBm. For differential drive with VCC = 5V it

is about 20dBm.

The differential LO port input impedance for EN = High

and PLO = 10dBm is given in Table 6.

Table 6. LOP - LOM Port Differential Input Impedance

vs Frequency for EN = High and PLO = 10dBm

FREQUENCY

(MHz)

LO DIFFERENTIAL

INPUT IMPEDANCE

0.1 642 – j25.7

1.0 626 – j112

2.0 572 – j204

4.0 429 – j305

8.0 222 – j287

16 102 – j181

30 64.2 – j104

60 50.9 – j58.9

100 46.2 – j40.2

200 37.4 – j28.6

400 28.3 – j19.4

800 20.0 – j10.6

1000 17.5 – j7.9

1250 16.6 – j2.7

1500 17.3 + j3.3

1800 20.6 + j10.2

RF Section

After upconversion, the RF outputs of the I and Q mixers are

combined. An on-chip buffer performs internal differential

to single-ended conversion, while transforming the output

impedance to 50Ω. Table 7 shows the RF port output

impedance vs frequency for EN = High.

APPLICATIONS INFORMATION

FREQUENCY (MHz)

RETURN LOSS (dB)

–5

–6

–10

–12

100

10 1000

–14

–4

5598 F05

EN = LOW; PLO = 0dBm

EN = LOW; PLO = 10dBm

EN = HIGH; PLO = 0dBm

EN = HIGH; PLO = 10dBm

C9, C10: 120Ω; L1, L2: 0Ω; C5, C7: 100nF

Figure 5. LO Port Return Loss vs Frequency

Optimized for Low Frequency (See Figure 10)

The LOP port return loss for the high end of the operating

frequency range can be optimized using slightly different

values for C9, C10 and L1, L2 (see Figure 6).

FREQUENCY (MHz)

1000

RETURN LOSS (dB)

–10

–20

–30

1400

1200 1600 1800 2000

–40

5598 F06

EN = LOW

EN = HIGH

C9, C10: 2.7pF; L1, L2: 1.5nH; C5, C7: 10nF

Figure 6. LO Port Return Loss vs Frequency

Optimized for High Frequency (See Figure 10)

The third-harmonic rejection on the applied LO signal is

recommended to be equal or better than the desired image

rejection performance since third-harmonic LO content can

degrade the image rejection severely. Image rejection is

not sensitive to second-harmonic LO content.

LTC5598

5598f

Table 7. RF Output Impedance vs Frequency for EN = High

FREQUENCY

(MHz)

RF OUTPUT

IMPEDANCE

REFLECTION COEFFICIENT

MAG ANGLE

0.1 59.0 – j0.6 0.083 –3.6

1 58.5 – j2.1 0.081 –12.7

2 57.3 – j3.5 0.076 –23.6

4 54.6 – j4.5 0.061 –41.6

8 51.9 – j3.6 0.040 –60.8

16 50.5 – j2.1 0.022 –74.8

30 50.2 – j1.1 0.011 –80

60 50 – j0.5 0.005 –86.5

100 50 – j0.2 0.002 –84.9

200 49.7 + j0 0.003 177.4

400 48.9 + j0.3 0.011 162

800 46.1 + j0.4 0.041 173.3

1000 44.5 + j0.2 0.058 178

1250 42.8 + j0 0.077 –179.7

1500 41.2 – j0.1 0.097 –179.4

1800 39.9 + j0.4 0.113 177.4

The RF port output impedance for EN = Low is given in Table

8. It is roughly equivalent to a 1.3pF capacitor to ground.

Table 8. RF Output Impedance vs Frequency for EN = Low

FREQUENCY

(MHz)

LO INPUT

IMPEDANCE

REFLECTION COEFFICIENT

MAG ANGLE

100 82.3 – j1223 0.995 –4.6

200 51.1 – j618 0.987 –9.2

400 35.3 – j310 0.965 –18.1

800 24.4 – j148 0.906 –36.6

1000 20.4 – j114 0.878 –46.4

1250 17 – j87 0.847 –58.4

1500 14.7 – j68 0.818 –70.7

1800 13.1 – j54 0.785 –84.3

In Figure 7 the simpliﬁ ed circuit schematic of the RF

output buffer is drawn. A plot of the RF port return loss vs

frequency is drawn in Figure 8 for EN = High and Low.

Enable Interface

Figure 9 shows a simpliﬁ ed schematic of the EN pin

interface. The voltage necessary to turn on the LTC5598

is 2V. To disable (shut down) the chip, the enable voltage

must be below 1V. If the EN pin is not connected, the chip

is enabled. This EN = High condition is assured by the 125k

on-chip pull-up resistor. It is important that the voltage at

the EN pin does not exceed VCC by more than 0.3V. Should

APPLICATIONS INFORMATION

1.8V

4.6V

48Ω

2.8V

FROM

INTERNAL

MIXERS

INTERNAL

BIAS 5598 F07

VCC2

Figure 7. Simpliﬁ ed Circuit Schematic of the RF Output

FREQUENCY (MHz)

RETURN LOSS (dB)

–10

–30

–20

–40

100 1000

–60

–50

5598 F08

EN = LOW

EN = HIGH

C6 = 220nF, SEE FIGURE 10

Figure 8. RF Port Return Loss vs Frequency

VCC1

125k

50k

INTERNAL

ENABLE

CIRCUIT

5598 F09

Figure 9: EN Pin Interface

LTC5598

5598f

APPLICATIONS INFORMATION

Figure 12. Bottom Side of Evaluation Board

Figure 11. Component Side of Evaluation Board

470nF

10nF

1nF

5.6Ω

1Ω

4.7μF

1nF

GND

LOP

LOM

GND

CAPA

7 8 9 10 11 12 25

24 23 22 21 20 19

VCC2

GNDRF

GND

BBPI

BBMI

GND

VCC1

CAPB

GND

BBMQ

BBPQ

GND

GND BBMQ

BBPQ

RF OUT

LTC5598

BOARD NUMBER: DC1455A

LOP

LOM

GND

5598 F10

C10

2.2pF

3.3nH

VCC

BBMI BBPI

Figure 10. Evaluation Circuit Schematic

this occur, the supply current could be sourced through

the EN pin ESD protection diodes, which are not designed

to carry the full supply current, and damage may result.

Evaluation Board

Figure 10 shows the evaluation board schematic. A good

ground connection is required for the exposed pad. If this

is not done properly, the RF performance will degrade.

Additionally, the exposed pad provides heat sinking for the

part and minimizes the possibility of the chip overheating.

Resistors R1 and R2 reduce the charging current in

capacitors C1 and C4 (see Figure 10) and will reduce

supply ringing during a fast power supply ramp-up in

case an inductive cable is connected to the VCC and GND

turrets. For EN = High, the voltage drop over R1 and R2

is about 0.15V. If a power supply is used that ramps up

slower than 10V/μs and limits the overshoot on the supply

below 5.6V, R1 and R2 can be omitted.

The LTC5598 can be used for base-station applications

with various modulation formats. Figure 13 shows a

typical application.

LTC5598

5598f

Information furnished by Linear Technology Corporation is believed to be accurate and reliable.

However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-

tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.

PACKAGE DESCRIPTION

UF Package

24-Lead (4mm × 4mm) Plastic QFN

(Reference LTC DWG # 05-08-1697)

4.00 p 0.10

(4 SIDES)

NOTE:

1. DRAWING PROPOSED TO BE MADE A JEDEC PACKAGE OUTLINE MO-220 VARIATION (WGGD-X)—TO BE APPROVED

2. DRAWING NOT TO SCALE

3. ALL DIMENSIONS ARE IN MILLIMETERS

4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE

MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE, IF PRESENT

5. EXPOSED PAD SHALL BE SOLDER PLATED

6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION

ON THE TOP AND BOTTOM OF PACKAGE

PIN 1

TOP MARK

(NOTE 6)

0.40 p 0.10

2423

BOTTOM VIEW—EXPOSED PAD

2.45 p 0.10

(4-SIDES)

0.75 p 0.05 R = 0.115

TYP

0.25 p 0.05

0.50 BSC

0.200 REF

0.00 – 0.05

(UF24) QFN 0105

RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS

0.70 p0.05

0.25 p0.05

0.50 BSC

2.45 p 0.05

(4 SIDES)

3.10 p 0.05

4.50 p 0.05

PACKAGE OUTLINE

PIN 1 NOTCH

R = 0.20 TYP OR

0.35 s 45o CHAMFER

Figure 13: 5MHz to 1600MHz Direct

Conversion Transmitter Application

90o

LTC5598

2, 5, 8, 11, 12,

19, 20, 23, 25

467

13, 15

14, 17

10nF

50Ω

18, 24

10nF 470nF

10nF

BASEBAND

GENERATOR

RF = 5MHz

TO 1600MHz

1nF

x2 4.7μF

V-I

I-CHANNEL

Q-CHANNEL

VCC

5598 F13

I-DAC

Q-DAC

VCO/SYNTHESIZER

APPLICATIONS INFORMATION

LTC5598

5598f

Linear Technology Corporation

1630 McCarthy Blvd., Milpitas, CA 95035-7417

(408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com

LT 0509 • PRINTED IN USA

RELATED PARTS

PART NUMBER DESCRIPTION COMMENTS

Infrastructure

LT5514 Ultralow Distortion, IF Ampliﬁ er/ADC Driver

with Digitally Controlled Gain

850MHz Bandwidth, 47dBm OIP3 at 100MHz, 10.5dB to 33dB Gain Control Range

LT5517 40MHz to 900MHz Quadrature Demodulator 21dBm IIP3, Integrated LO Quadrature Generator

LT5518 1.5GHz to 2.4GHz High Linearity Direct

Quadrature Modulator 22.8dBm OIP3 at 2GHz, –158.2dBm/Hz Noise Floor, 50Ω Single-Ended RF and LO

Ports, 4-Channel W-CDMA ACPR = –64dBc at 2.14GHz

LT5519 0.7GHz to 1.4GHz High Linearity Upconverting

Mixer 17.1dBm IIP3 at 1GHz, Integrated RF Output Transformer with 50Ω Matching,

Single-Ended LO and RF Ports Operation

LT5520 1.3GHz to 2.3GHz High Linearity Upconverting

Mixer 15.9dBm IIP3 at 1.9GHz, Integrated RF Output Transformer with 50Ω Matching,

Single-Ended LO and RF Ports Operation

LT5521 10MHz to 3700MHz High Linearity

Upconverting Mixer

24.2dBm IIP3 at 1.95GHz, NF = 12.5dB, 3.15V to 5.25V Supply, Single-Ended LO

Port Operation

LT5522 600MHz to 2.7GHz High Signal Level

Downconverting Mixer 4.5V to 5.25V Supply, 25dBm IIP3 at 900MHz, NF = 12.5dB, 50Ω Single-Ended RF

and LO Ports

LT5527 400MHz to 3.7GHz High Signal Level

Downconverting Mixer

IIP3 = 23.5dBm and NF = 12.5dBm at 1900MHz, 4.5V to 5.25V Supply, ICC = 78mA,

Conversion Gain = 2dB.

LT5528 1.5GHz to 2.4GHz High Linearity Direct

Quadrature Modulator 21.8dBm OIP3 at 2GHz, –159.3dBm/Hz Noise Floor, 50Ω, 0.5VDC Baseband

Interface, 4-Channel W-CDMA ACPR = –66dBc at 2.14GHz

LT5554 Broadband Ultra Low Distortion 7-Bit Digitally

Controlled VGA

48dBm OIP3 at 200MHz, 1.4nV/√Hz Input-Referred Noise, 2dB to 18dB Gain Range,

0.125dB Gain Step Size

LT5557 400MHz to 3.8GHz High Signal Level

Downconverting Mixer

IIP3 = 23.7dBm at 2600MHz, 23.5dBm at 3600MHz, ICC = 82mA at 3.3V

LT5560 Ultra-Low Power Active Mixer 10mA Supply Current, 10dBm IIP3, 10dB NF, Usable as Up- or Down-Converter.

LT5568 700MHz to 1050MHz High Linearity Direct

Quadrature Modulator 22.9dBm OIP3 at 850MHz, –160.3dBm/Hz Noise Floor, 50Ω, 0.5VDC Baseband

Interface, 3-Ch CDMA2000 ACPR = –71.4dBc at 850MHz

LT5571 620MHz - 1100MHz High Linearity Quadrature

Modulator

21.7dBm OIP3 at 900MHz, –159dBm/Hz Noise Floor, High-Ohmic 0.5VDC

Baseband Interface

LT5572 1.5GHz to 2.5GHz High Linearity Direct

Quadrature Modulator

21.6dBm OIP3 at 2GHz, –158.6dBm/Hz Noise Floor, High-Ohmic 0.5VDC Baseband

Interface, 4-Ch W-CDMA ACPR = –67.7dBc at 2.14GHz

LT5575 800MHz to 2.7GHz High Linearity Direct

Conversion I/Q Demodulator

50Ω, Single-Ended RF and LO Ports, 28dBm IIP3 at 900MHz, 13.2dBm P1dB,

0.04dB I/Q Gain Mismatch, 0.4° I/Q Phase Mismatch

LT5579 1.5GHz to 3.8GHz High Linearity

Upconverting Mixer

27.3dBm OIP3 at 2.14GHz, 9.9dB Noise Floor, 2.6dB Conversion Gain,

–35dBm LO Leakage

RF Power Detectors

LTC

5505 RF Power Detectors with >40dB Dynamic Range 300MHz to 3GHz, Temperature Compensated, 2.7V to 6V Supply

LTC5507 100kHz to 1000MHz RF Power Detector 100kHz to 1GHz, Temperature Compensated, 2.7V to 6V Supply

LTC5508 300MHz to 7GHz RF Power Detector 44dB Dynamic Range, Temperature Compensated, SC70 Package

LTC5509 300MHz to 3GHz RF Power Detector 36dB Dynamic Range, Low Power Consumption, SC70 Package

LTC5530 300MHz to 7GHz Precision RF Power Detector Precision VOUT Offset Control, Shutdown, Adjustable Gain

LTC5531 300MHz to 7GHz Precision RF Power Detector Precision VOUT Offset Control, Shutdown, Adjustable Offset

LTC5532 300MHz to 7GHz Precision RF Power Detector Precision VOUT Offset Control, Adjustable Gain and Offset

LT5534 50MHz to 3GHz Log RF Power Detector with

60dB Dynamic Range

±1dB Output Variation over Temperature, 38ns Response Time, Log Linear

Response

LTC5536 Precision 600MHz to 7GHz RF Power Detector

with Fast Comparator Output

25ns Response Time, Comparator Reference Input, Latch Enable Input,

–26dBm to +12dBm Input Range

LT5537 Wide Dynamic Range Log RF/IF Detector Low Frequency to 1GHz, 83dB Log Linear Dynamic Range

LT5538 3.8GHz Wide Dynamic Range Log Detector 75dB Dynamic Range, ±1dB Output Variation Over Temperature

LT5570 2.7GHz RMS Power Detector Fast Responding, up to 60dB Dynamic Range, ±0.3dB Accuracy Over Temperature

LT5581 40dB Dynamic Range RMS Detector 10MHz to 6GHz, ±1dB Accuracy Over Temperature, 1.4mA at 3.3V Supply