LMZ23610 LMZ23610 10A SIMPLE SWITCHER Power Module with 36V Maximum Input Voltageand Current Sharing Literature Number: SNVS707C LMZ23610 10A SIMPLE SWITCHER(R) Power Module with 36V Maximum Input Voltage and Current Sharing Easy to use 11 pin package Performance Benefits High efficiency reduces system heat generation Low radiated emissions (EMI) complies with EN55022 class B standard (Note 2) Only 7 external components Low output voltage ripple No external heat sink required Simple current sharing for higher current applications System Performance 30151101 Electrical Specifications 50W maximum total output power Up to 10A output current Input voltage range 6V to 36V Output voltage range 0.8V to 6V Efficiency up to 92% Efficiency VIN = 24V VOUT = 3.3V 100 90 EFFICIENCY (%) TO-PMOD 11 Pin Package 15 x 17.79 x 5.9 mm (0.59 x 0.7 x 0.232 in) JA = 9.9 C/W, JC = 1.0 C/W (Note 1) RoHS Compliant 80 70 60 50 40 30 24 Vin 20 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) Key Features 30151102 Integrated shielded inductor Simple PCB layout Frequency synchronization input (350 kHz to 600 kHz) Current sharing capability Flexible startup sequencing using external soft-start, tracking and precision enable Protection against inrush currents and faults such as input UVLO and output short circuit - 40C to 125C junction temperature range Single exposed pad and standard pinout for easy mounting and manufacturing Fully enabled for Webench(R) Power Designer Pin compatible with LMZ22010/08, LMZ12010/08, LMZ23608/06H, and LMZ13610/08/06H 12 10 8 6 4 2 JA = 9.9 C/W JA = 6.8 C/W JA = 5.2 C/W 0 20 40 60 80 100 TEMPERATURE (C) 120 30151103 Note 1: JA measured on a 75mm x 90mm four layer PCB. Note 2: EN 55022:2006, +A1:2007, FCC Part 15 Subpart B. Applications Thermal derating curve VIN = 24V, VOUT = 3.3V MAXIMUM OUTPUT CURRENT (A) 9 10 Point of load conversions from 12V and 24V input rail Time critical projects Space constrained / high thermal requirement applications Negative output voltage applications (See AN-2027) (c) 2011 National Semiconductor Corporation 301511 www.national.com LMZ23610 10A SIMPLE SWITCHER(R) Power Module with 36V Maximum Input Voltage and Current Sharing May 3, 2011 LMZ23610 Simplified Application Schematic 30151107 Connection Diagram 30151106 Top View 11-Lead TO-PMOD Ordering Information Order Number Package Type NSC Package Drawing LMZ23610TZ TO-PMOD-11 TZA11A 32 Units in a Rail LMZ23610TZE TO-PMOD-11 TZA11A 250 Units on Tape and Reel www.national.com 2 Supplied As Pin 1, 2 3 4 5, 6 Name Description VIN Supply input -- Nominal operating range is 6V to 36V . A small amount of internal capacitance is contained within the package assembly. Additional external input capacitance is required between this pin and PGND. SYNC Sync Input -- Apply a CMOS logic level square wave whose frequency is between 350 kHz and 600 kHz to synchronize the PWM operating frequency to an external frequency source. When not using synchronization this pin must be tied to ground. The module free running PWM frequency is 350 kHz. EN Enable -- Input to the precision enable comparator. Rising threshold is 1.274V typical. Once the module is enabled, a 20 uA source current is internally activated to accommodate programmable hysteresis. AGND Analog Ground -- Reference point for all stated voltages. Must be externally connected to EP/PGND. 7 FB Feedback -- Internally connected to the regulation, over-voltage, and short-circuit comparators. The regulation reference point is 0.8V at this input pin. Connect the feedback resistor divider between the output and AGND to set the output voltage. 8 SS Soft-Start/Track input -- To extend the 1.6 mSec internal soft-start connect an external soft start capacitor. For tracking connect to an external resistive divider connected to a higher priority supply rail. See applications section. 9 SH Share pin. Connect this to the share pin of other LMZ23610 modules to share the load between the devices. One device should be configured as the master by connecting the FB normally. All other devices should be configured as slaves by leaving their respective FB pins floating. Leave this pin floating if not used, do not ground. See applications section. 10, 11 VOUT Output Voltage -- Output from the internal inductor. Connect the output capacitor between this pin and PGND. EP PGND Exposed Pad / Power Ground Electrical path for the power circuits within the module. -- NOT Internally connected to AGND / pin 5. Used to dissipate heat from the package during operation. Must be electrically connected to pin 5 external to the package. 3 www.national.com LMZ23610 Pin Descriptions LMZ23610 ESD Susceptibility (Note 4) For soldering specifications: see product folder at www.national.com and www.national.com/ms/MS/MS-SOLDERING.pdf Absolute Maximum Ratings (Note 3) If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. VIN to PGND EN, SYNC to AGND SS, FB, SH to AGND AGND to PGND Junction Temperature Storage Temperature Range Operating Ratings -0.3V to 40V -0.3V to 5.5V -0.3V to 2.5V -0.3V to 0.3V 150C -65C to 150C 2 kV (Note 3) VIN EN, SYNC Operation Junction Temperature 6V to 36V 0V to 5.0V -40C to 125C Electrical Characteristics Limits in standard type are for TJ = 25C only; limits in boldface type apply over the junction temperature (TJ) range of -40C to +125C. Minimum and Maximum limits are guaranteed through test, design or statistical correlation. Typical values represent the most likely parametric norm at TJ = 25C, and are provided for reference purposes only. Unless otherwise stated the following conditions apply: VIN = 12V, VOUT = 3.3V Symbol Parameter Conditions Min (Note 5) Typ (Note 6) Max (Note 5) 1.096 1.274 1.452 Units SYSTEM PARAMETERS Enable Control VEN EN threshold VEN rising EN hysteresis source current VEN > 1.274V ISS SS source current VSS = 0V tSS Internal soft-start interval IEN-HYS 13 V A Soft-Start 40 50 60 1.6 A msec Current Limit ICL Current limit threshold d.c. average 12.5 A Internal Switching Oscillator fosc Free-running oscillator frequency Sync input connected to ground 314 fsync Synchronization range Vsync = 3.3Vp-p 314 VIL-sync Synchronization logic zero amplitude Relative to AGND VIH-sync Synchronization logic one amplitude Relative to AGND Sync d.c. Synchronization duty cycle range 359 404 kHz 600 kHz 0.4 V V 1.8 15 50 85 % 0.775 0.795 0.815 V Regulation and Over-Voltage Comparator VFB VFB-OV In-regulation feedback voltage VSS >+ 0.8V IO = 10A Feedback over-voltage protection threshold 0.86 V 5 nA IFB Feedback input bias current IQ Non Switching Quiescent Current SYNC = 3.0V 3 mA ISD Shut Down Quiescent Current VEN = 0V 32 A 85 % 165 C Dmax Maximum Duty Factor Thermal Characteristics TSD Thermal Shutdown Rising TSD-HYST Thermal shutdown hysteresis Falling 15 C JA Junction to Ambient (Note 7) Natural Convection 9.9 C/W 225 LFPM 6.8 500 LFPM 5.2 JC www.national.com Junction to Case 1.0 4 C/W Parameter Min (Note 5) Conditions Typ (Note 6) Max (Note 5) Units PERFORMANCE PARAMETERS (Note 8) VO Output voltage ripple BW@ 20 MHz 24 mV PP VO/VIN Line regulation VIN = 12V to 20V, IOUT= 10A 0.2 % VO/IOUT Load regulation VIN = 12V, IOUT= 0.001A to 10A 1 mV/A Peak efficiency VIN = 12V VOUT = 3.3V IOUT = 5A 89.5 % Full load efficiency VIN = 12V VOUT = 3.3V IOUT = 10A 87.5 % Note 3: Absolute Maximum Ratings are limits beyond which damage to the device may occur. Operating Ratings are conditions under which operation of the device is intended to be functional. For guaranteed specifications and test conditions, see the Electrical Characteristics. Note 4: The human body model is a 100pF capacitor discharged through a 1.5 k resistor into each pin. Test method is per JESD-22-114. Note 5: Min and Max limits are 100% production tested at 25C. Limits over the operating temperature range are guaranteed through correlation using Statistical Quality Control (SQC) methods. Limits are used to calculate National's Average Outgoing Quality Level (AOQL). Note 6: Typical numbers are at 25C and represent the most likely parametric norm. Note 7: Theta JA measured on a 3.0" x 3.5" four layer board, with two ounce copper on outer layers and one ounce copper on inner layers, two hundred and ten 12 mil thermal vias, and 2W power dissipation. Refer to evaluation board application note layout diagrams. Note 8: Refer to BOM in Typical Application Bill of Materials -- Table 1. 5 www.national.com LMZ23610 Symbol Unless otherwise specified, the following conditions apply: VIN = 12V; CIN = three x 10F + 47nF X7R Ceramic; COUT = two x 330F Specialty Polymer + 47 uF Ceramic + 47nF Ceramic; CFF = 4.7nF; Tambient = 25 C for waveforms. All indicated temperatures are ambient. Dissipation 5.0V output @ 25C 100 12 90 10 DISSIPATION (W) EFFICIENCY (%) Efficiency 5.0V output @ 25C 80 70 8 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 60 50 40 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 8 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 8 6 4 2 0 9 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 30151134 Dissipation 3.3V output @ 25C 12 90 10 DISSIPATION (W) 100 80 70 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 60 50 40 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 8 6 4 2 0 9 10 0 30151136 www.national.com 9 10 30151135 Efficiency 3.3V output @ 25C EFFICIENCY (%) LMZ23610 Typical Performance Characteristics 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 9 10 30151137 6 12 90 10 DISSIPATION (W) EFFICIENCY (%) Dissipation 2.5V output @ 25C 100 80 70 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 60 50 40 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 8 6 4 2 0 9 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 30151138 12 80 10 70 DISSIPATION (W) EFFICIENCY (%) Dissipation 1.8V output @ 25C 90 60 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 40 30 20 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 8 6 4 2 0 9 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 30151140 Dissipation 1.5V output @ 25C 12 80 10 70 DISSIPATION (W) EFFICIENCY (%) Efficiency 1.5V output @ 25C 60 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 40 30 20 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 9 10 30151141 90 50 9 10 30151139 Efficiency 1.8V output @ 25C 50 LMZ23610 Efficiency 2.5V output @ 25C 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 8 6 4 2 0 9 10 0 30151142 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 9 10 30151143 7 www.national.com LMZ23610 Efficiency 1.2V output @ 25C Dissipation 1.2V output @ 25C 12 90 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 10 70 DISSIPATION (W) EFFICIENCY (%) 80 60 50 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 40 30 20 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 8 6 4 2 0 9 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 30151144 30151145 Efficiency 1.0V output @ 25C Dissipation 1.0V output @ 25C 90 12 80 DISSIPATION (W) EFFICIENCY (%) 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 10 70 60 50 40 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 30 20 10 0 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 8 6 4 2 0 9 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 30151146 Dissipation 5.0V output @ 85C 12 90 10 DISSIPATION (W) EFFICIENCY (%) Efficiency 5.0V output @ 85C 80 70 8 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 50 40 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 8 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 8 6 4 2 0 9 10 0 30151148 www.national.com 9 10 30151147 100 60 9 10 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 9 10 30151149 8 Dissipation 3.3V output @ 85C 12 100 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 10 80 DISSIPATION (W) EFFICIENCY (%) 90 70 60 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 50 40 30 20 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 8 6 4 2 0 9 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 30151150 Dissipation 2.5V output @ 85C 12 100 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 10 80 DISSIPATION (W) EFFICIENCY (%) 90 70 60 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 40 30 20 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 8 6 4 2 0 9 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 30151152 Dissipation 1.8V output @ 85C 14 80 12 70 DISSIPATION (W) EFFICIENCY (%) Efficiency 1.8V output @ 85C 60 50 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 30 20 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 9 10 30151153 90 40 9 10 30151151 Efficiency 2.5V output @ 85C 50 LMZ23610 Efficiency 3.3V output @ 85C 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 10 8 6 4 2 0 9 10 0 30151154 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 9 10 30151155 9 www.national.com LMZ23610 Dissipation 1.5V output @ 85C 90 14 80 12 70 DISSIPATION (W) EFFICIENCY (%) Efficiency 1.5V output @ 85C 60 50 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 40 30 20 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 10 8 6 4 2 0 9 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 30151156 30151157 Dissipation 1.2V output @ 85C 90 14 80 12 70 DISSIPATION (W) EFFICIENCY (%) Efficiency 1.2V output @ 85C 60 50 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 40 30 20 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 10 8 6 4 2 0 9 10 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 30151158 Efficiency 1.0V output @ 85C Dissipation 1.0V output @ 85C 14 80 DISSIPATION (W) EFFICIENCY (%) 70 60 50 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36Vin 20 10 0 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 10 8 6 4 2 0 9 10 0 30151160 www.national.com 6 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 30 Vin 36 Vin 12 30 9 10 30151159 90 40 9 10 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 9 10 30151161 10 Thermal derating VIN = 24V, VOUT = 5.0V 12 MAXIMUM OUTPUT CURRENT (A) 1.002 NORMALIZED VOUT (V/V) LMZ23610 Normalized line and load regulation VOUT = 3.3V 1.001 1.000 6 Vin 8 Vin 10 Vin 12 Vin 16 Vin 20 Vin 24 Vin 36 Vin 0.999 0.998 0 1 2 3 4 5 6 7 8 OUTPUT CURRENT (A) 10 8 6 4 2 JA = 9.9 C/W JA = 6.8 C/W JA = 5.2 C/W 0 9 10 20 30 40 50 60 70 80 90 100 110 120 TEMPERATURE (C) 30151162 30151163 JA vs copper heat sinking area Thermal derating VIN = 24V, VOUT = 3.3V 30 10 24 8 6 4 2 0 2 Layer 0 LFPM 2 Layer 225 LFPM 4 Layer 0 LFPM 4 Layer 225 LFPM 27 THETA JA (C/W) MAXIMUM OUTPUT CURRENT (A) 12 21 18 15 12 9 JA = 9.9 C/W JA = 6.8 C/W JA = 5.2 C/W 6 3 20 30 40 50 60 70 80 90 100 110 120 TEMPERATURE (C) 0 2 4 6 8 COPPER AREA (in2) 10 12 30151164 30151165 Output ripple 12VIN, 5.0VOUT @ Full Load, BW = 20 MHz Output ripple 12VIN, 5.0VOUT@ Full Load, BW = 250 MHz 30151166 30151169 11 www.national.com LMZ23610 Output ripple 12VIN, 3.3VOUT @ Full Load, BW = 20 MHz Output ripple 12VIN, 3.3VOUT@ Full Load, BW = 250 MHz 30151170 30151167 Output ripple 12VIN, 1.2VOUT @ Full Load, BW = 20 MHz Output ripple 12VIN, 1.2VOUT@ Full Load, BW = 250 MHz 30151171 30151168 Transient response 12VIN, 5.0VOUT 1 to 10A Step Transient response 12VIN, 3.3VOUT 1 to 10A Step 30151172 www.national.com 30151173 12 LMZ23610 Transient response 12VIN, 1.2VOUT 1 to 10A Step Short circuit current vs input voltage 16 14 CURRENT (A) 12 10 8 6 4 Output Current Input Current 2 0 5 30151174 10 15 INPUT VOLTAGE (V) 20 30151175 3.3VOUT Soft Start, no CSS 3.3VOUT Soft Start, CSS = 0.47uF 30151176 301511a4 Block Diagram 30151177 13 www.national.com LMZ23610 precision under voltage lock out (UVLO), the Enable input may be left open circuit and the internal resistor will always enable the module. In such case, the internal UVLO occurs typically at 4.3V (VIN rising). In applications with separate supervisory circuits Enable can be directly interfaced to a logic source. In the case of sequencing supplies, the divider is connected to a rail that becomes active earlier in the power-up cycle than the LMZ23610 output rail. Enable provides a precise 1.274V threshold to allow direct logic drive or connection to a voltage divider from a higher enable voltage such as VIN. Additionally there is 13 A (typ) of switched offset current allowing programmable hysteresis. See Figure 1. The function of the enable divider is to allow the designer to choose an input voltage below which the circuit will be disabled. This implements the feature of a programmable UVLO. The two resistors should be chosen based on the following ratio: General Description The LMZ23610 SIMPLE SWITCHER(c) power module is an easy-to-use step-down DC-DC solution capable of driving up to 10A load. The LMZ23610 is available in an innovative package that enhances thermal performance and allows for hand or machine soldering. The LMZ23610 can accept an input voltage rail between 6V and 36V and deliver an adjustable and highly accurate output voltage as low as 0.8V. The LMZ23610 only requires two external resistors and three external capacitors to complete the power solution. The LMZ23610 is a reliable and robust design with the following protection features: thermal shutdown, input under-voltage lockout, output over-voltage protection, short-circuit protection, output current limit, and allows startup into a pre-biased output. The sync input allows synchronization over the 350 to 600 kHz switching frequency range. Design Steps for the LMZ23610 Application RENT / RENB = (VIN UVLO / 1.274V) - 1 (1) The LMZ23610 is fully supported by Webench(R) which offers: component selection, electrical and thermal simulations. Additionally, there are both evaluation and demonstration boards that may be used as a starting point for design. The following list of steps can be used to manually design the LMZ23610 application. All references to values refer to the typical applications schematic Figure 5 . * Select minimum operating VIN with enable divider resistors * Program VOUT with FB resistor divider selection * Select COUT * Select CIN * Determine module power dissipation * Layout PCB for required thermal performance The LMZ23610 typical application shows 12.7k for RENB and 42.2k for RENT resulting in a rising UVLO of 5.51V. Note that this divider presents 4.62V to the EN input when VIN is raised to 20V. This upper voltage should always be checked, making sure that it never exceeds the Abs Max 5.5V limit for Enable. A 5.1V Zener clamp can be applied in cases where the upper voltage would exceed the EN input's range of operation. The zener clamp is not required if the target application prohibits the maximum Enable input voltage from being exceeded. Additional enable voltage hysteresis can be added with the inclusion of RENH. It is possible to select values for RENT and RENB such that RENH is a value of zero allowing it to be omitted from the design. Rising threshold can be calculated as follows: ENABLE DIVIDER, RENT, RENB AND RENHSELECTION Internal to the module is a 2 mega ohm pull-up resistor connected from VIN to Enable. For applications not requiring Whereas the falling threshold level can be calculated using: VEN(rising) = 1.274 ( 1 + (RENT|| 2 meg)/ RENB) VEN(falling) = VEN(rising) - 13 A ( RENT|| 2 meg || RENTB + RENH ) 30151179 FIGURE 1. Enable input detail www.national.com 14 (2) (3) VOUT = 0.795V * (1 + RFBT / RFBB) (4) Rearranging terms; the ratio of the feedback resistors for a desired output voltage is: RFBT / RFBB = (VOUT / 0.795V) - 1 (5) These resistors should generally be chosen from values in the range of 1.0 k to 10.0 k. For VOUT = 0.8V the FB pin can be connected to the output directly and RFBB can be set to 8.06k to provide minimum output load. A table of values for RFBT , and RFBB, is included in the simplified applications schematic on page 2. 30151180 SOFT-START CAPACITOR SELECTION Programmable soft-start permits the regulator to slowly ramp to its steady state operating point after being enabled, thereby reducing current inrush from the input supply and slowing the output voltage rise-time. Upon turn-on, after all UVLO conditions have been passed, an internal 1.6msec circuit slowly ramps the SS input to implement internal soft start. If 1.6 msec is an adequate turn-on time then the Css capacitor can be left unpopulated. Longer soft-start periods are achieved by adding an external capacitor to this input. Soft start duration is given by the formula: tSS = VREF * CSS / Iss = 0.795V * CSS / 50uA FIGURE 2. Tracking option input detail COUT SELECTION None of the required COUT output capacitance is contained within the module. A minimum value ranging from 330 F for 6VOUT to 660 F for 1.2VOUT applications is required based on the values of internal compensation in the error amplifier. These minimum values can be decreased if the effective capacitor ESR is higher than 15 mOhms. A Low ESR (15 mOhm) tantalum, organic semiconductor or specialty polymer capacitor types in parallel with a 47nF X7R ceramic capacitor for high frequency noise reduction is recommended for obtaining lowest ripple. The output capacitor COUT may consist of several capacitors in parallel placed in close proximity to the module. The output capacitor assembly must also meet the worst case ripple current rating of iL, as calculated in equation (18) below. Beyond that, additional capacitance will reduce output ripple so long as the ESR is low enough to permit it. Loop response verification is also valuable to confirm closed loop behavior. For applications with dynamic load steps; the following equation provides a good first pass approximation of COUT for load transient requirements. (6) This equation can be rearranged as follows: CSS = tSS * 50A / 0.795V (7) Using a 0.22F capacitor results in 3.5 msec typical soft-start duration; and 0.47F results in 7.5 msec typical. 0.47 F is a recommended initial value. As the soft-start input exceeds 0.795V the output of the power stage will be in regulation and the 50 A current is deactivated. Note that the following conditions will reset the soft-start capacitor by discharging the SS input to ground with an internal current sink. * The Enable input being pulled low * A thermal shutdown condition * VIN falling below 4.3V (TYP) and triggering the VCC UVLO (8) TRACKING SUPPLY DIVIDER OPTION The tracking function allows the module to be connected as a slave supply to a primary voltage rail (often the 3.3V system rail) where the slave module output voltage is lower than that of the master. Proper configuration allows the slave rail to power up coincident with the master rail such that the voltage difference between the rails during ramp-up is small (i.e. <0.15V typ). The values for the tracking resistive divider should be selected such that the effect of the internal 50uA current source is minimized. In most cases the ratio of the tracking divider resistors is the same as the ratio of the output voltage setting divider. Proper operation in tracking mode dictates the soft-start time of the slave rail be shorter than the master rail; a condition that is easy to satisfy since the CSS cap is replaced by RTKB. The tracking function is only supported for the power up interval of the master supply; once For 12VIN, 3.3VOUT, a transient voltage of 5% of VOUT = 0.165V (VOUT), a 9A load step (ISTEP), an output capacitor effective ESR of 3 mOhms, and a switching frequency of 350kHz (fSW): (9) Note that the stability requirement for minimum output capacitance must always be met. One recommended output capacitor combination is two 330F, 15 mOhm ESR tantalum polymer capacitors connected in parallel with a 47 uF 6.3V X5R ceramic. This combination provides excellent performance that may exceed the 15 www.national.com LMZ23610 the SS/TRK rises past 0.795V the input is no longer enabled and the 50 uA internal current source is switched off. OUTPUT VOLTAGE SELECTION Output voltage is determined by a divider of two resistors connected between VOUT and AGND. The midpoint of the divider is connected to the FB input. The regulated output voltage determined by the external divider resistors RFBT and RFBB is: LMZ23610 requirements of certain applications. Additionally some small 47nF ceramic capacitors can be used for high frequency EMI suppression. Given the typical thermal resistance from junction to case (JC) to be 1.0 C/W. Use the 85C power dissipation curves in the Typical Performance Characteristics section to estimate the PIC-LOSS for the application being designed. In this application it is 5.3W. CIN SELECTION The LMZ23610 module contains two internal ceramic input capacitors. Additional input capacitance is required external to the module to handle the input ripple current of the application. The input capacitor can be several capacitors in parallel. This input capacitance should be located in very close proximity to the module. Input capacitor selection is generally directed to satisfy the input ripple current requirements rather than by capacitance value. Input ripple current rating is dictated by the equation: (14) To reach CA = 13.15, the PCB is required to dissipate heat effectively. With no airflow and no external heat-sink, a good estimate of the required board area covered by 2 oz. copper on both the top and bottom metal layers is: (15) (10) where D VOUT / VIN As a result, approximately 38.02 square cm of 2 oz copper on top and bottom layers is the minimum required area for the example PCB design. This is 6.16 x 6.16 cm (2.42 x 2.42 in) square. The PCB copper heat sink must be connected to the exposed pad. For best performance, use approximately 100, 12mil (305 m) thermal vias spaced 59 mil (1.5 mm) apart connect the top copper to the bottom copper. Another way to estimate the temperature rise of a design is using JA. An estimate of JA for varying heat sinking copper areas and airflows can be found in the typical applications curves. If our design required the same operating conditions as before but had 225 LFPM of airflow. We locate the required JA of (As a point of reference, the worst case ripple current will occur when the module is presented with full load current and when VIN = 2 * VOUT). Recommended minimum input capacitance is 30 uF X7R (or X5R) ceramic with a voltage rating at least 25% higher than the maximum applied input voltage for the application. It is also recommended that attention be paid to the voltage and temperature derating of the capacitor selected. It should be noted that ripple current rating of ceramic capacitors may be missing from the capacitor data sheet and you may have to contact the capacitor manufacturer for this parameter. If the system design requires a certain minimum value of peak-to-peak input ripple voltage (VIN) to be maintained then the following equation may be used. (11) (16) If VIN is 200 mV or 1.66% of VIN for a 12V input to 3.3V output application and fSW = 350 kHz then: On the Theta JA vs copper heatsinking curve, the copper area required for this application is now only 2 square inches. The airflow reduced the required heat sinking area by a factor of three. To reduce the heat sinking copper area further, this package is compatable with D3-PAK surface mount heat sinks. For an example of a high thermal performance PCB layout for SIMPLE SWITCHER(c) power modules, refer to AN-2093, AN-2084, AN-2125, AN-2020 and AN-2026. (12) Additional bulk capacitance with higher ESR may be required to damp any resonant effects of the input capacitance and parasitic inductance of the incoming supply lines. The LMZ23610 typical applications schematic and evaluation board include a 150 F 50V aluminum capacitor for this function. There are many situations where this capacitor is not necessary. PC BOARD LAYOUT GUIDELINES PC board layout is an important part of DC-DC converter design. Poor board layout can disrupt the performance of a DCDC converter and surrounding circuitry by contributing to EMI, ground bounce and resistive voltage drop in the traces. These can send erroneous signals to the DC-DC converter resulting in poor regulation or instability. Good layout can be imple- POWER DISSIPATION AND BOARD THERMAL REQUIREMENTS When calculating module dissipation use the maximum input voltage and the average output current for the application. Many common operating conditions are provided in the characteristic curves such that less common applications can be derived through interpolation. In all designs, the junction temperature must be kept below the rated maximum of 125C. For the design case of VIN = 12V, VOUT = 3.3V, IOUT = 10A, and TA-MAX = 50C, the module must see a thermal resistance from case to ambient (CA) of less than: (13) www.national.com 16 Additional Features SYNCHRONIZATION INPUT The PWM switching frequency can be synchronized to an external frequency source. The PWM switching will be in phase with the external frequency source. If this feature is not used, connect this input either directly to ground, or connect to ground through a resistor of 1.5 k ohm or less. The allowed synchronization frequency range is 314 kHz to 600 kHz. The typical input threshold is 1.4V. Ideally, the input clock should overdrive the threshold by a factor of 2, so direct drive from 3.3V logic via a 1.5k or less Thevenin source resistance is recommended. Note that applying a sustained "logic 1" corresponds to zero Hz PWM frequency and will cause the module to stop switching. 30151181 FIGURE 3. High Current Loops CURRENT SHARING When a load current higher than 10A is required by the application, the LMZ23610 can be configured to share the load between multiple devices. To share the load current between the devices, connect the SH pin of all current sharing LMZ23610 modules. One device should be configured as the master by connecting FB normally. All other devices should be configured as slaves by leaving their respective FB pins floating. The modules should be synchronized by a clock signal to avoid beat frequencies in the output voltage caused by small differences in the internal 359 kHz clock. If the modules are not synchronized, the magnitude of the ripple voltage will depend on the phase relationship of the internal clocks. The external synchronizing clocks can be in phase for all modules, or out of phase to reduce the current stress on the input and output capacitors. As an example, two modules can be run 180 degrees out of phase, and three modules can be run 120 degrees out of phase. The VIN, VOUT, PGND, and AGND pins should also be connected with low impedance paths. It is particularly important to pay close attention to the layout of AGND and SH, as offsets in grounding or noise picked up from other devices will be seen as a mismatch in current sharing and could cause noise issues. Current sharing modules can be configured to share the same set of bulk input and output capacitors, while each having their own local input and output bypass capacitors. A CIN_BYP >= 30uF is still recommended for each module that is connected in a current sharing configuration. A COUT_BYP consisting of 47nF X7R ceramic capacitor in parallel with a 22F ceramic capacitor is recommended to locally bypass the output voltage for each module. These capacitors will provide local bypassing of high frequency switched currents. The loop gain of the master module increases by a factor of two when the share pin is connected with a second module. This increases the bulk output capacitance required for stability. For example, two modules configured to provide 1.2VOUT and 20 amps have a required total bulk output capacitance of COUT_BULK = 2 x 450F (ESR 25mOhms). This is a thirty six percent increase in the required output capacitance of a stand alone module. Up to 6 modules can be connected in parallel for loads up to 60A. For more information on current sharing refer to AN-2093 (Current sharing evaluation board). 1. Minimize area of switched current loops. From an EMI reduction standpoint, it is imperative to minimize the high di/dt paths during PC board layout as shown in the figure above. The high current loops that do not overlap have high di/dt content that will cause observable high frequency noise on the output pin if the input capacitor (CIN) is placed at a distance away from the LMZ23610. Therefore place CIN as close as possible to the LMZ23610 VIN and PGND exposed pad. This will minimize the high di/dt area and reduce radiated EMI. Additionally, grounding for both the input and output capacitor should consist of a localized top side plane that connects to the PGND exposed pad (EP). 2. Have a single point ground. The ground connections for the feedback, soft-start, and enable components should be routed to the AGND pin of the device. This prevents any switched or load currents from flowing in the analog ground traces. If not properly handled, poor grounding can result in degraded load regulation or erratic output voltage ripple behavior. Additionally provide a single point ground connection from pin 4 (AGND) to EP/ PGND. 3. Minimize trace length to the FB pin. Both feedback resistors, RFBT and RFBB should be located close to the FB pin. Since the FB node is high impedance, maintain the copper area as small as possible. The traces from RFBT, RFBB should be routed away from the body of the LMZ23610 to minimize possible noise pickup. 4. Make input and output bus connections as wide as possible. This reduces any voltage drops on the input or output of the converter and maximizes efficiency. To optimize voltage accuracy at the load, ensure that a separate feedback voltage sense trace is made to the load. Doing so will correct for voltage drops and provide optimum output accuracy. 5. Provide adequate device heat-sinking. Use an array of heat-sinking vias to connect the exposed pad to the ground plane on the bottom PCB layer. If the PCB has multiple copper layers, these thermal vias can also be connected to inner layer heat-spreading ground planes. For best results use a 10 x 10 via array or larger with a minimum via 17 www.national.com LMZ23610 diameter of 12mil (305 m) thermal vias spaced 46.8mil (1.5 mm). Ensure enough copper area is used for heat-sinking to keep the junction temperature below 125C. mented by following a few simple design rules. A good layout example is shown in Figure 6. LMZ23610 30151182 FIGURE 4. Current Sharing Example Schematic Output voltage ripple of two modules with synchronization clocks in phase OUTPUT OVER-VOLTAGE PROTECTION If the voltage at FB is greater than a 0.86V internal reference, the output of the error amplifier is pulled toward ground, causing VOUT to fall. CURRENT LIMIT The LMZ23610 is protected by both low side (LS) and high side (HS) current limit circuitry. The LS current limit detection is carried out during the off-time by monitoring the current through the LS synchronous MOSFET. Referring to the Functional Block Diagram, when the top MOSFET is turned off, the inductor current flows through the load, the PGND pin and the internal synchronous MOSFET. If this current exceeds 13A (typical) the current limit comparator disables the start of the next switching period. Switching cycles are prohibited until current drops below the limit. It should also be noted that d.c. current limit is dependent on duty cycle as illustrated in the graph in the typical performance section. The HS current limit monitors the current of top side MOSFET. Once HS current limit is detected (16A typical) , the HS MOSFET is shutoff immediately, until the next cycle. Exceeding HS current limit causes VOUT to fall. Typical behavior of exceeding LS current limit is that fSW drops to 1/2 of the operating frequency. 30151183 Output voltage ripple of two modules with synchronization clocks 180 degrees out of phase THERMAL PROTECTION The junction temperature of the LMZ23610 should not be allowed to exceed its maximum ratings. Thermal protection is implemented by an internal Thermal Shutdown circuit which activates at 165 C (typ) causing the device to enter a low power standby state. In this state the main MOSFET remains off causing VOUT to fall, and additionally the CSS capacitor is discharged to ground. Thermal protection helps prevent catastrophic failures for accidental device overheating. When the junction temperature falls back below 150 C (typ Hyst = 30151184 www.national.com 18 In CCM, current flows through the inductor through the entire switching cycle and never falls to zero during the off-time. Following is a comparison pair of waveforms showing both the CCM (upper) and DCM operating modes. CCM and DCM Operating Modes VIN = 12V, VO = 3.3V, IO = 3A/0.3A PRE-BIASED STARTUP The LMZ23610 will properly start up into a pre-biased output. This startup situation is common in multiple rail logic applications where current paths may exist between different power rails during the startup sequence. The following scope capture shows proper behavior in this mode. Trace one is Enable going high. Trace two is 1.8V pre-bias rising to 3.3V. Trace three is the SS voltage with a CSS= 0.47uF. Risetime determined by CSS. Pre-Biased Startup 30151186 The approximate formula for determining the DCM/CCM boundary is as follows: (17) The inductor internal to the module is 2.2 H. This value was chosen as a good balance between low and high input voltage applications. The main parameter affected by the inductor is the amplitude of the inductor ripple current (iL). iL can be calculated with: 30151185 DISCONTINUOUS CONDUCTION AND CONTINUOUS CONDUCTION MODES At light load the regulator will operate in discontinuous conduction mode (DCM). With load currents above the critical conduction point, it will operate in continuous conduction mode (CCM). When operating in DCM, inductor current is maintained to an average value equaling Iout . In DCM the low-side switch will turn off when the inductor current falls to zero, this causes the inductor current to resonate. Although it is in DCM, the current is allowed to go slightly negative to charge the bootstrap capacitor. (18) Where V IN is the maximum input voltage and fSW is typically 359 kHz. If the output current IOUT is determined by assuming that IOUT = IL, the higher and lower peak of iL can be determined. 19 www.national.com LMZ23610 15C) the SS pin is released, VOUT rises smoothly, and normal operation resumes. Applications requiring maximum output current especially those at high input voltage may require additional derating at elevated temperatures. LMZ23610 Typical Application Schematic Diagram and BOM 30151187 FIGURE 5. Typical Application Bill of Materials -- Table 1 Ref Des Description Case Size Manufacturer Manufacturer P/N U1 SIMPLE SWITCHER (R) TO-PMOD-11 National Semiconductor LMZ23610TZ CIN1,6 (OPT) 0.047 F, 50V, X7R 1206 Yageo America CC1206KRX7R9BB473 CIN2,3,4 10 F, 50V, X7R 1210 Taiyo Yuden UMK325BJ106MM-T CIN5 (OPT) CAP, AL, 150F, 50V Radial G Panasonic EEE-FK1H151P CO1,5 (OPT) 0.047 F, 50V, X7R 1206 Yageo America CC1206KRX7R9BB473 CO2 (OPT) 47 F, 10V, X7R 1210 Murata GRM32ER61A476KE20L CO3,4 330 F, 6.3V, 0.015 ohm CAPSMT_6_UE Kemet T520D337M006ATE015 RFBT 3.32 k 0805 Panasonic ERJ-6ENF3321V RFBB 1.07 k 0805 Panasonic ERJ-6ENF1071V RSYNC 1.50 k 0805 Vishay Dale CRCW08051K50FKEA RENT 42.2 k 0805 Panasonic ERJ-6ENF4222V RENB 12.7 k 0805 Panasonic ERJ-6ENF1272V CSS 0.47 F, 10%, X7R, 16V 0805 AVX 0805YC474KAT2A D1 (OPT) 5.1V, 0.5W SOD-123 Diodes Inc. MMSZ5231BS-7-F www.national.com 20 LMZ23610 30151188 30151189 FIGURE 6. Layout example 21 www.national.com LMZ23610 www.national.com 22 LMZ23610 Physical Dimensions inches (millimeters) unless otherwise noted 11-Lead TZA Package NS Package Number TZA11A 23 www.national.com LMZ23610 10A SIMPLE SWITCHER(R) Power Module with 36V Maximum Input Voltage and Current Sharing Notes For more National Semiconductor product information and proven design tools, visit the following Web sites at: www.national.com Products Design Support Amplifiers www.national.com/amplifiers WEBENCH(R) Tools www.national.com/webench Audio www.national.com/audio App Notes www.national.com/appnotes Clock and Timing www.national.com/timing Reference Designs www.national.com/refdesigns Data Converters www.national.com/adc Samples www.national.com/samples Interface www.national.com/interface Eval Boards www.national.com/evalboards LVDS www.national.com/lvds Packaging www.national.com/packaging Power Management www.national.com/power Green Compliance www.national.com/quality/green Switching Regulators www.national.com/switchers Distributors www.national.com/contacts LDOs www.national.com/ldo Quality and Reliability www.national.com/quality LED Lighting www.national.com/led Feedback/Support www.national.com/feedback Voltage References www.national.com/vref Design Made Easy www.national.com/easy www.national.com/powerwise Applications & Markets www.national.com/solutions Mil/Aero www.national.com/milaero PowerWise(R) Solutions Serial Digital Interface (SDI) www.national.com/sdi Temperature Sensors www.national.com/tempsensors SolarMagicTM www.national.com/solarmagic PLL/VCO www.national.com/wireless www.national.com/training PowerWise(R) Design University THE CONTENTS OF THIS DOCUMENT ARE PROVIDED IN CONNECTION WITH NATIONAL SEMICONDUCTOR CORPORATION ("NATIONAL") PRODUCTS. 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