ADC081000CIYB/NOPB - NATIONAL SEMICONDUCTOR

ADC081000

ADC081000 High Performance, Low Power 8-Bit, 1 GSPS A/D Converter

Literature Number: SNAS209F

ADC081000

April 21, 2009

High Performance, Low Power 8-Bit, 1 GSPS A/D Converter

General Description

The ADC081000 is a low power, high performance CMOS

analog-to-digital converter that digitizes signals to 8 bits res-

olution at sampling rates up to 1.6 GSPS. Consuming a typical

1.4 Watts at 1 GSPS from a single 1.9 Volt supply, this device

is guaranteed to have no missing codes over the full operating

temperature range. The unique folding and interpolating ar-

chitecture, the fully differential comparator design, the inno-

vative design of the internal sample-and-hold amplifier and

the self-calibration scheme enable a very flat response of all

dynamic parameters beyond Nyquist, producing a high 7.5

ENOB with a 500 MHz input signal and a 1 GHz sample rate

while providing a 10-18 B.E.R. Output formatting is offset bi-

nary and the LVDS digital outputs are compliant with IEEE

1596.3-1996, with the exception of a reduced common mode

voltage of 0.8V.

The converter has a 1:2 demultiplexer that feeds two LVDS

buses, reducing the output data rate on each bus to half the

sampling rate. The data on these buses are interleaved in

time to provide a 500 MHz output rate per bus and a combined

output rate of 1 GSPS.

The converter typically consumes less than 10 mW in the

Power Down Mode and is available in a 128-lead, thermally

enhanced exposed pad LQFP and operates over the indus-

trial (-40°C ≤ TA ≤ +85°C) temperature range.

Features

■Internal Sample-and-Hold

■Single +1.9V ±0.1V Operation

■Adjustable Output Levels

■Guaranteed No Missing Codes

■Low Power Standby Mode

Key Specifications

■Resolution 8 Bits

■Max Conversion Rate 1 GSPS (min)

■ENOB @ 500 MHz Input 7.5 Bits (typ)

■DNL ±0.25 LSB (typ)

■Conversion Latency 7 and 8 Clock Cycles

■Power Consumption

■—Operating 1.45 W (typ)

—Power Down Mode 9 mW (typ)

Applications

■Direct RF Down Conversion

■Digital Oscilloscopes

■Satellite Set-top boxes

■Communications Systems

■Test Instrumentation

Block Diagram

20068153

ADC081000 High Performance, Low Power 8-Bit, 1 GSPS A/D Converter

Ordering Information

Extended Commercial Temperature Range (-40°C < TA < +85°C) NS Package

ADC081000CIYB 128-Pin Exposed Pad LQFP

ADC08D1000DEV (use Dual product) Development Board

Pin Configuration

20068101

* Exposed pad on back of package must be soldered to ground plane to ensure rated performance.

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ADC081000

Pin Descriptions and Equivalent Circuits

Pin Functions

Pin No. Symbol Equivalent Circuit Description

3 OutV

Output Voltage Amplitude set. Tie this pin high for normal

differential output amplitude. Ground this pin for a reduced

differential output amplitude and reduced power

consumption. See Section 1.5.

4 OutEdge

Output Edge Select. Sets the edge of the DCLK+ (pin 82) at

which the output data transitions. The output transitions with

the DCLK+ rising edge when this pin is high or on the falling

edge when this pin is low. See Section 5.3.

14 DC_Coup

DC Coupling select. When this pin is high, the VIN+ and VIN-

analog inputs are d.c. coupled and the input common mode

voltage should equal the VCMO (pin 7) output voltage. When

this pin is low, the analog input pins are internally biased and

the input signal should be a.c. coupled to the analog input

pins. See Section 3.0.

26 PD

Power Down Pin. A logic high on this pin puts the ADC into

the Power Down mode. A logic low on this pin allows normal

operation.

30 CAL

Calibration. A minimum 10 clock cycles low followed by a

minimum of 10 clock cycles high on this pin will initiate the

self calibration sequence. See Section 1.1.

35 FSR

Full scale Range Select. With a logic low on this pin, the full-

scale differential input is 600 mVP-P. With a logic high on this

pin, the full-scale differential input is 800 mVP-P. See Section

1.3.

127 CalDly Calibration Delay. This sets the number of clock cycles after

power up before calibration begins. See Section 1.1.

CLK+

CLK-

Clock input pins for the ADC. The differential clock signal

must be a.c. coupled to these pins. The input signal is

sampled on the falling edge of CLK+.

VIN+

VIN-Analog Signal Differential Inputs to the ADC.

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ADC081000

Pin Functions

Pin No. Symbol Equivalent Circuit Description

7VCMO

Common Mode Output voltage for VIN+ and VIN- when d.c.

input coupling is used, in which case the voltage at this pin

is required to be the common mode input voltage at VIN+ and

VIN−. See Section 3.0.

31 VBG

Bandgap output voltage. This pin is capable of sourcing or

sinking up to 1.0 µA.

126 CalRun Calibration Running indication. This pin is at a logic high

when calibration is running.

32 REXT

External Bias Resistor connection. The required value is

3.3k-Ohms (±0.1%) to ground. See Section 1.1.

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ADC081000

Pin Functions

Pin No. Symbol Equivalent Circuit Description

100

101

102

103

D7-

D7+

D6-

D6+

D5-

D5+

D4-

D4+

D3-

D3+

D2-

D2+

D1-

D1+

D0-

D0+

LVDS data output bits sampled second in time sequence.

These outputs should always be terminated with a differential

100Ω resistance.

104

105

106

107

111

112

113

114

115

116

117

118

122

123

124

125

Dd7-

Dd7+

Dd6-

Dd6+

Dd5-

Dd5+

Dd4-

Dd4+

Dd3-

Dd3+

Dd2-

Dd2+

Dd1-

Dd1+

Dd0-

Dd0+

LVDS data output bits sampled first in time sequence. These

outputs should always be terminated with a differential

100Ω resistance.

OR+

OR-

Out of Range output. A differential high at these pins

indicates that the differential input is out of range (outside the

range of ±300 mV or ±400 mV as defined by the FSR pin).

See Section 1.6.

DCLK+

DCLK-

Differential Clock Outputs used to latch the output data.

Delayed and non-delayed data outputs are supplied

synchronous to this signal.

2, 5, 8, 13, 16,

17, 20, 25, 28,

33, 128

VA Analog power supply pins. Bypass these pins to GND.

40, 51, 62, 73,

88, 99, 110, 121 VDR Output Driver power supply pins. Bypass these pins to DR

GND.

1, 6, 9, 12, 15,

21, 24, 27 GND Ground return for VA

42, 53, 64, 74,

87, 97, 108, 119 DR GND Ground return for VDR

22, 23, 29, 34,

36 - 39,

41, 43 - 50, 52,

54 - 61, 63,

65 - 72,

75 - 78, 98, 109,

120

NC No Connection. Make no connection to these pins.

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ADC081000

Absolute Maximum Ratings

(Notes 1, 2)

If Military/Aerospace specified devices are required,

please contact the National Semiconductor Sales Office/

Distributors for availability and specifications.

Analog Supply Voltage (VA, VDR)2.2V

Digital Supply above Analog Supply

(VDR - VA)300 mV

Voltage on Any Input Pin

(Except VIN+, VIN-)

−0.15V to

(VA +0.15V)

Voltage on VIN+, VIN-

(Maintaining Common Mode) -0.15V to 2.5V

Ground Difference

|GND - DR GND| 0V to 100 mV

Input Current at Any Pin (Note 3) ±25 mA

Package Input Current (Note 3) ±50 mA

Power Dissipation at TA = 25°C 2.0 W

ESD Susceptibility (Note 4)

Human Body Model

Machine Model

2500V

250V

Soldering Temperature, Infrared,

10 seconds (Note 5) 235°C

Storage Temperature −65°C to +150°C

Operating Ratings (Notes 1, 2)

Ambient Temperature Range −40°C ≤ TA ≤ +85°C

Supply Voltage (VA)+1.8V to +2.0V

Driver Supply Voltage (VDR) +1.8V to VA

Analog Input Common Mode Voltage 1.2V to 1.3V

VIN+, VIN- Voltage Range

(Maintaining Common Mode)

0V to 2.15V

(100% duty cycle)

0V to 2.5V

(10% duty cycle)

Ground Difference

(|GND - DR GND|) 0V

CLK Pins Voltage Range 0V to VA

Differential CLK Amplitude 0.6VP-P to 2.0VP-P

Package Thermal Resistances

Package

θJ-C

(Top of

Package)

θJ-PAD

(Thermal Pad)

128-Lead Exposed Pad

LQFP 10°C / W 2.8°C / W

Soldering process must comply with National

Semiconductor’s Reflow Temperature Profile specifications.

Refer to www.national.com/packaging.

Converter Electrical Characteristics

The following specifications apply after calibration for VA = VDR = +1.9VDC, OutV = 1.9V, VIN FSR (a.c. coupled) = differential

800mVP-P, CL = 10 pF, Differential, a.c. coupled Sinewave Clock, fCLK = 1 GHz at 0.5VP-P with 50% duty cycle, REXT = 3300Ω ±

0.1%, Analog Signal Source Impedance = 100Ω. Boldface limits apply for TA = TMIN to TMAX. All other limits TA = 25°C, unless

otherwise stated. (Notes 6, 7)

Symbol Parameter Conditions Typical

(Note 8)

Limits

(Note 8)

Units

(Limits)

STATIC CONVERTER CHARACTERISTICS

INL Integral Non-Linearity ±0.35 ±0.9 LSB (max)

DNL Differential Non-Linearity ±0.25 ±0.7 LSB (max)

Resolution with No Missing Codes 8Bits

VOFF Offset Error −0.45 −1.5

0.5

LSB (min)

LSB (max)

TC VOFF Offset Error Tempco −40°C to +85°C −3 ppm/°C

PFSE Positive Full-Scale Error (Note 9) −2.2 ±25 mV (max)

NFSE Negative Full-Scale Error (Note 9) −1.1 ±25 mV (max)

TC PFSE Positive Full Scale Error Tempco −40°C to +85°C 20 ppm/°C

TC NFSE Negative Full Scale Error Tempco −40°C to +85°C 13 ppm/°C

Dynamic Converter Characteristics

FPBW Full Power Bandwidth 1.7 GHz

B.E.R. Bit Error Rate 10-18 Error/Bit

Gain Flatness d.c. to 500 MHz ±0.5 dBFS

d.c. to 1 GHz ±1.0 dBFS

ENOB Effective Number of Bits

fIN = 100 MHz, VIN = FSR − 0.5 dB 7.5 Bits

fIN = 248 MHz, VIN = FSR − 0.5 dB 7.5 7.1 Bits (min)

fIN = 498 MHz, VIN = FSR − 0.5 dB 7.5 7.1 Bits (min)

SINAD Signal-to-Noise Plus Distortion Ratio

fIN = 100 MHz, VIN = FSR − 0.5 dB 47 dB

fIN = 248 MHz, VIN = FSR − 0.5 dB 47 44.8 dB (min)

fIN = 498 MHz, VIN = FSR − 0.5 dB 47 44.8 dB (min)

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ADC081000

Symbol Parameter Conditions Typical

(Note 8)

Limits

(Note 8)

Units

(Limits)

SNR Signal-to-Noise Ratio

fIN = 100 MHz, VIN = FSR − 0.5 dB 48 dB

fIN = 248 MHz, VIN = FSR − 0.5 dB 48 45.5 dB (min)

fIN = 498 MHz, VIN = FSR − 0.5 dB 48 45.5 dB (min)

THD Total Harmonic Distortion

fIN = 100 MHz, VIN = FSR − 0.5 dB -57 dB

fIN = 248 MHz, VIN = FSR − 0.5 dB -57 −50 dB (max)

fIN = 498 MHz, VIN = FSR − 0.5 dB -57 −50 dB (max)

2nd Harm Second Harmonic Distortion

fIN = 100 MHz, VIN = FSR − 0.5 dB −64 dB

fIN = 248 MHz, VIN = FSR − 0.5 dB −64 dB

fIN = 498 MHz, VIN = FSR − 0.5 dB −64 dB

3rd Harm Third Harmonic Distortion

fIN = 100 MHz, VIN = FSR − 0.5 dB −64 dB

fIN = 248 MHz, VIN = FSR − 0.5 dB −64 dB

fIN = 498 MHz, VIN = FSR − 0.5 dB −64 dB

SFDR Spurious-Free dynamic Range

fIN = 100 MHz, VIN = FSR − 0.5 dB 58.5 dB

fIN = 248 MHz, VIN = FSR − 0.5 dB 58.5 50 dB (min)

fIN = 498 MHz, VIN = FSR − 0.5 dB 58.5 50 dB (min)

IMD Intermodulation Distortion fIN1 = 121 MHz, VIN = FSR − 7 dB

fIN2 = 126 MHz, VIN = FSR − 7 dB -51 dB

Out of Range Output Code

(In addition to OR Output high)

(VIN+) − (VIN−) > + Full Scale 255

(VIN+) − (VIN−) < − Full Scale 0

ANALOG INPUT AND REFERENCE CHARACTERISTICS

VIN

Full Scale Analog Differential Input

Range

FSR pin Low 600 550 mVP-P (min)

650 mVP-P (max)

FSR pin High 800 750 mVP-P (min)

850 mVP-P (max)

VCMI Common Mode Analog Input Voltage VCMO

VCMO − 50

VCMO+ 50

mV (min)

mV (max)

CIN

Analog Input Capacitance

(Note 10)

Differential 0.02 pF

Each input to ground 1.6 pF

RIN Differential Input Resistance 100 94 Ω (min)

106 Ω (max)

ANALOG OUTPUT CHARACTERISTICS

VCMO Common Mode Output Voltage ICMO = ±1 µA 1.21 0.95

1.45

V (min)

V (max)

TC VCMO

Common Mode Output Voltage

Temperature Coefficient TA = −40°C to +85°C 118 ppm/°C

VBG Bandgap Reference Output Voltage IBG = ±100 µA 1.26 1.22

1.33

V (min)

V (max)

TC VBG

Bandgap Reference Voltage

Temperature Coefficient

TA = −40°C to +85°C,

IBG = ±100 µA -28 ppm/°C

CLOCK INPUT CHARACTERISTICS

VID Differential Clock Input Level

Square Wave Clock 0.6 0.4

2.0

VP-P (min)

VP-P (max)

Sine Wave Clock 0.6 0.4

2.0

VP-P (min)

VP-P (max)

IIInput Current VIN = 0V or VIN = VA±1 µA

CIN Input Capacitance (Note 10) Differential 0.02 pF

Each Input to Ground 1.5 pF

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ADC081000

Symbol Parameter Conditions Typical

(Note 8)

Limits

(Note 8)

Units

(Limits)

DIGITAL CONTROL PIN CHARACTERISTICS

VIH Logic High Input Voltage (Note 12) 1.4 V (min)

VIL Logic Low Input Voltage (Note 12) 0.5 V (max)

IIInput Current VIN = 0 or VIN = VA±1 µA

CIN Logic Input Capacitance (Note 13) Each input to ground 1.2 pF

DIGITAL OUTPUT CHARACTERISTICS

VOD LVDS Differential Output Voltage

OutV = VA, measured single-ended 300 200 mVP-P (min)

450 mVP-P (max)

OutV = GND, measured single-ended 225 140 mVP-P (min)

340 mVP-P (max)

Δ VOD DIFF

Change in LVDS Output Swing

Between Logic Levels ±1 mV

VOS Output Offset Voltage 800 mV

Δ VOS

Output Offset Voltage Change

Between Logic Levels ±1 mV

IOS Output Short Circuit Current Output+ & Output- connected to 0.8V −4 mA

ZODifferential Output Impedance 100 Ohms

POWER SUPPLY CHARACTERISTICS

IAAnalog Supply Current PD = Low

PD = High

646

4.5

792 mA (max)

IDR Output Driver Supply Current PD = Low 108 160 mA (max)

PD = High 0.1 mA

PDPower Consumption PD = Low 1.43 1.8 W (max)

PD = High 8.7 mW

PSRR1 D.C. Power Supply Rejection Ratio Change in Offset Error with change in

VA from 1.8V to 2.0V 73 dB

AC ELECTRICAL CHARACTERISTICS

fCLK1 Maximum Conversion Rate

TA = 85°C 1.1 1.0 GHz (min)

TA ≤ 75°C 1.3 GHz

TA ≤ 70°C 1.6 GHz

fCLK2 Minimum Conversion Rate 200 MHz

Input Clock Duty Cycle 200 MHz ≤ Input clock frequency < 1

GHz 50 20

% (min)

% (max)

tCL Input Clock Low Time (Note 12) 500 200 ps (min)

tCH Input Clock High Time (Note 12) 500 200 ps (min)

DCLK Duty Cycle (Note 12) 50 45

% (min)

% (max)

tLHT

Differential Low to High Transition

Time 10% to 90%, CL = 2.5 pF 250 ps

tHLT

Differential High to Low Transition

Time 10% to 90%, CL = 2.5 pF 250 ps

tOSK

DCLK to Data Output Skew

(Note 11)

50% of DCLK transition to 50% of Data

transition 0±200 ps (max)

tAD Sampling (Aperture) Delay Input CLK+ Fall to Acquisition of Data 930 ps

tAJ Aperture Jitter 0.4 ps rms

tOD Input Clock to Data Output Delay 50% of Input Clock transition to 50% of

Data transition 2.7 ns

Pipeline Delay (Latency) (Note 11) "D" Outputs 7Clock Cycles

"Dd" Outputs 8

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ADC081000

Symbol Parameter Conditions Typical

(Note 8)

Limits

(Note 8)

Units

(Limits)

tWU

PD low to Rated Accuracy Conversion

(Wake-Up Time) 500 ns

tCAL Calibration Cycle Time 46,000 Clock Cycles

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. There is no guarantee of operation at the Absolute Maximum

Ratings. Operating Ratings indicate conditions for which the device is functional, but do not guarantee specific performance limits. For guaranteed specifications

and test conditions, see the Electrical Characteristics. The guaranteed specifications apply only for the test conditions listed. Some performance characteristics

may degrade when the device is not operated under the listed test conditions.

Note 2: All voltages are measured with respect to GND = DR GND = 0V, unless otherwise specified.

Note 3: When the input voltage at any pin exceeds the power supply limits (that is, less than GND or greater than VA), the current at that pin should be limited to

25 mA. The 50 mA maximum package input current rating limits the number of pins that can safely exceed the power supplies with an input current of 25 mA to

two. This limit is not placed upon the power, ground and digital output pins.

Note 4: Human body model is 100 pF capacitor discharged through a 1.5 kΩ resistor. Machine model is 220 pF discharged through ZERO Ohms.

Note 5: See the section entitled "Surface Mount" found in any post 1986 National Semiconductor Linear Data Book for methods of soldering surface mount

devices.

Note 6: The analog inputs are protected as shown below. Input voltage magnitudes beyond the Absolute Maximum Ratings may damage this device.

20068104

Note 7: To guarantee accuracy, it is required that VA and VDR be well bypassed. Each supply pin must be decoupled with separate bypass capacitors. Additionally,

achieving rated performance requires that the backside exposed pad be well grounded.

Note 8: Typical figures are at TJ = 25°C, and represent most likely parametric norms. Test limits are guaranteed to National's AOQL (Average Outgoing Quality

Level).

Note 9: Calculation of Full-Scale Error for this device assumes that the actual reference voltage is exactly its nominal value. Full-Scale Error for this device,

therefore, is a combination of Full-Scale Error and Reference Voltage Error. See Transfer Characteristic Figure 2. For relationship between Gain Error and Full-

Scale Error, see Specification Definitions for Gain Error.

Note 10: The analog and clock input capacitances are die capacitances only. Additional package capacitances of 0.65 pF differential and 0.95 pF each pin to

ground are isolated from the die capacitances by lead and bond wire inductances.

Note 11: This parameter is guaranteed by design and is not tested in production.

Note 12: This parameter is guaranteed by design and characterization and is not tested in production.

Note 13: The digital control pin capacitances are die capacitances only. Additional package capacitance of 1.6 pF each pin to ground are isolated from the die

capacitances by lead and bond wire inductances.

Note 14: The ADC081000 has two interleaved LVDS output buses, which each clock data out at one half the sample rate. The data at each bus is clocked out

at one half the sample rate. The second bus (D0 through D7) has a pipeline latency that is one clock cycle less than the latency of the first bus (Dd0 through

Dd7).

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ADC081000

Specification Definitions

APERTURE (SAMPLING) DELAY is that time required after

the fall of the clock input for the sampling switch to open. The

Sample/Hold circuit effectively stops capturing the input sig-

nal and goes into the “hold” mode the aperture delay time

(tAD) after the clock goes low.

APERTURE JITTER (tAJ) is the variation in aperture delay

from sample to sample. Aperture jitter shows up as input

noise.

Bit Error Rate (B.E.R.) is the probability of error and is de-

fined as the probable number of errors per unit of time divided

by the number of bits seen in that amount of time. A B.E.R. of

10-18 corresponds to a statistical error in one bit about every

four (4) years.

CLOCK DUTY CYCLE is the ratio of the time that the clock

wave form is at a logic high to the total time of one clock pe-

riod.

COMMON MODE VOLTAGE is the d.c. potential that is com-

mon to both pins of a differential pair. For a voltage to be a

common mode one, the signal departure from this d.c. com-

mon mode voltage at any given instant must be the same for

each of the pins, but in opposite directions from each other.

DIFFERENTIAL NON-LINEARITY (DNL) is the measure of

the maximum deviation from the ideal step size of 1 LSB.

Measured at 1 GSPS with a ramp input.

EFFECTIVE NUMBER OF BITS (ENOB, or EFFECTIVE

BITS) is another method of specifying Signal-to-Noise and

Distortion Ratio, or SINAD. ENOB is defined as (SINAD −

1.76) / 6.02 and says that the converter is equivalent to a per-

fect ADC of this (ENOB) number of bits.

FULL POWER BANDWIDTH (FPBW) is a measure of the

frequency at which the reconstructed output fundamental

drops 3 dB below its low frequency value for a full scale input.

GAIN ERROR is the deviation from the ideal slope of the

transfer function. It can be calculated from Offset and Full-

Scale Errors:

– PGE = OE − PFSE

– NGE = −(OE − NFSE) = NFSE − OE

– Gain Error = NFSE − PFSE = PGE + NGE

where PGE is Positive Gain Error, NGE is Negative Gain Er-

ror, OE is Offset Error, PFSE is Positive Full-Scale Error and

NFSE is Negative Full-Scale Error.

INTEGRAL NON-LINEARITY (INL) is a measure of the de-

viation of each individual code from a straight line through the

input to output transfer function. The deviation of any given

code from this straight line is measured from the center of that

code value. The best fit method is used.

INTERMODULATION DISTORTION (IMD) is the creation of

additional spectral components as a result of two sinusoidal

frequencies being applied to the ADC input at the same time.

it is defined as the ratio of the power in the second and third

order intermodulation products to the power in one of the

original frequencies. IMD is usually expressed in dBFS.

LSB (LEAST SIGNIFICANT BIT) is the bit that has the small-

est value or weight of all bits. This value is

LSB = VFS / 2n

where VFS is the differential full-scale amplitude VIN as set by

the FSR input and "n" is the ADC resolution in bits, which is

8 for the ADC081000.

LVDS DIFFERENTIAL OUTPUT VOLTAGE (VOD) is this ab-

solute value of the difference between the VD+ and VD−

outputs, each measured with respect to Ground.

LVDS OUTPUT OFFSET VOLTAGE (VOS) is the midpoint

between the the D+ and D− pins' output voltages; i.e.,

[ (VD+) + (VD−) ] / 2.

20068190

FIGURE 1.

MISSING CODES are those output codes that are skipped

and will never appear at the ADC outputs. These codes can-

not be reached with any input value.

MSB (MOST SIGNIFICANT BIT) is the bit that has the largest

value or weight. Its value is one half of full scale.

NEGATIVE FULL-SCALE ERROR is a measure of how far

the last code transition is from the ideal 1/2 LSB above a dif-

ferential −VIN/2. For the ADC081000 the reference voltage is

assumed to be ideal, so this error is a combination of full-scale

error and reference voltage error.

OFFSET ERROR (VOFF) is a measure of how far the mid-

scale point is from the ideal zero voltage differential input.

OUTPUT DELAY (tOD) is the time delay after the falling edge

of the DCLK before the data update is present at the output

pins.

OVER-RANGE RECOVERY TIME is the time required after

the differential input voltages goes from ±1.2V to 0V for the

converter to recover and make a conversion with its rated ac-

curacy.

PIPELINE DELAY (LATENCY) is the number of clock cycles

between initiation of conversion and when that data is pre-

sented to the output driver stage. New data is available at

every clock cycle, but the data lags the conversion by the

Pipeline Delay plus the tOD.

POSITIVE FULL-SCALE ERROR (PFSE) is a measure of

how far the last code transition is from the ideal 1-1/2 LSB

below a differential +VIN/2. For the ADC081000 the reference

voltage is assumed to be ideal, so this error is a combination

of full-scale error and reference voltage error.

POWER SUPPLY REJECTION RATIO (PSRR) can be one

of two specifications. PSRR1 (DC PSRR) is the ratio of the

change in offset error that results from a power supply voltage

change from 1.8V to 2.0V. PSRR2 (AC PSRR) is a measure

of how well an a.c. signal riding upon the power supply is re-

jected from the output and is measured with a 248 MHz, 50

mVP-P signal riding upon the power supply. It is the ratio of the

output amplitude of that signal at the output to its amplitude

on the power supply pin. PSRR is expressed in dB.

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ADC081000

SIGNAL TO NOISE RATIO (SNR) is the ratio, expressed in

dB, of the rms value of the input signal at the output to the rms

value of the sum of all other spectral components below one-

half the sampling frequency, not including harmonics or d.c.

SIGNAL TO NOISE PLUS DISTORTION (S/(N+D) or

SINAD) is the ratio, expressed in dB, of the rms value of the

input signal at the output to the rms value of all of the other

spectral components below half the clock frequency, includ-

ing harmonics but excluding d.c.

SPURIOUS FREE DYNAMIC RANGE (SFDR) is the differ-

ence, expressed in dB, between the rms values of the input

signal at the output and the peak spurious signal, where a

spurious signal is any signal present in the output spectrum

that is not present at the input, excluding d.c.

TOTAL HARMONIC DISTORTION (THD) is the ratio ex-

pressed in dB, of the rms total of the first nine harmonic levels

at the output to the level of the fundamental at the output. THD

is calculated as

where Af1 is the RMS power of the fundamental (output) fre-

quency and Af2 through Af10 are the RMS power of the first 9

harmonic frequencies in the output spectrum.

– Second Harmonic Distortion (2nd Harm) is the differ-

ence, expressed in dB, between the RMS power in the input

frequency seen at the output and the power in its 2nd har-

monic level at the output.

– Third Harmonic Distortion (3rd Harm) is the difference

expressed in dB between the RMS power in the input fre-

quency seen at the output and the power in its 3rd harmonic

level at the output.

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ADC081000

Transfer Characteristic

20068156

FIGURE 2. Input / Output Transfer Characteristic

Timing Diagrams

20068114

FIGURE 3. ADC081000 Timing

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ADC081000

Typical Performance Characteristics VA = VDR = +1.9V, fCLK = 1 GHz (differential clock),

fIN = 248 MHz, Differential Inputs, unless otherwise stated. Parameters shown across temperature were measured after

recalibration at each temperature.

INL

20068117

INL vs. Temperature

20068118

INL vs. Supply Voltage

20068119

INL vs. Output Driver Voltage

20068120

INL vs. Sample Rate

20068121

DNL

20068122

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ADC081000

DNL vs. Temperature

20068123

DNL vs. Supply Voltage

20068124

DNL vs. Output Driver Voltage

20068125

DNL vs. Sample Rate

20068126

SNR vs. Temperature

20068127

SNR vs. Supply Voltage

20068128

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ADC081000

SNR vs. Output Driver Voltage

20068129

SNR vs. Sample Rate

20068130

SNR vs. Clock Duty Cycle

20068131

SNR vs. Input Frequency

20068132

Distortion vs. Temperature

20068133

Distortion vs. Supply Voltage

20068134

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ADC081000

Distortion vs. Output Driver Voltage

20068135

Distortion vs. Sample Rate

20068136

Distortion vs. Clock Duty Cycle

20068137

Distortion vs. Input Frequency

20068138

Distortion vs. Input Common Mode

20068181

SINAD vs. Temperature

20068139

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ADC081000

SINAD vs. Supply Voltage

20068140

SINAD vs. Output Driver Voltage

20068141

SINAD vs. Sample Rate

20068142

SINAD vs. Clock Duty Cycle

20068143

SINAD vs. Input Frequency

20068160

ENOB vs. Temperature

20068161

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ADC081000

ENOB vs. Supply Voltage

20068162

ENOB vs. Output Driver Voltage

20068163

ENOB vs. Sample Rate

20068164

ENOB vs. Clock Duty Cycle

20068165

ENOB vs. Input Frequency

20068166

ENOB vs. Input Common Mode

20068182

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ADC081000

SFDR vs. Temperature

20068167

SFDR vs. Supply Voltage

20068168

SFDR vs. Output Driver Voltage

20068169

SFDR vs. Sample Rate

20068170

SFDR vs. Clock Duty Cycle

20068171

SFDR vs. Input Frequency

20068172

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ADC081000

Power Consumption vs. Sample Rate

20068174

Spectral Response @ fIN = 100 MHz

20068175

Spectral Response @ fIN = 248 MHz

20068176

Spectral Response @ fIN = 498 MHz

20068177

Spectral Response @ fIN = 1.5 GHz

20068178

Spectral Response @ fIN = 1.6 GHz

20068179

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ADC081000

Intermodulation Distortion

20068183

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ADC081000

Functional Description

The ADC081000 is a versatile, high performance, easy to use

A/D Converter with an innovative architecture permitting very

high speed operation. The controls available ease the appli-

cation of the device to circuit solutions. The ADC081000 uses

a calibrated folding and interpolating architecture that

achieves over 7.5 effective bits. The use of folding amplifiers

greatly reduces the number of comparators and power con-

sumption, while Interpolation reduces the number of front-end

amplifiers required, minimizing the load on the input signal

and further reducing power requirements. In addition to other

things, on-chip calibration reduces the INL bow often seen

with folding architectures. The result is an extremely fast, high

performance, low power converter. Optimum performance re-

quires adherence to the provisions discussed here and in the

Applications Information Section.

1.0 OVERVIEW

The analog input signal that is within the converter's input

voltage range is digitized to eight bits at speeds of 200 MSPS

to 1.6 GSPS, typical. Differential input voltages below nega-

tive full-scale will cause the output word to consist of all

zeroes. Differential input voltages above positive full-scale

will cause the output word to consist of all ones. The OR (Out

of Range) output is activated whenever the correct output

code would be outside of the 00h to FFh range.

The converter has a 1:2 demultiplexer that feeds two LVDS

output buses. The data on these buses provide an output

word rate on each bus at half the ADC sampling rate and must

be interleaved by the user to provide output words at the full

conversion rate.

The output levels may be selected to be normal or reduced.

Using reduced levels saves power but could result in erro-

neous data capture of some or all of the bits, especially at

higher sample rates and in marginally designed systems.

The voltage reference for the ADC081000 is derived from a

1.254V bandgap reference which is made available to the us-

er at the VBG pin. This output is capable of sourcing or sinking

±100 μA.

The internal bandgap derived reference voltage has a nomi-

nal value of 600 mV or 800 mV, as determined by the FSR

pin and described in Section 1.3. There is no provision for the

use of an external reference voltage.

The fully differential comparator design and the innovative

design of the sample-and-hold amplifier, together with self

calibration, enables flat SINAD/ENOB response beyond 1.0

GHz. The ADC081000 output data signaling is LVDS and the

output format is offset binary.

1.1 Self-Calibration

A self-calibration is performed upon power-up and can also

be invoked by the user upon command. Calibration trims the

100Ω analog input differential termination resistor and mini-

mizes full-scale error, offset error, DNL and INL, resulting in

maximizing SNR, THD, SINAD (SNDR), SFDR and ENOB.

Internal bias currents are also set with the calibration process.

All of this is true whether the calibration is performed upon

power up or is performed upon command.

Running the self calibration is important for this chip's func-

tionality and is required in order to obtain adequate perfor-

mance. In addition to the requirement to be run at power-up,

self calibration must be re-run whenever the sense of the FSR

pin is changed.

For best performance, we recommend that self calibration be

run 20 seconds or more after application of power and when-

ever the operating ambient temperature changes more than

30°C since calibration was last performed. See Section 5.1.2

for more information.

During the calibration process, the input termination resistor

is trimmed to a value that is equal to REXT / 33. This external

resistor must be placed between pin 32 and ground and must

be 3300 Ω ±0.1%. With this value, the input termination re-

sistor is trimmed to be 100 Ω. Because REXT is also used to

set the proper bias current for the Track and Hold amplifier,

for the preamplifiers and for the comparators, other values of

REXT should not be used.

In normal operation, calibration is performed just after appli-

cation of power and whenever a valid calibration command is

given, which is holding the CAL pin low for at least 10 clock

cycles, then holding it high for at least another 10 clock cycles.

There is no need to bring the CAL pin low after the 10 clock

cycles of CAL high to begin the calibration routine. Holding

the CAL pin high upon power up, however, will prevent the

calibration process from running until the CAL pin experi-

ences the above-mentioned 10 clock cycles low followed by

10 cycles high.

The CalDly pin is used to select one of two delay times after

the application of power to the start of calibration. This cali-

bration delay is 224 clock cycles (about 16.8 ms at 1 GSPS)

with CalDly low, or 230 clock cycles (about 1.07 seconds at 1

GSPS) with CalDly high. These delay values allow the power

supply to come up and stabilize before calibration takes place.

If the PD pin is high upon power-up, the calibration delay

counter will be disabled until the PD pin is brought low. There-

fore, holding the PD pin high during power up will further delay

the start of the power-up calibration cycle. The best setting of

the CalDly pin depends upon the power-on settling time of the

power supply.

The CalRun output is high whenever the calibration proce-

dure is running. This is true whether the calibration is done at

power-up or on-command.

Calibration can not be initiated or run while the device is in the

power-down mode. See Section 1.7 for information on the in-

teraction between Power Down and Calibration.

1.2 Acquiring the Input

Data is acquired at the falling edge of CLK+ (pin 18) and the

digital equivalent of that data is available at the digital outputs

7 clock cycles later for the "D" output bus and 8 clock cycles

later for the "Dd" output bus. There is an additional internal

delay called tOD before the data is available at the outputs.

See the Timing Diagram. The ADC081000 will convert as long

as the clock signal is present and the PD pin is low.

1.3 The Analog Inputs

The ADC081000 must be driven with a differential input sig-

nal. It is important that the inputs either be a.c. coupled to the

inputs with the DC_Coup pin grounded or d.c. coupled with

the DC_Coup pin high and have an input common mode volt-

age that is equal to and tracks the VCMO output.

Two full-scale range settings are provided with the FSR pin.

A high on that pin causes an input differential full-scale range

setting of 800 mVP-P, while grounding that pin causes an input

differential full-scale range setting of 600 mVP-P.

1.4 Clocking

The ADC081000 must be driven with an a.c. coupled, differ-

ential clock signal. Section 4 describes the use of the clock

input pins. A differential LVDS output clock is available for use

in latching the ADC output data into whatever receives that

data.

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ADC081000

To help ease data capture, the output data may be caused to

transition on either the positive or the negative edge of the

output data clock (DCLK). This is chosen with the OutEdge

input. A high on the OutEdge input causes the output data to

transition on the rising edge of DCLK, while grounding this

input causes the output to transition on the falling edge of

DCLK.

1.5 The LVDS Outputs

The data outputs, the Out Of Range (OR) and DCLK are

LVDS compliant outputs. Output current sources provide 3

mA of output current to a differential 100 Ohm load when the

OutV input is high or 2.2 mA when the OutV input is low. For

short LVDS lines and low noise systems, satisfactory perfor-

mance may be realized with the OutV input low, which results

in lower power consumption. If the LVDS lines are long and/

or the system in which the ADC081000 is used is noisy, it may

be necessary to tie the OutV pin high.

Note that the LVDS levels are not intended to meet any given

LVDS specification, but output levels are such that interfacing

with LVDS receivers is practical.

1.6 Out Of Range (OR) Indication

The input signal is out of range whenever the correct code

would be above positive full-scale or below negative full scale.

When the input signal for any given sample is thus out of

range, the OR output is high for that word time.

1.7 Power Down

The ADC081000 is in the active state when the Power Down

pin (PD) is low. When the PD pin is high, the device is in the

power down mode, where the device power consumption is

reduced to a minimal level and the outputs are in a high

impedance state. Upon return to normal operation, the

pipeline will contain meaningless information and must be

flushed.

If the PD input is brought high while a calibration is running,

the device will not go into power down until the calibration

sequence is complete. However, if power is applied and PD

is already high, the device will not begin the calibration se-

quence until the PD input goes low. If a manual calibration is

requested while the device is powered down, the calibration

will not begin at all. That is, the manual calibration input is

completely ignored in the power down state.

1.8 Summary of Control Pins and Convenience Outputs

Table 1 and Table 2 are provided as a guide to the use of the

various control and convenience pins of the ADC081000.

Note that this table is only a guide and that the rest of this data

sheet should be consulted for the full meaning and use of

these pins.

TABLE 1. Digital Control Pins

PIN DESCRIPTION LOW HIGH

3 OutV 440mV Outputs 600mV Outputs

4 OutEdge Data Transition

at DCLK Fall

Data Transition

at DCLK Rise

14 DC_Coup A.C. Coupled

Inputs

D.C. Coupled

Inputs

26 PD Normal

Operation Power Down

30 CAL Normal

Operation Run Calibration

35 FSR 600 mVP-P Full-

Scale In

800 mVP-P Full-

Scale In

127 CalDly 224 Clock

Cycles

230 Clock

Cycles

TABLE 2. Convenience Output Pins

PIN DESCRIPTION USE / INDICATION

7VCMO Common Mode Output Voltage.

31 VBG 1.25V Convenience Output.

OR+

OR−

Differential Out-Of-Range

Indication; active high.

126 CalRun Low is normal operation. High

indicates Calibration is running.

Applications Information

2.0 THE REFERENCE VOLTAGE

The voltage reference for the ADC081000 is derived from a

1.254V bandgap reference which is made available at the

VBG output for user convenience and has an output current

capability of ±100 μA. The VBG output should be buffered if

more current than this is required of it.

The internal bandgap-derived reference voltage causes the

full-scale peak-to-peak input swing to be either 600 mV or 800

mV, as determined by the FSR pin and described in Section

1.3. There is no provision for the use of an external reference

voltage.

3.0 THE ANALOG INPUT

The analog input is a differential one to which the signal

source may be a.c. coupled or d.c. coupled. Table 3 gives the

input to output relationship with the FSR pin high. With the

FSR pin grounded, the millivolt values in Table 3 are reduced

to 75% of the values indicated.

The buffered analog inputs simplify the task of driving these

inputs and the RC pole that is generally used at sampling ADC

inputs is not required. If it is desired to use an amplifier circuit

before the ADC, use care in choosing an amplifier with ade-

quate noise and distortion performance and adequate gain at

the frequencies used for the application.

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ADC081000

TABLE 3. DIFFERENTIAL INPUT TO OUTPUT

RELATIONSHIP (FSR High)

VIN+ VIN−Output Code

VCM − 200 mV VCM + 200 mV 0000 0000

VCM − 99 mV VCM + 99 mV 0100 0000

VCM VCM

0111 1111 /

1000 0000

VCM + 101 mV VCM − 101 mV 1100 0000

VCM + 200mV VCM − 200 mV 1111 1111

Note that a precise d.c. common mode voltage must be

present at the ADC inputs. This common mode voltage,

VCMO, is provided on-chip when DC_Coup (pin 14) is low and

the input signal is a.c. coupled to the ADC. See Figure 4.

20068149

FIGURE 4. Differential Input Drive

When pin 14 is high, the analog inputs are d.c. coupled and

a common mode voltage must be externally provided at the

analog input pins. This common mode voltage should track

the VCMO output voltage. Note that the VCMO output potential

will change with temperature. The common mode output of

the driving device should track this change. Full-scale distor-

tion performance falls off rapidly as the input common mode

voltage deviates from VCMO. This is a direct result of using a

very low supply voltage to minimize power. Keep the input

common voltage within 50 mV of VCMO.

Performance of the ADC081000 is as good in the d.c. coupled

mode as it is in the a.c. coupled mode, provided the input

common mode voltage at both analog input pins remain within

50 mV of VCMO.

If d.c. coupling is used, it is best to servo the input common

mode voltage, using the VCMO pin, to maintain optimum per-

formance.

Be sure that any current drawn from the VCMO output does not

exceed ±1 μA.

The Input impedance in the d.c. coupled mode (DC_Coup pin

high) consists of a precision 100 Ohm resistor between VIN+

and VIN- and a capacitance from each of these inputs to

ground. Driving the inputs beyond full scale will result in sat-

uration or clipping of the reconstructed output.

3.1 Handling Single-Ended Analog Signals

There is no provision for the ADC081000 to adequately pro-

cess single-ended input signals. The best way to handle

single-ended signals is to convert them to differential signals

before presenting them to the ADC. The easiest way to ac-

complish single-ended to differential signal conversion is with

an appropriate balun, as shown in Figure 5.

A balun is especially designed for very high frequencies and

has a wider bandwidth than does a transformer so is perferred

over a transformer for use with very high frequencies.

The ADC081000 is not designed to work with single-ended

signals, so it is NOT RECOMMENDED that this be done.

However, if the resulting drop in performance is allowable,

drive the ADC08100 with a single-ended signal by bypassing

the unused input to a.c. ground with a capacitor or connect it

directly to the VCMO pin. DO NOT connect either input pin di-

rectly to ground.

20068146

FIGURE 5. Single-Ended to Differential signal conversion

with a balun

When d.c. coupling to the ADC081000 analog inputs is re-

quired, single-ended to differential conversion may be easily

accomplished with the LMH6555, as shown in Figure 6. In

such applications, the LMH6555 performs the task of single-

ended to differential conversion while delivering low distortion

and noise, as well as output balance, that supports the oper-

ation of the ADC081000. Connecting the ADC081000 VCMO

pin to the VCM_REF pin of the LMH6555, through the appropri-

ate buffer, will ensure that the ADC081000 common mode

input voltage is as needed for optimum performance of the

ADC081000. See Figure 6. The LMV321 was chosen as the

buffer in Figure 6 for its low voltage operation and reasonable

offset voltage. Be sure to limit output current from the

ADC081000 VCMO pin to 1.0 μA.

20068155

FIGURE 6. Example of Servoing the Analog Input with

VCMO

3.2 Out Of Range (OR) Indication

When the conversion result is clipped the Out of Range output

is activated such that OR+ goes high and OR- goes low. This

output is active as long as accurate data on either or both of

the buses would be outside the range of 00h to FFh.

3.3 Full-Scale Input Range

As with all A/D Converters, the input range is determined by

the value of the ADC's reference voltage. The reference volt-

age of the ADC081000 is derived from an internal bandgap

reference. The FSR pin controls the effective reference volt-

age of the ADC081000 such that the differential full-scale

input range at the analog inputs is 800 mVP-P with the FSR

pin high, or is 600 mVP-P with FSR pin low. Best SNR is ob-

tained with FSR high, but better distortion and SFDR are

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ADC081000

obtained with the FSR pin low. The LMH6555 is suitable for

both settings.

4.0 THE CLOCK INPUTS

The ADC081000 has differential LVDS clock inputs, CLK+

and CLK-, which must be driven with an a.c. coupled, differ-

ential clock signal. Although the ADC081000 is tested and its

performance is guaranteed with a differential 1.0 GHz clock,

it typically will function well with clock frequencies indicated

in the Electrical Characteristics Table. The clock inputs are

internally terminated and biased. The clock signal must be

capacitive coupled to the clock pins as indicated in Figure 7.

Operation up to the sample rates indicated in the Electrical

Characteristics Table is typically possible if the conditions of

the Operating Ratings are not exceeded. Operating at higher

sample rates than indicated for the given ambient tempera-

ture may result in reduced device reliability and product life-

time. This is because of the higher power consumption and

die temperatures at high sample rates. Important also for re-

liability is proper thermal management . See Section 7.2.

20068147

FIGURE 7. Differential (LVDS) Clock Connection

The differential Clock line pair should have a characteristic

impedance of 100Ω and be terminated at the clock source in

that (100Ω) characteristic impedance. The clock line should

be as short and as direct as possible. The ADC081000 clock

input is internally terminated with an untrimmed 100Ω resis-

tor.

Insufficient clock levels will result in poor dynamic perfor-

mance. Excessively high clock levels could cause a change

in the analog input offset voltage. To avoid these problems,

keep the clock level within the range specified in the Operat-

ing Ratings.

While it is specified and performance is guaranteed at 1.0

GSPS with a 50% clock duty cycle, ADC081000 performance

is essentially independent of clock duty cycle. However, to

ensure performance over temperature, it is recommended

that the input clock duty cycle be such that the minimum clock

high and low times are maintained within the range specified

in the Electrical Characteristics Table.

High speed, high performance ADCs such as the ADC081000

require very stable clock signals with minimum phase noise

or jitter. ADC jitter requirements are defined by the ADC res-

olution (number of bits), maximum ADC input frequency and

the input signal amplitude relative to the ADC input full scale

range. The maximum jitter (the total of the jitter from all

sources) allowed to prevent a jitter-induced reduction in SNR

is found to be

tJ(MAX) = (VINFSR / VIN(P-P)) x (1/(2(N+1) x π x fIN))

where tJ(MAX) is the rms total of all jitter sources in seconds,

VIN(P-P) is the peak-to-peak analog input signal, VINFSR is the

full-scale range of the ADC, "N" is the ADC resolution in bits

and fIN is the maximum input frequency, in Hertz, to the ADC

analog input.

Note that the maximum jitter described above is the rms total

of the jitter from all sources, including that in the ADC clock,

that added by the system to the ADC clock and input signals

and that added by the ADC itself. Since the effective jitter

added by the ADC is beyond user control, the best the user

can do is to keep the sum of the externally added clock jitter

and the jitter added by the analog circuitry to the analog signal

to a minimum.

5.0 CONTROL PINS

Seven control pins provide a wide range of possibilities in the

operation of the ADC081000 and facilitate its use. These con-

trol pins provide Full-Scale Input Range setting, Self Calibra-

tion, Calibration Delay, Output Edge Synchronization choice,

LVDS Output Level choice and a Power Down feature.

5.1 Self Calibration

The ADC081000 self-calibration must be run to achieve rated

performance. This procedure is performed upon power-up

and can be run any time on command. The calibration pro-

cedure is exactly the same whether there is a clock present

upon power up or if the clock begins some time after appli-

cation of power. The CalRun output indicator is high while a

calibration is in progress.

5.1.1 Power-on Calibration

Power-on calibration begins after a time delay following the

application of power. This time delay is determined by the

setting of CalDly, as described in Section 1.1.

The calibration process will be not be performed if the CAL

pin is high at power up. In this case, the calibration cycle will

not begin until on-command calibration conditions are met.

The ADC081000 will function with the CAL pin held high at

power up, but no calibration will be done and performance will

be impaired. A manual calibration, however, may be per-

formed after powering up with the CAL pin high. See On-

Command Calibration Section 5.1.2.

The internal power-on calibration circuitry comes up in a ran-

dom state. If the clock is not running at power up and the

power on calibration circuitry is active, it will hold the analog

circuitry in power down and the power consumption will typi-

cally be less than 200 mW. The power consumption will be

normal after the clock starts.

5.1.2 On-Command Calibration

Calibration may be run at any time by bringing the CAL pin

high for a minimum of 10 clock cycles after it has been low for

a minimum of 10 clock cycles. Holding the CAL pin high upon

power up will prevent execution of power-on calibration until

the CAL pin is low for a minimum of 10 clock clock cycles,

then brought high for a minimum of another 10 clock cycles.

The calibration cycle will begin 10 clock cycles after the CAL

pin is thus brought high.

The minimum 10 clock cycle sequences are required to en-

sure that random noise does not cause a calibration to begin

when it is not desired. As mentioned in section 1.1, for best

performance, a self calibration should be performed 20 sec-

onds or more after power up and repeated when the ambient

temperature changes more than 30°C since the last self cal-

ibration was run. SINAD drops about 1.5 dB for every 30°C

change in die temperature and ENOB drops about 0.25 bit for

every 30°C change in die temperature.

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ADC081000

5.2 Calibration Delay

The CalDly input (pin 127) is used to select one of two delay

times after the application of power to the start of calibration,

as described in Section 1.1. The calibration delay values allow

the power supply to come up and stabilize before calibration

takes place. With no delay or insufficient delay, calibration

would begin before the power supply is stabilized at its oper-

ating value and result in non-optimal calibration coefficients.

If the PD pin is high upon power-up, the calibration delay

counter will be disabled until the PD pin is brought low. There-

fore, holding the PD pin high during power up will further delay

the start of the power-up calibration cycle. The best setting of

the CalDly pin depends upon the power-on settling time of the

power supply.

5.3 Output Edge Synchronization

DCLK signals are available to help latch the converter output

data into external circuitry. The output data can be synchro-

nized with either edge of these clock signals. That is, the

output data transition can be set to occur with either the rising

edge or the falling edge of the DCLK signal, so that either

edge of that clock signal can be used to latch the output data

into the receiving circuit.

When the OutEdge pin is high, the output data is synchro-

nized with (changes with) the rising edge of DCLK+. When

OutEdge is low, the output data is synchronized with the

falling edge of DCLK+.

At the very high speeds of which the ADC081000 is capable,

slight differences in the lengths of the clock and data lines can

mean the difference between successful and erroneous data

capture. The OutEdge pin is used to capture data on the

DCLK edge that best suits the application circuit and layout.

5.4 Power Down Feature

The Power Down (PD) pin, when high, puts the ADC081000

into a low power mode where power consumption is greatly

reduced.

The digital output pins retain the last conversion output code

when the clock is stopped, but are in a high impedance state

when the PD pin is high. However, upon return to normal op-

eration (re-establishment of the clock and/or lowering of the

PD pin), the pipeline will contain meaningless information and

must be flushed.

If the PD input is brought high while a calibration is running,

the device will not go into power down until the calibration

sequence is complete. However, if power is applied and PD

is already high, the device will not begin the calibration se-

quence until the PD input goes low. If a manual calibration is

requested while the device is powered down, the calibration

will not begin at all. That is, the manual calibration input is

completely ignored in the power down state.

6.0 THE DIGITAL OUTPUTS

The ADC081000 demultiplexes its output data onto two LVDS

output buses.

The results of successive conversions started on the odd

falling edges of the CLK+ pin are available on one of the two

LVDS buses, while the results of conversions started on the

even falling edges of the CLK+ pin are available on the other

LVDS bus. This means that the word rate at each LVDS bus

is 1/2 the ADC081000 clock rate and the two buses must be

interleaved to obtain the entire 1 GSPS conversion result.

Since the minimum recommended clock rate for this device

is 200 MSPS, the effective sample rate can be reduced to as

low as 100 MSPS by using the results available on just one

of the the two LVDS buses and a 200 MHz input clock, deci-

mating the 200 MSPS data by two.

There is one LVDS clock pair available for use to latch the

LVDS outputs on both buses. Whether the data is sent at the

rising or falling edge of DCLK+ is determined by the sense of

the OutEdge pin, as described in Section 5.3.

The OutV pin is used to set the LVDS differential output levels.

See Section 1.5.

The output format is Offset Binary. Accordingly, a full-scale

input level with VIN+ positive with respect to VIN− will produce

an output code of all ones, a full-scale input level with VIN−

positive with respect to VIN+ will produce an output code of all

zeros and when VIN+ and VIN− are equal, the output code will

vary between 127 and 128.

7.0 POWER CONSIDERATIONS

A/D converters draw sufficient transient current to corrupt

their own power supplies if not adequately bypassed. A 33 µF

capacitor should be placed within an inch (2.5 cm) of the A/D

converter power pins. A 0.1 μF capacitor should be placed as

close as possible to each VA pin, preferably within one-half

centimeter. Leadless chip capacitors are preferred because

they have low lead inductance. Having power and ground

planes in adjacent layers of the PC Board will provide the best

supply bypass capacitance in terms of low ESL.

The VA and VDR supply pins should be isolated from each

other to prevent any digital noise from being coupled into the

analog portions of the ADC. A ferrite choke, such as the JW

Miller FB20009-3B, is recommended between these supply

lines when a common source is used for them.

As is the case with all high speed converters, the ADC081000

should be assumed to have little power supply noise rejection.

Any power supply used for digital circuity in a system where

a lot of digital power is being consumed should not be used

to supply power to the ADC081000. The ADC supplies should

be the same supply used for other analog circuitry, if not a

dedicated supply.

7.1 Supply Voltage

The ADC081000 is specified to operate with a supply voltage

of 1.9V ±0.1V. It is very important to note that, while this de-

vice will function with slightly higher supply voltages, these

higher supply voltages may reduce product lifetime.

No pin should ever have a voltage on it that is in excess of the

supply voltage or below ground by more than 150 mV, not

even on a transient basis. This can be a problem upon appli-

cation of power and power shut-down. Be sure that the sup-

plies to circuits driving any of the input pins, analog or digital,

do not come up any faster than does the voltage at the

ADC081000 power pins.

20068154

FIGURE 8. Non-Spiking Power Supply

The Absolute Maximum Ratings should be strictly observed,

even during power up and power down. A power supply that

www.national.com 26

ADC081000

produces a voltage spike at turn-on and/or turn-off of power

can destroy the ADC081000. The circuit of Figure 8 will pro-

vide supply overshoot protection.

Many linear regulators will produce output spiking at power-

on unless there is a minimum load provided. Active devices

draw very little current until their supply voltages reach a few

hundred millivolts. The result can be a turn-on spike that can

destroy the ADC081000, unless a minimum load is provided

for the supply. The 100Ω resistor at the regulator output in

Figure 8 provides a minimum output current during power-up

to ensure there is no turn-on spiking.

In this circuit, an LM317 linear regulator is satisfactory if its

input supply voltage is 4V to 5V . If a 3.3V supply is used, an

LM1086 linear regulator is recommended. Also, be sure that

the impedance of the power distribution system is low to min-

imize resistive losses and minimize noise on the power sup-

ply.

The output drivers should have a supply voltage, VDR, that is

within the range specified in the Operating Ratings table. This

voltage should not exceed the VA supply voltage and should

never spike to a voltage greater than (VA + 100mV).

If the power is applied to the device without a clock signal

present, the current drawn by the device might be below 100

mA. This is because the ADC081000 gets reset through

clocked logic and its initial state is random. If the reset logic

comes up in the "on" state, it will cause most of the analog

circuitry to be powered down, resulting in less than 100 mA

of current draw. This current is greater than the power down

current because not all of the ADC is powered down. The de-

vice current will be normal after the clock is established.

7.2 Thermal Management

The ADC081000 is capable of impressive speeds and per-

formance at very low power levels for its speed. However, the

power consumption is still high enough to require attention to

thermal management. For reliability reasons, the die temper-

ature should be kept to a maximum of 130°C. That is, tA

(ambient temperature) plus ADC power consumption times

θJA (junction to ambient thermal resistance) should not ex-

ceed 130°C. This is not a problem if the ambient temperature

is kept to a maximum of +85°C, the device is soldered to a

PC Board and the sample rate is at or below 1 Gsps.

Note that the following are general recommendations for

mounting exposed pad devices onto a PCB. This should be

considered the starting point in PCB and assembly process

development. It is recommended that the process be devel-

oped based upon past experience in package mounting.

The package of the ADC081000 has an exposed pad on its

back that provides the primary heat removal path as well as

excellent electrical grounding to the printed circuit board. The

land pattern design for lead attachment to the PCB should be

the same as for a conventional LQFP, but the exposed pad

must be attached to the board to remove the maximum

amount of heat from the package, as well as to ensure best

product parametric performance.

To maximize the removal of heat from the package, a thermal

land pattern must be incorporated on the PC board within the

footprint of the package. The exposed pad of the device must

be soldered down to ensure adequate heat conduction out of

the package. The land pattern for this exposed pad should be

at least as large as the 5 x 5 mm of the exposed pad of the

package and be located such that the exposed pad of the

device is entirely over that thermal land pattern. This thermal

land pattern should be electrically connected to ground. A

clearance of at least 0.5 mm should separate this land pattern

from the mounting pads for the package pins.

Since a large aperture opening may result in poor release, the

aperture opening should be subdivided into an array of small-

er openings, similar to the land pattern of Figure 9.

20068151

FIGURE 9. Recommended Package Land Pattern

To minimize junction temperature, it is recommended that a

simple heat sink be built into the PCB. This is done by includ-

ing a minimum copper pad of 2 inches by 2 inches (5.1 cm by

5.1 cm) on the opposite side of the PCB. This copper area

may be plated or solder coated to prevent corrosion, but

should not have a conformal coating, which could provide

some thermal insulation. Thermal vias should be used to con-

nect these top and bottom copper areas. These thermal vias

act as "heat pipes" to carry the thermal energy from the device

side of the board to the opposite side of the board where it

can be more effectively dissipated. The use of 9 to 16 thermal

vias is recommended.

The thermal vias should be placed on a 1.2 mm grid spacing

and have a diameter of 0.30 to 0.33 mm. These vias should

be barrel plated to avoid solder wicking into the vias during

the soldering process as this wicking could cause voids in the

solder between the package exposed pad and the thermal

land on the PCB. Such voids could increase the thermal re-

sistance between the device and the thermal land on the

board, which would cause the device to run hotter.

On a board of FR-4 material and the built in heat sink de-

scribed above (4 square inch pad and 9 thermal vias), the die

temperature stabilizes at about 30°C above the ambient tem-

perature in about 20 seconds.

If it is desired to monitor die temperature, a temperature sen-

sor may be mounted on the heat sink area of the board near

the thermal vias. Allow for a thermal gradient between the

temperature sensor and the ADC081000 die of θJC times typ-

ical power consumption = 2.8 x 1.43 = 4°C. Allowing for a 5°

C (including an extra 1°C) temperature drop from the die to

the temperature sensor, then, would mean that maintaining a

maximum pad temperature reading of 125°C will ensure that

the die temperature does not exceed 130°C, assuming that

the exposed pad of the ADC081000 is properly soldered

down and the thermal vias are adequate.

8.0 LAYOUT AND GROUNDING

Proper grounding and proper routing of all signals are essen-

tial to ensure accurate conversion. A single ground plane

should be used, as opposed to splitting the ground plane into

analog and digital areas.

Since digital switching transients are composed largely of

high frequency components, the skin effect tells us that total

ground plane copper weight will have little effect upon the

logic-generated noise. Total surface area is more important

27 www.national.com

ADC081000

than is total ground plane volume. Coupling between the typ-

ically noisy digital circuitry and the sensitive analog circuitry

can lead to poor performance that may seem impossible to

isolate and remedy. The solution is to keep the analog cir-

cuitry well separated from the digital circuitry.

High power digital components should not be located on or

near any linear component or power supply trace or plane that

services analog or mixed signal components as the resulting

common return current path could cause fluctuation in the

analog input “ground” return of the ADC, causing excessive

noise in the conversion result.

Generally, we assume that analog and digital lines should

cross each other at 90° to avoid getting digital noise into the

analog path. In high frequency systems, however, avoid

crossing analog and digital lines altogether. Clock lines

should be isolated from ALL other lines, analog AND digital.

The generally accepted 90° crossing should be avoided as

even a little coupling can cause problems at high frequencies.

Best performance at high frequencies is obtained with a

straight signal path.

The analog input should be isolated from noisy signal traces

to avoid coupling of spurious signals into the input. This is

especially important with the low level drive required of the

ADC081000. Any external component (e.g., a filter capacitor)

connected between the converter's input and ground should

be connected to a very clean point in the analog ground plane.

All analog circuitry (input amplifiers, filters, etc.) should be

separated from any digital components.

9.0 DYNAMIC PERFORMANCE

The ADC081000 is a.c. tested and its dynamic performance

is guaranteed. To meet the published specifications and avoid

jitter-induced noise, the clock source driving the CLK input

must exhibit low rms jitter. The allowable jitter is a function of

the input frequency and the input signal level, as described in

Section 4.0.

It is good practice to keep the ADC clock line as short as pos-

sible, to keep it well away from any other signals and to treat

it as a transmission line. Other signals can introduce jitter into

the clock signal. The clock signal can also introduce noise into

the analog path if not isolated from that path.

Best dynamic performance is obtained when the exposed pad

at the back of the package has a good connection to ground.

This is because this path from the die to ground is a lower

impedance than that offered by the package pins.

10.0 COMMON APPLICATION PITFALLS

Allowing loose power supply voltage tolerance. The

ADC081000 is specified for operation between 1.8 Volts to

2.0 Volts. Using a 1.8 Volt power supply then implies the need

for no negative tolerance. The best solution is to use an ad-

justable linear regulator such as the LM317 or LM1086 set for

1.9V as discussed in Section 7.1.

Driving the inputs (analog or digital) beyond the power

supply rails. For device reliability, all inputs should not go

more than 150 mV below the ground pins or 150 mV above

the supply pins. Exceeding these limits on even a transient

basis may not only cause faulty or erratic operation, but may

impair device reliability. It is not uncommon for high speed

digital circuits to exhibit undershoot that goes more than a volt

below ground. Controlling the impedance of high speed lines

and terminating these lines in their characteristic impedance

should control overshoot.

Care should be taken not to overdrive the inputs of the

ADC081000. Such practice may lead to conversion inaccu-

racies and even to device damage.

Incorrect analog input common mode voltage in the d.c.

coupled mode. As discussed in Sections 1.3 and 3.0, the

Input common mode voltage must remain within 50 mV of the

VCMO output and track that output, which has a variability with

temperature that must also be tracked. Distortion perfor-

mance will be degraded if the input common mode voltage is

more than 50 mV from VCMO.

Using an inadequate amplifier to drive the analog input.

Use care when choosing a high frequency amplifier to drive

the ADC081000 as many high speed amplifiers will have

higher distortion than will the ADC081000, resulting in overall

system performance degradation.

Driving the VBG pin to change the reference voltage. As

mentioned in Section 1.3, the reference voltage is intended to

be fixed to provide one of two different full-scale values (600

mVP-P and 800 mVP-P). Over driving this pin will not change

the full scale value, but can otherwise upset operation.

Driving the clock input with an excessively high level

signal. The ADC clock level should not exceed the level de-

scribed in the Operating Ratings Table or the input offset error

could increase.

Inadequate clock levels. As described in Section 4.0, insuf-

ficient clock levels can result in poor performance. Excessive

clock levels could result in the introduction of an input offset.

Using an excessively long clock signal trace, or having

other signals coupled to the clock signal trace. This will

cause the sampling interval to vary, causing excessive output

noise and a reduction in SNR performance.

Failure to provide adequate heat removal. As described in

Section 7.2, it is important to provide an adequate heat re-

moval to ensure device reliability. This can either be done with

adequate air flow or the use of a simple heat sink built into the

board. The backside pad should be grounded for best perfor-

mance.

www.national.com 28

ADC081000

Physical Dimensions inches (millimeters) unless otherwise noted

NOTES: UNLESS OTHERWISE SPECIFIED

REFERENCE JEDEC REGISTRATION MS-026, VARIATION BFB.

128-Lead Exposed Pad LQFP

Order Number ADC081000CIYB

NS Package Number VNX128A

29 www.national.com

ADC081000

Notes

ADC081000 High Performance, Low Power 8-Bit, 1 GSPS A/D Converter

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